EP1732364B1 - Circuit et procédé de commande de puissance d'un ballast électronique en fonction de la tension de réseau - Google Patents

Circuit et procédé de commande de puissance d'un ballast électronique en fonction de la tension de réseau Download PDF

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Publication number
EP1732364B1
EP1732364B1 EP06011520.1A EP06011520A EP1732364B1 EP 1732364 B1 EP1732364 B1 EP 1732364B1 EP 06011520 A EP06011520 A EP 06011520A EP 1732364 B1 EP1732364 B1 EP 1732364B1
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EP
European Patent Office
Prior art keywords
system voltage
power
threshold value
electronic device
event
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Active
Application number
EP06011520.1A
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German (de)
English (en)
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EP1732364A2 (fr
EP1732364A3 (fr
Inventor
Olaf Busse
Markus Heckmann
Reinhard Lecheler
Alfons Lechner
Siegfried Mayer
Thomas Pollischansky
Bernd Rudolph
Bernhard Schemmel
Kay Dr. Schmidtmann
Harald Schmitt
Thomas Dr. Siegmund
Arwed Storm
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Osram GmbH
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Osram GmbH
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Publication of EP1732364A2 publication Critical patent/EP1732364A2/fr
Publication of EP1732364A3 publication Critical patent/EP1732364A3/fr
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Publication of EP1732364B1 publication Critical patent/EP1732364B1/fr
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Classifications

    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
    • H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
    • H05B41/282—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices
    • H05B41/285—Arrangements for protecting lamps or circuits against abnormal operating conditions
    • H05B41/2851—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions
    • H05B41/2853—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions against abnormal power supply conditions
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
    • H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
    • H05B41/295—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices and specially adapted for lamps with preheating electrodes, e.g. for fluorescent lamps
    • H05B41/298—Arrangements for protecting lamps or circuits against abnormal operating conditions
    • H05B41/2981—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions
    • H05B41/2983—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions against abnormal power supply conditions

Definitions

  • the invention relates to a circuit arrangement for mains voltage-dependent power control of an electronic device and a method for mains voltage-dependent power control of such an electronic device. Moreover, the invention relates to an electronic ballast, which has a circuit arrangement for mains voltage-dependent power control.
  • electronic ballasts are provided for operating and adjusting electric lamps, in particular fluorescent lamps.
  • Such electronic ballasts are electrically connected between a network and the electric lamp and limit and regulate the one hand, the lamp current and on the other hand ensure safe ignition under the specific conditions.
  • high values of the recorded mains input current occur in the case of a mains undervoltage.
  • the absorbed current increases again, which leads to a battery power supply that this battery is discharged faster or has a shorter life.
  • high loads also occur on the input components during this operation.
  • the recording of the electrical power of the electronic ballast is curtailed when it falls below a certain input voltage.
  • the dimensioning of the down regulation and the design of the components is based on the stronger loads in DC operation.
  • AC operation AC operation
  • the reduction control with the same dimensions is used sustainably even at higher values of the mains undervoltage.
  • the working voltage range is expanded (eg 220V to 240VAC)
  • the reduction may not be too early.
  • the DE 100 56 347 A1 discloses a method of monitoring the performance of a film or video recording light and circuitry therefor.
  • the circuit is always connected to a battery, a network operation is not provided.
  • the US 2003/0102821 discloses a circuit arrangement for operating a low-pressure discharge lamp.
  • the circuit arrangement is always connected to a supply network, an operation on a DC voltage such as a battery and its detection is not provided.
  • the EP 0 563 801 A1 discloses an electronic ballast for operating a low pressure discharge lamp.
  • the circuit arrangement has a recognition of the type of input voltage, and in battery operation, a power feedback control is provided. A power feedback control in network operation is not provided.
  • the EP 0 450 728 A2 discloses an electronic operating device, which is designed for a network operation and for battery operation. The input voltage is measured and depending on the performance of the electronic control gear set.
  • the EP 1 271 745 A1 discloses a method and apparatus for operating electrical end users that may be powered by a grid or a battery.
  • the device has a frequency counter, by means of which operation on the network or on the battery can be detected.
  • various services are set and / or end consumers are switched off.
  • FIG. 1 is a control characteristic of an electrical power is shown, in which case a system performance, which characterizes the male electrical power of the electronic ballast, is plotted as a function of the mains voltage.
  • a regulation of the recording of the electrical power of the electronic ballast takes place without a finding that whether a DC operation or an AC operation of the electronic ballast is present.
  • the power consumption of the electronic ballast is thus reduced virtually quasi-flat if there is a drop below a certain input voltage.
  • a DC operation DC operation
  • the electrical power is kept substantially constant at mains voltages with values greater than a first mains voltage control value, which is approximately at 160V, up to this first mains voltage control value.
  • a first mains voltage control value which is approximately at 160V
  • a second mains voltage threshold which is in FIG. 1 is about 125V
  • the absorption of electrical power is reduced. If the mains voltage falls below this second mains voltage threshold, the electronic ballast is switched off and thus logically reduces the absorption of the electrical power to zero.
  • the reduction in the case of an AC operation adversely affects even at higher values of the mains voltage. How to do that FIG.
  • the object is achieved by a circuit arrangement having the features of claim 1, and an electronic ballast having the features of claim 8, solved. Furthermore, the object is achieved by a method for mains voltage-dependent power control of an electronic device having the features of claim 10.
  • a circuit arrangement for line voltage-dependent power control of an electronic device comprises means with which a direct current operation or an alternating current operation of the electronic device can be detected. Another essential idea of the invention is to be seen in that the circuit arrangement also has a control unit in which at least one characteristic for a DC operation and at least one characteristic for an AC operation is stored, wherein the control unit is designed such that depending on the detected operation of electronic device, a regulation of the electronic device to be included in the electrical power according to the associated characteristic is feasible.
  • Each of the characteristic curves characterizes a course of a system power or an electrical power to be absorbed by the electronic device as a function of the mains voltage.
  • the means with which the operation of the electronic device is detectable advantageously comprise a discriminator stage.
  • the stored in the control unit characteristic for DC operation and the stored characteristic for AC operation have at least partially different characteristics curves.
  • the control unit according to the invention is designed such that in the case of a detected DC operation, a power control is performed such that the electrical power is kept substantially constant with a drop in the mains voltage up to a first Netzwoodsschwellwert. Furthermore, the control unit is designed such that in the case of a detected DC operation, a power control is carried out such that the electrical power is lowered at a fall in the mains voltage below the first mains voltage threshold continuously decreasing up to a second mains voltage threshold.
  • the control unit is also designed such that in the case of a detected DC operation, a power control is performed such that when a drop in the mains voltage below the second mains voltage threshold, the electronic device is turned off.
  • the control unit is designed such that in the case of such a detected AC operation, a power control is performed so that the electric power at a drop in the mains voltage up to a third Netzwoodsschwellwert in Is kept substantially constant and the electrical power is lowered at a fall in the mains voltage below the third Netzwoodsschwellwert continuously decreasing up to a fourth Netzwoodsschwellwert.
  • the control unit is preferably designed such that in the case of a detected AC operation, a power control is performed such that at a drop in the mains voltage below the fourth mains voltage threshold, the electronic device is also switched off.
  • the first and / or the second mains voltage threshold value and the third and / or the fourth mains voltage threshold value can be variably determined in an advantageous manner.
  • the first and third mains voltage threshold and the second and fourth mains voltage thresholds are the same.
  • the continuous drop in electrical power between the first and second grid voltage thresholds is advantageously steeper than the continuous drop in electrical power between the third and fourth grid voltage thresholds.
  • the electronic device is designed as an electronic ballast.
  • electronic ballasts with a PFC (Power Factor Correction) input stage thus a mains voltage-dependent power control can be performed in an optimized manner.
  • the electrical output power of the PFC input stage can be regulated depending on the mains voltage.
  • Another aspect of the invention relates to an electronic ballast for operating electric lamps, in particular fluorescent lamps, which has a circuit arrangement according to the invention or an advantageous embodiment of the circuit arrangement according to the invention.
  • FIG. 2 a simplified block diagram representation of an electronic ballast 3 is shown, which has a circuit arrangement according to the invention.
  • the circuit arrangement according to the invention comprises a discriminator stage 31 with which it is detected whether a DC operation or an AC operation of the electronic ballast 3 is present.
  • the electronic ballast 3 comprises a control unit 32 which is electrically connected to the discriminator 31.
  • a system power-mains voltage characteristic 321 power-mains voltage characteristic
  • a system power mains voltage characteristic 322 power-mains voltage characteristic for an AC operation of the electronic ballast 3 is stored.
  • the control unit 32 is electrically connected to a PFC input stage 33 of the electronic ballast 3.
  • the curves of curves 321 and 322 are shown.
  • the characteristic curve 321 stored for the DC operation of the electronic ballast 3 is substantially constant above a first mains voltage threshold, which in the embodiment shown is at a mains voltage threshold of approximately 180V.
  • the system performance of the electronic ballast 3 is adjusted in accordance with the sloping characteristic shown. If, in the DC operation of the electronic ballast 3, the mains voltage applied to the electronic ballast 3 drops below the second mains voltage threshold at approximately 140V, the electronic ballast 3 is switched off.
  • the characteristic curve 322 shown which is used to control the system performance in an AC operation of the electronic ballast 3 of the control unit 32.
  • a third mains voltage threshold which corresponds to the first Netzwoodsschwellwert in the embodiment shown, and thus also is approximately at 180V, a constant power control.
  • a fourth mains voltage threshold which in the exemplary embodiment corresponds to the second mains voltage threshold and is therefore approximately 140V, a continuously decreasing power control takes place.
  • the electronic ballast 3 is switched off in AC operation falls below the fourth mains voltage threshold.
  • the slope of the characteristic 321 in the range between the first and the second mains voltage threshold is steeper than the slope of the characteristic 322 between the third and the fourth mains voltage threshold.
  • This control behavior contributes to the extension of the service life of the battery supply after falling below the first mains voltage threshold.
  • the system performance or the electrical power of the electronic ballast 3 in DC operation between the first and the second Netzwoodsschwellwert from a value of about 100 is adjusted to a value of about 60.
  • the values 100 and 60 indicate the system performance in percent of the rated power of the electronic ballast 3.
  • the system power between the third and the fourth mains voltage threshold value is reduced from a value of about 100 to a value of about 80.
  • the characteristics 321 and 322 can also be shifted from each other. It is also possible that the first and third Netzwoodsschwellwert and / or the second and fourth Netzwoodsschwellwert differ from each other.
  • the system in DC operation, when the first mains voltage threshold value is undershot, the system is also switched directly to a significantly reduced system performance, in which, for example, the system power is immediately reduced to a value of approximately 60%.
  • FIG. 4 shows an embodiment of a circuit arrangement.
  • a mains voltage UN generates via a rectifier GL a rectified mains voltage UGL with respect to a reference potential GND.
  • a choke L01, a diode D01 and a transistor T01 are connected in a known manner as a step-up converter, which generates a bus voltage UBUS on a storage capacitor C01.
  • the bus voltage UBUS feeds an electronic ballast ECG for a fluorescent lamp, which is shown schematically in a known half-bridge arrangement.
  • the transistor T01 of the boost converter is controlled by an integrated circuit Ic01 via a resistor R01 such that a power factor corrector with respect to the mains voltage and the resulting grid current results.
  • Integrated circuits that enable power factor correction are widely used in the marketplace. Examples of these are ICB1FL02G from Infineon, or IR2166 and IR1150S from International Rectifier.
  • the circuit Ic01 has a feedback input FB to which a voltage proportional to the bus voltage UBUS is supplied. First, this is done by a voltage divider consisting of the resistors R1 and R2, which is connected between the bus voltage UBUS and the reference potential GND. The feedback input FB is connected to the connection point of the resistors R1 and R2. This closes a control loop, which keeps the bus voltage UBUS constant regardless of the mains voltage UN. At the same time, the circuit Ic01 drives the transistor T01 so that the mains current is approximately proportional to the mains voltage.
  • the mains voltage UN is an alternating voltage (AC voltage) with a mains frequency of 50-60Hz.
  • the mains voltage UN is a DC voltage (DC voltage).
  • AC voltage alternating voltage
  • DC voltage DC voltage
  • the current load of the transistor T01 in DC operation is greater than in AC operation.
  • the transistor T01 must therefore be designed for the higher load at DC voltage, which leads to greater component complexity compared to the normal operating case. Therefore, it is advantageous in the circuit arrangement according to FIG. 4 reduces the input power at DC voltage.
  • a discriminator stage which is the following Components comprises: the capacitors C10, C11; the diodes D10, D11; the resistors R11, R12.
  • the series connection of the capacitor C10 and the resistor R12 is connected in parallel to the rectified mains voltage UGL. Parallel to the resistor R12, the series circuit of the diode D11 and the capacitor C11 is connected. Parallel to capacitor C11, the diode D10 and the resistor R11 are still connected.
  • an AC voltage with respect to the reference potential GND is formed at the junction of the capacitor C10 and the resistor R12.
  • This AC voltage is rectified by the diode D11 and the capacitor C11 is charged with this rectified voltage.
  • On the capacitor C11 is thus a voltage relative to the reference potential GND available, if the mains voltage is an AC voltage.
  • the resistor R11 is used to discharge the capacitor C11 in the absence of the AC voltage.
  • the diode D10 is a Zener diode and thereby limits the voltage across the capacitor C11 for the protection of further evaluation stages.
  • the capacitor C10 In the event that the mains voltage is a DC voltage, in the steady state, the capacitor C10 is charged to the DC voltage. Thus, the voltage across resistor R12 is zero and also the voltage across capacitor C11 is zero.
  • the voltage across the capacitor C10 evaluates a switch S10, which in accordance with FIG. 4 is designed as a MOSFET.
  • Source of the switch S10 is connected to the reference potential.
  • Gate and source form the control input of the switch S10 and are connected to the capacitor C10.
  • Drain of the switch S10 is connected via a resistor R10 to the feedback input FB. If the mains voltage UN is now an AC voltage, the switch S10 is turned on by the voltage across the capacitor C11. Thus, the resistor R10 is connected in parallel to the resistor R1.
  • the circuit Ic01 controls the transistor T01 so that a higher bus voltage UBUS sets in the AC voltage case than in the DC voltage case.
  • the respective absolute values of the bus voltage UBUS can be determined by the selection of the resistors R1, R2 and R10.
  • the bus voltage UBUS is lower in the DC voltage case than in the AC voltage case, the power related to the mains voltage is lower in the DC voltage case. This advantageously reduces the load on a battery in the DC voltage case.
  • the load of the transistor T01 in the DC voltage case is also advantageously reduced.
  • the ratio of the bus voltages in the AC voltage case and DC voltage case can be set so that the load of the transistor T01 is the same in both cases.
  • no more load-bearing transistor T01 is required for the DC voltage case.
  • the characteristic curve which describes the relationship between the input power PIN of the circuit arrangement and the mains voltage UN is in the exemplary embodiment in each case a constant.
  • the input power PIN is lower in the DC voltage case than in the AC voltage case.
  • FIG. 5 a further embodiment of a circuit arrangement is shown.
  • the difference from the embodiment according to FIG. 4 consists essentially in that the switch S10 off FIG. 4 in FIG. 5 was replaced by a switch S20.
  • the switch S20 is now designed as a bipolar transistor. This allows the voltage-limiting Zener diode D10 off FIG. 4 omitted.
  • the base of the switch S20 is connected via a current-limiting resistor R24 to the capacitor C11.
  • the base of the switch S20 is also connected via a resistor R23 to the reference potential GND. It can thus be adjusted at which voltage value on the capacitor C11 the switch S20 closes.
  • an emitter resistor R21 is still inserted to reduce the sensitivity of the switch S20 to noise.
  • FIG. 6a shows a diagram of the relationship between mains voltage UN and input power PIN without DC control.
  • the input power PIN is constant above the mains voltage UN and for the AC voltage case and the DC voltage case approximately the same.
  • FIG. 6b shows a diagram of the relationship between mains voltage UN and power loss PV without feedback in DC operation.
  • the power loss PV describes the losses of the transistor T01 from the FIGS. 4 or 5 . It can be clearly seen that the losses in the DC voltage case are approx. 0.1 W higher than in the AC voltage case. Without feedback control in the DC voltage case, the transistor T01 must therefore be designed for the load in the DC voltage case. This is uneconomical, since the DC voltage case rarely occurs in emergency power operation.
  • FIG. 6c shows a diagram of the relationship between mains voltage UN and input power PIN with back regulation in DC operation.
  • the input power PIN is constant above the mains voltage UN. Different from FIG. 6a For the DC voltage case, the input power PIN is now lowered by approx. 30 W compared to the AC voltage drop.
  • FIG. 6d shows a diagram of the relationship between mains voltage UN and power loss PV with back regulation in DC operation.
  • the power loss PV describes the losses of the transistor T01 from the FIGS. 4 or 5 ,
  • the circumstances are opposite FIG. 6b now vice versa: It can be clearly seen that the losses in the DC voltage case are about 0.1 W lower than in the AC voltage case.
  • the transistor T01 can be designed economically for the normal case of the AC voltage.

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  • Rectifiers (AREA)
  • Control Of Electrical Variables (AREA)
  • Dc-Dc Converters (AREA)

Claims (10)

  1. Agencement de circuit pour la régulation de puissance d'un appareil électronique (3) en fonction de la tension de réseau, l'agencement de circuit comportant des moyens (31) conçus pour détecter un fonctionnement en courant continu ou un fonctionnement en courant alternatif de l'appareil électronique (3), et l'agencement de circuit comportant une unité de régulation (32) dans laquelle sont déposées au moins une caractéristique puissance-tension de réseau (321) pour un fonctionnement en courant continu et au moins une caractéristique puissance-tension de réseau (322) pour un fonctionnement en courant alternatif de l'appareil électronique (3), la caractéristique puissance-tension de réseau (321) pour un fonctionnement en courant continu et la caractéristique puissance-tension de réseau (322) pour un fonctionnement en courant alternatif déposées dans l'unité de régulation (32) ayant des courbes au moins partiellement différentes,
    sachant que l'unité de régulation (32) est conçue pour effectuer en fonction du fonctionnement détecté de l'appareil électronique (3), un réglage de la puissance électrique absorbée de l'appareil électrique (3) selon la caractéristique puissance-tension de réseau (321, 322) associée,
    caractérisé en ce que
    l'unité de régulation (32) est conçue de telle manière qu'en cas de détection d'un fonctionnement en courant continu, elle maintient sensiblement constante la puissance électrique de l'appareil électronique (3) selon la caractéristique puissance-tension de réseau (321) pour le fonctionnement en courant continu lorsque la tension de réseau descend jusqu'à une première valeur seuil de tension de réseau, et abaisse la puissance électrique de façon continue lorsque la tension de réseau descend au-dessous de la première valeur seuil de tension de réseau jusqu'à une deuxième valeur seuil de tension de réseau, et en ce que l'unité de régulation (32) est conçue de telle manière qu'en cas de détection d'un fonctionnement en courant alternatif, elle maintient sensiblement constante la puissance électrique de l'appareil électronique (3) selon la caractéristique puissance-tension de réseau (322) déposée pour le fonctionnement en courant alternatif lorsque la tension de réseau descend jusqu'à une troisième valeur seuil de tension de réseau, et abaisse la puissance électrique de façon continue lorsque la tension de réseau descend au-dessous de la troisième valeur seuil de tension de réseau jusqu'à une quatrième valeur seuil de tension de réseau.
  2. Agencement de circuit selon la revendication 1,
    caractérisé en ce que
    les moyens de détection du fonctionnement de l'appareil électronique (3) comportent un étage discriminateur (31).
  3. Agencement de circuit selon la revendication 1,
    caractérisé en ce que
    l'unité de régulation (32) est conçue de telle manière qu'en cas de détection d'un fonctionnement en courant continu selon la caractéristique puissance-tension de réseau (321) déposée pour le fonctionnement en courant continu, elle met l'appareil électronique (3) hors tension lorsque la tension de réseau descend au-dessous de la deuxième valeur seuil de tension de réseau.
  4. Agencement de circuit selon la revendication 1,
    caractérisé en ce que
    l'unité de régulation (32) est conçue de telle manière qu'en cas de détection d'un fonctionnement en courant alternatif selon la caractéristique puissance-tension de réseau (322) déposée pour le fonctionnement en courant alternatif, elle met l'appareil électronique (3) hors tension lorsque la tension de réseau descend au-dessous de la quatrième valeur seuil de tension de réseau.
  5. Agencement de circuit selon la revendication 3 et 4,
    caractérisé en ce que
    la première et/ou la deuxième valeur seuil de tension de réseau et la troisième et/ou la quatrième valeur seuil de tension de réseau peuvent être fixées d'une manière variable.
  6. Agencement de circuit selon la revendication 3 et 4,
    caractérisé en ce que
    la première valeur seuil de tension de réseau correspond à la quatrième valeur seuil de tension de réseau et la troisième valeur seuil de tension de réseau correspond à la quatrième valeur seuil de tension de réseau.
  7. Agencement de circuit selon la revendication 6,
    caractérisé en ce que
    la baisse continue de la puissance électrique entre la première et la deuxième valeur seuil de tension de réseau selon la caractéristique puissance-tension de réseau (321) pour le fonctionnement en courant continu est plus abrupte que la baisse continue de la puissance électrique entre la troisième et la quatrième valeur seuil de tension de réseau selon la caractéristique puissance-tension de réseau (322) pour le fonctionnement en courant alternatif.
  8. Ballast électronique pour faire fonctionner des lampes électriques, en particulier des lampes fluorescentes, comportant un agencement de circuit selon l'une des revendications 1 à 7.
  9. Ballast électronique selon la revendication 8,
    caractérisé par
    un étage d'entrée PFC (33),
    l'agencement de circuit étant conçue pour régler la puissance électrique de sortie de l'étage d'entrée PFC (33) en fonction de la tension de réseau.
  10. Procédé pour la régulation de puissance d'un appareil électronique (3) en fonction de la tension de réseau, l'appareil électronique comportant des moyens (31) permettant de détecter un fonctionnement en courant continu ou un fonctionnement en courant alternatif de l'appareil électronique (3), et ledit appareil électronique comportant une unité de régulation (32) dans laquelle sont déposées au moins une caractéristique puissance-tension de réseau (321) pour un fonctionnement en courant continu et au moins une caractéristique puissance-tension de réseau (322) pour un fonctionnement en courant alternatif de l'appareil électronique (3), la caractéristique puissance-tension de réseau (321) déposée pour un fonctionnement en courant continu et la caractéristique puissance-tension de réseau (322) déposée pour un fonctionnement en courant alternatif ayant des courbes au moins partiellement différentes, sachant que l'unité de régulation (32) effectue un réglage de la puissance électrique à absorber de l'appareil électrique (3) selon la caractéristique puissance-tension de réseau (321, 322) associée en fonction du fonctionnement détecté de l'appareil électronique (3),
    caractérisé en ce que
    en cas de détection d'un fonctionnement en courant continu, l'unité de régulation (32) effectue une régulation de puissance de telle manière qu'elle maintient sensiblement constante la puissance électrique de l'appareil électronique (3) selon la caractéristique puissance-tension de réseau (321) déposée pour le fonctionnement en courant continu lorsque la tension de réseau descend jusqu'à une première valeur seuil de tension de réseau, et abaisse la puissance électrique de façon continue lorsque la tension de réseau descend au-dessous de la première valeur seuil de tension de réseau jusqu'à une deuxième valeur seuil de tension de réseau, et en ce que
    en cas de détection d'un fonctionnement en courant alternatif, l'unité de régulation (32) effectue une régulation de puissance de telle manière qu'elle maintient sensiblement constante la puissance électrique de l'appareil électronique (3) selon la caractéristique puissance-tension de réseau (322) déposée pour le fonctionnement en courant alternatif lorsque la tension de réseau descend jusqu'à une troisième valeur seuil de tension de réseau, et qu'elle abaisse la puissance électrique de façon continue lorsque la tension de réseau descend au-dessous de la troisième valeur seuil de tension de réseau jusqu'à une quatrième valeur seuil de tension de réseau.
EP06011520.1A 2005-06-10 2006-06-02 Circuit et procédé de commande de puissance d'un ballast électronique en fonction de la tension de réseau Active EP1732364B1 (fr)

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Application Number Priority Date Filing Date Title
DE102005027015A DE102005027015A1 (de) 2005-06-10 2005-06-10 Schaltungsanordnung und Verfahren zur netzspannungsabhängigen Leistungsregelung eines elektronischen Geräts, insbesondere eines elektronischen Vorschaltgeräts

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EP1732364A2 EP1732364A2 (fr) 2006-12-13
EP1732364A3 EP1732364A3 (fr) 2011-09-21
EP1732364B1 true EP1732364B1 (fr) 2018-04-11

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EP06011520.1A Active EP1732364B1 (fr) 2005-06-10 2006-06-02 Circuit et procédé de commande de puissance d'un ballast électronique en fonction de la tension de réseau

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EP (1) EP1732364B1 (fr)
CN (1) CN1893757B (fr)
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US7301291B1 (en) * 2006-10-02 2007-11-27 Osram Sylvania Inc. Power controller having current limited RMS regulated output
RU2526375C2 (ru) 2008-05-06 2014-08-20 Конинклейке Филипс Электроникс Н.В. Устройство для подключения источника питания к светильнику
DE202012012473U1 (de) 2012-02-03 2013-03-01 Eckerle Industrie-Elektronik Gmbh Vorrichtung zur Ansteuerung einer Leuchtstofflampe
EP3651312A1 (fr) 2018-11-12 2020-05-13 polynom ag Unité de lumière de secours, installation d'éclairage de secours et élément de lumière de secours
CN111693817B (zh) * 2020-06-10 2022-12-13 深圳市创仁科技有限公司 一种调光设备的测试方法

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EP1271745A1 (fr) * 2001-06-18 2003-01-02 Almat AG Procédé pour l'exploitation de consommateurs d'électricité et dispositif utilisant un tel procédé

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DE4210367A1 (de) * 1992-03-30 1993-10-07 Abb Patent Gmbh Elektronisches Vorschaltgerät
DE9204380U1 (fr) 1992-03-31 1993-08-12 Kran- Und Stahlbau Gmbh, 17036 Neubrandenburg, De
US5872429A (en) * 1995-03-31 1999-02-16 Philips Electronics North America Corporation Coded communication system and method for controlling an electric lamp
DE19820615A1 (de) * 1998-05-08 1999-11-11 Walter Holzer Verfahren und Vorrichtung zur Regelung von Energiesparlampen
US5973455A (en) * 1998-05-15 1999-10-26 Energy Savings, Inc. Electronic ballast with filament cut-out
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DE10056347A1 (de) 2000-11-14 2002-05-16 Bron Elektronik Ag Verfahren zur Überwachung der Leistung einer Film- oder Videoaufnahmeleuchte sowie Vorschaltgerät zur Durchführung eines solchen Verfahrens
US6507157B1 (en) * 2001-09-25 2003-01-14 Koninklijke Philips Electronics N.V. Electronic ballast system with dual power and dimming capability
CN1579113A (zh) 2001-10-29 2005-02-09 皇家飞利浦电子股份有限公司 镇流电路
EP1435764A1 (fr) * 2002-06-07 2004-07-07 Matsushita Electric Industrial Co., Ltd. Dispositif d'eclairage de lampe a decharge sans electrode, lampe fluorescente sans electrode du type ampoule electrique et dispositif d'eclairage de lampe a decharge
AU2003242025A1 (en) * 2002-06-07 2003-12-22 Matsushita Electric Industrial Co., Ltd. Electrodeless light bulb type fluorescent lamp and discharge lamp lighting device
DE202004004462U1 (de) * 2004-03-22 2004-06-17 Tridonicatco Gmbh & Co. Kg Schaltungsanordnung zum Betreiben einer Lampe mit Batterie-Versorgung

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EP1271745A1 (fr) * 2001-06-18 2003-01-02 Almat AG Procédé pour l'exploitation de consommateurs d'électricité et dispositif utilisant un tel procédé

Also Published As

Publication number Publication date
EP1732364A2 (fr) 2006-12-13
DE102005027015A1 (de) 2006-12-14
CN1893757B (zh) 2013-01-02
EP1732364A3 (fr) 2011-09-21
CN1893757A (zh) 2007-01-10

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