EP1732364A2 - Circuit et procédé de commande de puissance d'un ballast électronique en fonction de la tension de réseau - Google Patents

Circuit et procédé de commande de puissance d'un ballast électronique en fonction de la tension de réseau Download PDF

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Publication number
EP1732364A2
EP1732364A2 EP06011520A EP06011520A EP1732364A2 EP 1732364 A2 EP1732364 A2 EP 1732364A2 EP 06011520 A EP06011520 A EP 06011520A EP 06011520 A EP06011520 A EP 06011520A EP 1732364 A2 EP1732364 A2 EP 1732364A2
Authority
EP
European Patent Office
Prior art keywords
power
mains voltage
circuit arrangement
electronic device
arrangement according
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Granted
Application number
EP06011520A
Other languages
German (de)
English (en)
Other versions
EP1732364B1 (fr
EP1732364A3 (fr
Inventor
Olaf Busse
Markus Heckmann
Reinhard Lecheler
Alfons Lechner
Siegfried Mayer
Thomas Pollischansky
Bernd Rudolph
Bernhard Schemmel
Kay Dr. Schmidtmann
Harald Schmitt
Thomas Dr. Siegmund
Arwed Storm
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Osram GmbH
Original Assignee
Osram GmbH
Patent Treuhand Gesellschaft fuer Elektrische Gluehlampen mbH
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Osram GmbH, Patent Treuhand Gesellschaft fuer Elektrische Gluehlampen mbH filed Critical Osram GmbH
Publication of EP1732364A2 publication Critical patent/EP1732364A2/fr
Publication of EP1732364A3 publication Critical patent/EP1732364A3/fr
Application granted granted Critical
Publication of EP1732364B1 publication Critical patent/EP1732364B1/fr
Active legal-status Critical Current
Anticipated expiration legal-status Critical

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Classifications

    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
    • H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
    • H05B41/282—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices
    • H05B41/285—Arrangements for protecting lamps or circuits against abnormal operating conditions
    • H05B41/2851—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions
    • H05B41/2853—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions against abnormal power supply conditions
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
    • H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
    • H05B41/295—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices and specially adapted for lamps with preheating electrodes, e.g. for fluorescent lamps
    • H05B41/298—Arrangements for protecting lamps or circuits against abnormal operating conditions
    • H05B41/2981—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions
    • H05B41/2983—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions against abnormal power supply conditions

Definitions

  • the invention relates to a circuit arrangement for mains voltage-dependent power control of an electronic device and a method for mains voltage-dependent power control of such an electronic device. Moreover, the invention relates to an electronic ballast, which has a circuit arrangement for mains voltage-dependent power control.
  • electronic ballasts are provided for operating and adjusting electric lamps, in particular fluorescent lamps.
  • Such electronic ballasts are electrically connected between a network and the electric lamp and limit and regulate the one hand, the lamp current and on the other hand ensure safe ignition under the specific conditions.
  • high values of the recorded mains input current occur in the case of a mains undervoltage.
  • the absorbed current increases again, which leads to a battery power supply that this battery is discharged faster or has a shorter life.
  • high loads also occur on the input components during this operation.
  • the recording of the electrical power of the electronic ballast is curtailed when it falls below a certain input voltage.
  • the dimensioning of the down regulation and the design of the components is based on the stronger loads in DC operation.
  • AC operation AC operation
  • the reduction control with the same dimensions is used sustainably even at higher values of the mains undervoltage.
  • the working voltage range eg 220V to 240VAC
  • the reduction may not be too early. Due to this, higher operating currents must be permitted in DC operation.
  • the slow discharge of a possible battery supply is disregarded in this interpretation.
  • FIG. 1 shows a control characteristic of an electrical power, whereby a system power which characterizes the electrical power of the electronic ballast to be received is plotted as a function of the mains voltage.
  • a system power which characterizes the electrical power of the electronic ballast to be received is plotted as a function of the mains voltage.
  • the commercially available power-controlled electronic ballasts is a Abreglung the recording of the electrical power of the electronic ballast without a determination of whether a DC operation or an AC operation of the electronic ballast is present.
  • the power consumption of the electronic ballast is thus reduced virtually quasi-flat if there is a drop below a certain input voltage.
  • a reduction takes place, as indicated by the graph 1.
  • the electrical power is kept substantially constant at mains voltages with values greater than a first mains voltage control value, which is approximately at 160V, up to this first mains voltage control value.
  • a first mains voltage control value which is approximately at 160V
  • a second mains voltage threshold which is approximately 125V in FIG. 1
  • the absorption of the electrical power is reduced. If the mains voltage falls below this second mains voltage threshold, the electronic ballast is switched off and thus logically reduces the absorption of the electrical power to zero.
  • the reduction in the case of an AC operation adversely affects even at higher values of the mains voltage.
  • an essentially constant control of the electrical power consumption of the electronic ballast in the mains voltage range is greater than approximately 180V, the value of approximately 180V representing a third mains voltage threshold value.
  • a fourth mains voltage threshold value which in the exemplary embodiment is approximately 140V, a reduction of this electrical power consumption of the electronic ballast takes place.
  • the electronic ballast is switched off again and thus a reduction of the power consumption to 0. From the illustration in FIG. 1, the already mentioned disadvantages of the known power-controlled electronic ballasts are once again clear in the curves 1 and 2 shown to recognize or to understand.
  • the object is achieved by a circuit arrangement having the features of claim 1, and an electronic ballast having the features of claim 14, solved. Furthermore, the object is achieved by a method for mains voltage-dependent power control of an electronic device having the features of claim 16.
  • a circuit arrangement for line voltage-dependent power control of an electronic device comprises means with which a direct current operation or an alternating current operation of the electronic device can be detected. Another essential idea of the invention is to be seen in that the circuit arrangement also has a control unit in which at least one characteristic for a DC operation and at least one characteristic for an AC operation is stored, wherein the control unit is designed such that depending on the detected operation of electronic device, a regulation of the electronic device to be included in the electrical power according to the associated characteristic is feasible.
  • Each of the characteristic curves characterizes a course of a system power or an electrical power to be absorbed by the electronic device as a function of the mains voltage.
  • the means with which the operation of the electronic device is detectable advantageously comprise a discriminator stage.
  • the stored in the control unit characteristic for DC operation and the stored characteristic for AC operation have at least partially different characteristic curves.
  • the control unit is preferably designed such that in the case of a detected DC operation, a power control is performed such that the electrical power is kept substantially constant with a drop in the mains voltage up to a first Netzwoodsschwellwert. Furthermore, the control unit is designed such that in the case of a detected DC operation, a power control is carried out such that the electrical power is lowered at a fall in the mains voltage below the first mains voltage threshold continuously decreasing up to a second mains voltage threshold.
  • the control unit is also designed such that in the case of a detected DC operation, a power control is performed such that when the mains voltage drops below the second mains voltage threshold, the electronic device is turned off.
  • the control unit is preferably designed such that, in the case of AC operation thus detected, power control is performed such that the electric power is decreased up to a third mains voltage threshold is kept substantially constant and in an advantageous manner, the electrical power is lowered at a fall in the mains voltage below the third mains voltage threshold continuously decreasing up to a fourth Netzwoodsschwellwert.
  • the control unit is preferably designed such that in the case of a detected AC operation, a power control is performed such that at a drop in the mains voltage below the fourth mains voltage threshold, the electronic device is also switched off.
  • the first and / or the second mains voltage threshold value and the third and / or the fourth mains voltage threshold value can be variably determined in an advantageous manner.
  • the first and third mains voltage threshold and the second and fourth mains voltage thresholds are the same.
  • the continuous drop in electrical power between the first and second grid voltage thresholds is advantageously steeper than the continuous drop in electrical power between the third and fourth grid voltage thresholds.
  • the electronic device is designed as an electronic ballast.
  • electronic ballasts with a PFC (Power Factor Correction) input stage thus a mains voltage-dependent power control can be performed in an optimized manner.
  • the electrical output power of the PFC input stage can be regulated depending on the mains voltage.
  • Another aspect of the invention relates to an electronic ballast for operating electric lamps, in particular fluorescent lamps, which has a circuit arrangement according to the invention or an advantageous embodiment of the circuit arrangement according to the invention.
  • a mains voltage-dependent power control of an electronic device is performed.
  • the electronic device comprises means with which a direct current operation or an alternating current operation of the electronic device is detected and moreover has a control unit in which at least one power-mains voltage characteristic for a direct current operation and at least one power mains voltage characteristic for an alternating current operation are stored be, depending on the detected operation of the electronic device, a regulation of the electrical power recorded by the electronic device is performed according to the associated characteristic by the control unit.
  • the characteristic curves characterize an electrical power to be absorbed by the electronic device as a function of a mains voltage.
  • the circuit arrangement according to the invention comprises a discriminator stage 31 with which it is detected whether a DC operation or an AC operation of the electronic ballast 3 is present.
  • the electronic ballast 3 comprises a control unit 32 which is electrically connected to the discriminator 31.
  • a system power-mains voltage characteristic 321 power-mains voltage characteristic
  • a system power mains voltage characteristic 322 power-mains voltage characteristic for an AC operation of the electronic ballast 3 is stored.
  • the control unit 32 is electrically connected to a PFC input stage 33 of the electronic ballast 3.
  • the control unit 32 is characterized according to the invention in that for AC operation and DC operation of the electronic ballast 3 individual different characteristics 321 and 322 are present, according to this regulation of the electrical system performance and the male electrical power of the electronic ballast 3 can be controlled optimized ,
  • FIG. 3 shows the curves of characteristic curves 321 and 322.
  • the characteristic curve 321 stored for the DC operation of the electronic ballast 3 is substantially constant above a first mains voltage threshold, which in the embodiment shown is at a mains voltage threshold of approximately 180V.
  • a first mains voltage threshold which in the embodiment shown is at a mains voltage threshold of approximately 180V.
  • the system performance of the electronic ballast 3 is adjusted according to the sloping characteristic shown. If, in the DC operation of the electronic ballast 3, the mains voltage applied to the electronic ballast 3 drops below the second mains voltage threshold at approximately 140V, the electronic ballast 3 is switched off.
  • the characteristic curve 322 is shown in FIG. 3, which is used by the control unit 32 to control the system power during an AC operation of the electronic ballast 3.
  • a third mains voltage threshold value which in the exemplary embodiment shown corresponds to the first mains voltage threshold value and thus likewise approximately at 180V
  • a constant power control takes place.
  • a fourth mains voltage threshold which in the exemplary embodiment corresponds to the second mains voltage threshold and is therefore approximately 140V
  • a continuously decreasing power control takes place.
  • the electronic ballast 3 is switched off in AC operation falls below the fourth mains voltage threshold.
  • FIG. 3 is used by the control unit 32 to control the system power during an AC operation of the electronic ballast 3.
  • the slope of the characteristic curve 321 in the region between the first and the second mains voltage threshold value is steeper than the slope of the characteristic curve 322 between the third and the fourth system voltage threshold value.
  • This control behavior contributes to the extension of the service life of the battery supply after falling below the first mains voltage threshold.
  • the system power or the electrical power of the electronic ballast 3 consumed in DC operation between the first and the second mains voltage threshold value is reduced from a value of approximately 100 to a value of approximately 60.
  • the values 100 and 60 indicate the system performance in percent of the rated power of the electronic ballast 3.
  • the system power between the third and fourth mains voltage threshold values is reduced from a value of approximately 100 to a value of approximately 80.
  • the characteristics 321 and 322 can also be shifted from each other. It is also possible that the first and third Netzwoodsschwellwert and / or the second and fourth Netzwoodsschwellwert differ from each other.
  • the system in DC operation, when the first mains voltage threshold value is undershot, the system is also switched directly to a significantly reduced system performance, in which, for example, the system power is immediately reduced to a value of approximately 60%.
  • FIG. 4 shows an exemplary embodiment of a circuit arrangement according to the invention.
  • a mains voltage UN generates via a rectifier GL a rectified mains voltage UGL with respect to a reference potential GND.
  • a choke L01, a diode D01 and a transistor T01 are connected in a known manner as a step-up converter, which generates a bus voltage UBUS on a storage capacitor C01.
  • the bus voltage UBUS feeds an electronic ballast ECG for a fluorescent lamp, which is shown schematically in a known half-bridge arrangement.
  • the transistor T01 of the boost converter is controlled by an integrated circuit Ic01 via a resistor R01 such that a power factor corrector with respect to the mains voltage and the resulting grid current results.
  • Integrated circuits that enable power factor correction are widely used in the marketplace. Examples of these are ICB1FL02G from Infineon, or IR2166 and IR1150S from International Rectifier.
  • the circuit Ic01 has a feedback input FB to which a voltage proportional to the bus voltage UBUS is supplied. First, this is done by a voltage divider consisting of the resistors R1 and R2, which is connected between the bus voltage UBUS and the reference potential GND. The feedback input FB is connected to the connection point of the resistors R1 and R2. This closes a control loop, which keeps the bus voltage UBUS constant regardless of the mains voltage UN. At the same time, the circuit Ic01 drives the transistor T01 so that the mains current is approximately proportional to the mains voltage.
  • the mains voltage UN is an alternating voltage (AC voltage) with a mains frequency of 50-60Hz.
  • the mains voltage UN is a DC voltage (DC voltage).
  • AC voltage alternating voltage
  • DC voltage DC voltage
  • the current load of the transistor T01 in DC operation is greater than in AC operation.
  • the transistor T01 must therefore be designed for the higher load at DC voltage, which leads to greater component complexity compared to the normal operating case.
  • the input power is advantageously reduced at DC voltage.
  • a discriminator stage which is the following Components comprises: the capacitors C10, C11; the diodes D10, D11; the resistors R11, R12.
  • the series connection of the capacitor C10 and the resistor R12 is connected in parallel to the rectified mains voltage UGL. Parallel to the resistor R12, the series circuit of the diode D11 and the capacitor C11 is connected. Parallel to capacitor C11, the diode D10 and the resistor R11 are still connected.
  • an AC voltage with respect to the reference potential GND is formed at the junction of the capacitor C10 and the resistor R12.
  • This AC voltage is rectified by the diode D11 and the capacitor C11 is charged with this rectified voltage.
  • On the capacitor C11 is thus a voltage relative to the reference potential GND available, if the mains voltage is an AC voltage.
  • the resistor R11 is used to discharge the capacitor C11 in the absence of the AC voltage.
  • the diode D10 is a Zener diode and thereby limits the voltage across the capacitor C11 for the protection of further evaluation stages.
  • the capacitor C10 In the event that the mains voltage is a DC voltage, in the steady state, the capacitor C10 is charged to the DC voltage. Thus, the voltage across resistor R12 is zero and also the voltage across capacitor C11 is zero.
  • the voltage across the capacitor C10 evaluates a switch S10, which is designed according to Figure 4 as a MOSFET.
  • Source of the switch S10 is connected to the reference potential.
  • Gate and source form the control input of the switch S10 and are connected to the capacitor C10.
  • Drain of the switch S10 is connected via a resistor R10 to the feedback input FB. If the mains voltage UN is now an AC voltage, the switch S10 is turned on by the voltage across the capacitor C11. Thus, the resistor R10 is connected in parallel to the resistor R1.
  • the circuit Ic01 controls the transistor T01 so that a higher bus voltage UBUS sets in the AC voltage case than in the DC voltage case.
  • the respective absolute values of the bus voltage UBUS can be determined by the selection of the resistors R1, R2 and R10.
  • the bus voltage UBUS is lower in the DC voltage case than in the AC voltage case, the power related to the mains voltage is lower in the DC voltage case. This advantageously reduces the load on a battery in the DC voltage case.
  • the load of the transistor T01 in the DC voltage case is also advantageously reduced.
  • the ratio of the bus voltages in the AC voltage case and DC voltage case can be set so that the load of the transistor T01 is the same in both cases.
  • no more load-bearing transistor T01 is required for the DC voltage case.
  • the characteristic curve which describes the relationship between the input power PIN of the circuit arrangement and the mains voltage UN is in the exemplary embodiment in each case a constant.
  • the input power PIN is lower in the DC voltage case than in the AC voltage case.
  • FIG. 5 shows a further exemplary embodiment of a circuit arrangement according to the invention.
  • the difference from the exemplary embodiment according to FIG. 4 is essentially that the switch S 10 in FIG. 4 in FIG. 5 has been replaced by a switch S20.
  • the switch S20 is now designed as a bipolar transistor.
  • the voltage-limiting Zener diode D10 of Figure 4 can be omitted.
  • the base of the switch S20 is connected via a current-limiting resistor R24 to the capacitor C11.
  • the base of the switch S20 is also connected via a resistor R23 to the reference potential GND. It can thus be adjusted at which voltage value on the capacitor C11 the switch S20 closes.
  • an emitter resistor R21 is still inserted to reduce the sensitivity of the switch S20 to noise.
  • FIG. 6a shows a diagram of the relationship between mains voltage UN and input power PIN without feedback in DC operation.
  • the input power PIN is constant above the mains voltage UN and for the AC voltage case and the DC voltage case approximately the same.
  • FIG. 6b shows a diagram of the relationship between mains voltage UN and power loss PV without feedback in DC operation.
  • the power loss PV describes the losses of the transistor T01 from FIGS. 4 or 5. It can be clearly seen that the losses in the DC voltage case are about 0.1 W higher than in the AC voltage case. Without feedback control in the DC voltage case, the transistor T01 must therefore be designed for the load in the DC voltage case. This is uneconomical, since the DC voltage case rarely occurs in emergency power operation.
  • FIG. 6c shows a diagram of the relationship between mains voltage UN and input power PIN with back regulation in DC operation.
  • the input power PIN is constant above the mains voltage UN.
  • the input power PIN is now lowered by approximately 30 W in relation to the AC voltage drop.
  • FIG. 6d shows a diagram of the relationship between mains voltage UN and power loss PV with back regulation in DC operation.
  • the power loss PV describes the losses of the transistor T01 from FIGS. 4 or 5.
  • the conditions are now reversed compared with FIG. 6b. It can clearly be seen that the losses in the DC voltage case are about 0.1 W lower than in the AC power supply. Tension case.
  • the transistor T01 can be designed economically for the normal case of the AC voltage.

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  • Control Of Electrical Variables (AREA)
  • Dc-Dc Converters (AREA)
EP06011520.1A 2005-06-10 2006-06-02 Circuit et procédé de commande de puissance d'un ballast électronique en fonction de la tension de réseau Active EP1732364B1 (fr)

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
DE102005027015A DE102005027015A1 (de) 2005-06-10 2005-06-10 Schaltungsanordnung und Verfahren zur netzspannungsabhängigen Leistungsregelung eines elektronischen Geräts, insbesondere eines elektronischen Vorschaltgeräts

Publications (3)

Publication Number Publication Date
EP1732364A2 true EP1732364A2 (fr) 2006-12-13
EP1732364A3 EP1732364A3 (fr) 2011-09-21
EP1732364B1 EP1732364B1 (fr) 2018-04-11

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EP06011520.1A Active EP1732364B1 (fr) 2005-06-10 2006-06-02 Circuit et procédé de commande de puissance d'un ballast électronique en fonction de la tension de réseau

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EP (1) EP1732364B1 (fr)
CN (1) CN1893757B (fr)
DE (1) DE102005027015A1 (fr)

Cited By (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP2070396A2 (fr) * 2006-10-02 2009-06-17 Osram-Sylvania Inc. Régulateur de puissance à tension efficace de sortie régulée limitée en courant
DE202012012473U1 (de) 2012-02-03 2013-03-01 Eckerle Industrie-Elektronik Gmbh Vorrichtung zur Ansteuerung einer Leuchtstofflampe
US8791653B2 (en) 2008-05-06 2014-07-29 Koninklijke Philips N.V. Apparatus for coupling power source to lamp
EP3651312A1 (fr) 2018-11-12 2020-05-13 polynom ag Unité de lumière de secours, installation d'éclairage de secours et élément de lumière de secours
CN111693817A (zh) * 2020-06-10 2020-09-22 深圳市创仁科技有限公司 一种调光设备的测试方法

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EP0450728A2 (fr) 1990-04-06 1991-10-09 Koninklijke Philips Electronics N.V. Ballast pour lampe fluorescente pouvant être alimenté indifféremment par 2 sources de puissance différentes
EP0563801A1 (fr) 1992-03-31 1993-10-06 KRAN- UND STAHLBAU GmbH Citerne
DE10013279A1 (de) 2000-03-17 2001-09-27 Trilux Lenze Gmbh & Co Kg Verfahren zur Überwachung der Eingangsspannung eines elektronischen Vorschaltgerätes zum Betrieb von Leuchtstofflampen
DE10056347A1 (de) 2000-11-14 2002-05-16 Bron Elektronik Ag Verfahren zur Überwachung der Leistung einer Film- oder Videoaufnahmeleuchte sowie Vorschaltgerät zur Durchführung eines solchen Verfahrens
EP1271745A1 (fr) 2001-06-18 2003-01-02 Almat AG Procédé pour l'exploitation de consommateurs d'électricité et dispositif utilisant un tel procédé
US20030102821A1 (en) 2001-10-29 2003-06-05 Van Der Veen Geert Willem Circuit arrangement

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US5872429A (en) * 1995-03-31 1999-02-16 Philips Electronics North America Corporation Coded communication system and method for controlling an electric lamp
DE19820615A1 (de) * 1998-05-08 1999-11-11 Walter Holzer Verfahren und Vorrichtung zur Regelung von Energiesparlampen
US5973455A (en) * 1998-05-15 1999-10-26 Energy Savings, Inc. Electronic ballast with filament cut-out
US5936357A (en) * 1998-07-24 1999-08-10 Energy Savings, Inc. Electronic ballast that manages switching frequencies for extrinsic purposes
US6507157B1 (en) * 2001-09-25 2003-01-14 Koninklijke Philips Electronics N.V. Electronic ballast system with dual power and dimming capability
EP1513377A1 (fr) * 2002-06-07 2005-03-09 Matsushita Electric Industrial Co., Ltd. Lampe fluorescente sans electrode du type ampoule electrique
AU2003242026A1 (en) * 2002-06-07 2003-12-22 Matsushita Electric Industrial Co., Ltd. Electrodeless discharge lamp lighting device, light bulb type electrodeless fluorescent lamp and discharge lamp lighting device
DE202004004462U1 (de) * 2004-03-22 2004-06-17 Tridonicatco Gmbh & Co. Kg Schaltungsanordnung zum Betreiben einer Lampe mit Batterie-Versorgung

Patent Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0450728A2 (fr) 1990-04-06 1991-10-09 Koninklijke Philips Electronics N.V. Ballast pour lampe fluorescente pouvant être alimenté indifféremment par 2 sources de puissance différentes
EP0563801A1 (fr) 1992-03-31 1993-10-06 KRAN- UND STAHLBAU GmbH Citerne
DE10013279A1 (de) 2000-03-17 2001-09-27 Trilux Lenze Gmbh & Co Kg Verfahren zur Überwachung der Eingangsspannung eines elektronischen Vorschaltgerätes zum Betrieb von Leuchtstofflampen
DE10056347A1 (de) 2000-11-14 2002-05-16 Bron Elektronik Ag Verfahren zur Überwachung der Leistung einer Film- oder Videoaufnahmeleuchte sowie Vorschaltgerät zur Durchführung eines solchen Verfahrens
EP1271745A1 (fr) 2001-06-18 2003-01-02 Almat AG Procédé pour l'exploitation de consommateurs d'électricité et dispositif utilisant un tel procédé
US20030102821A1 (en) 2001-10-29 2003-06-05 Van Der Veen Geert Willem Circuit arrangement

Cited By (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP2070396A2 (fr) * 2006-10-02 2009-06-17 Osram-Sylvania Inc. Régulateur de puissance à tension efficace de sortie régulée limitée en courant
EP2070396A4 (fr) * 2006-10-02 2012-08-29 Osram Sylvania Inc Régulateur de puissance à tension efficace de sortie régulée limitée en courant
US8791653B2 (en) 2008-05-06 2014-07-29 Koninklijke Philips N.V. Apparatus for coupling power source to lamp
DE202012012473U1 (de) 2012-02-03 2013-03-01 Eckerle Industrie-Elektronik Gmbh Vorrichtung zur Ansteuerung einer Leuchtstofflampe
EP3651312A1 (fr) 2018-11-12 2020-05-13 polynom ag Unité de lumière de secours, installation d'éclairage de secours et élément de lumière de secours
CN111693817A (zh) * 2020-06-10 2020-09-22 深圳市创仁科技有限公司 一种调光设备的测试方法
CN111693817B (zh) * 2020-06-10 2022-12-13 深圳市创仁科技有限公司 一种调光设备的测试方法

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Publication number Publication date
DE102005027015A1 (de) 2006-12-14
CN1893757B (zh) 2013-01-02
EP1732364B1 (fr) 2018-04-11
EP1732364A3 (fr) 2011-09-21
CN1893757A (zh) 2007-01-10

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