EP1655800B1 - Ligne hyperfréquence planaire avec changement de direction - Google Patents

Ligne hyperfréquence planaire avec changement de direction Download PDF

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Publication number
EP1655800B1
EP1655800B1 EP05023458A EP05023458A EP1655800B1 EP 1655800 B1 EP1655800 B1 EP 1655800B1 EP 05023458 A EP05023458 A EP 05023458A EP 05023458 A EP05023458 A EP 05023458A EP 1655800 B1 EP1655800 B1 EP 1655800B1
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EP
European Patent Office
Prior art keywords
microstrip
microwave guide
region
microstrip conductor
conductor
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Not-in-force
Application number
EP05023458A
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German (de)
English (en)
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EP1655800A1 (fr
Inventor
Detlef Zimmerling
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Atmel Germany GmbH
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Atmel Germany GmbH
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Publication of EP1655800A1 publication Critical patent/EP1655800A1/fr
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P5/00—Coupling devices of the waveguide type
    • H01P5/12—Coupling devices having more than two ports
    • H01P5/16—Conjugate devices, i.e. devices having at least one port decoupled from one other port
    • H01P5/18—Conjugate devices, i.e. devices having at least one port decoupled from one other port consisting of two coupled guides, e.g. directional couplers
    • H01P5/184—Conjugate devices, i.e. devices having at least one port decoupled from one other port consisting of two coupled guides, e.g. directional couplers the guides being strip lines or microstrips
    • H01P5/185—Edge coupled lines
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/02—Bends; Corners; Twists
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P3/00—Waveguides; Transmission lines of the waveguide type
    • H01P3/003—Coplanar lines

Definitions

  • the invention relates to a planar microwave line having a dielectric substrate and a planar arrangement of a first microstrip line and at least one further microstrip line, wherein a distance of the first microstrip line and the further microstrip line allows electromagnetic coupling, a first region in which the microwave line a first direction has, a second region in which the microwave line has a second direction, and a transition region in which a change from the first direction to the second direction occurs.
  • Such a microwave line is from the DE 29 43 502 , which forms the preamble of claim 1, known.
  • This document relates to so-called supported microstrip lines, under which there is understood a composite of two parallel metal surfaces, a parallel to and arranged between these dielectric support and arranged on a first surface of the support first strip-shaped microstrip.
  • a second microstrip conductor is to be arranged on the surface of the carrier, which runs mainly parallel to the first conductor and can be electromagnetically coupled thereto.
  • this document prescribes interrupting the first and second lines through a gap in the direction of a bisector of the deflection angle and cross-connecting the first and second conductors.
  • the crosswise connection takes place with the aid of a first connection running in the conductor plane and with the aid of a second connection which runs outside the conductor plane and is realized in the form of a conductor wire bridge.
  • discontinuities in the signal path such as open ends, vias through the dielectric, impedance jumps, line crossings, or direction changes, for example kinks in the line, create distortions in the electromagnetic fields that distort transmitted signals.
  • coplanar lines (without accompanying ground layer on the substrate side, the substrate side with the planar microstrip lines opposite), with straight laying very good high-frequency characteristics.
  • changes in direction as occur, for example, when laying in circular arcs, unwanted signal distortions and shifts of the electrical ground zero point are shown.
  • the known microwave line also has discontinuities and the outgoing from the plane in the third dimension extending conductor wire bridge discontinuities and thus undesirable wave resistance jumps.
  • the object of the invention is to specify a directional changes having planar microwave line with minimized distortion of transmitted signals.
  • the object of the invention is achieved.
  • the invention is based on the fact that both different transit times of signals on mutually coupled microstrip conductors, as well as discontinuities in the line path are avoided.
  • the identical lengths of the coupled microstrip conductors in the transition region according to the invention eliminate the cause of signal distortions resulting from different signal path lengths in the two-dimensional transition region from a first direction to a second direction.
  • discontinuities due to the course of the microstrip conductors, which also takes place in a transitional region in a plane and without crossing, discontinuities are avoided.
  • the invention thus provides a planar microwave line, the good high-frequency properties are largely retained even with a curved installation.
  • the microwave line it is preferable for the microwave line to have a second microstrip conductor and a third microstrip conductor as further microstrip conductors.
  • This configuration results in a coplanar line, which can be known to be used as a cost-effective replacement for a coaxial line. It is a particular advantage of the invention that it can also be used in such coplanar lines.
  • the distance of the first microstrip conductor from each further microstrip conductor in the first region and in the second region is constant in each case and in the transition region has a periodic modulation around an average which corresponds to the distance in the first region and / or in the second region.
  • the periodic modulation of the spacing results from a periodic convolution of at least one inner edge having a particular wavelength.
  • an inner edge can be lengthened as desired and thus be matched to the length of a further outer edge of an adjacent microstrip conductor having a larger radius of curvature.
  • the periodic modulation of the pitch results from convolution of opposite edges of adjacent microstrip lines having different wavelengths.
  • a number of convolution periods, that is a number of wavelengths, on an inner edge of the microwave line is equal to a number of convolution periods on each other inner edge of the microwave line.
  • minimum distance deviations from a mean distance also result for microwave lines with more than two microstrip lines coupled to one another.
  • the lengths of all edges of all microstrip lines in a transition region are the same.
  • at least the lengths of the inner edges are equal, wherein the lengths of the outer edges may be different.
  • the amplitude of the convolution increases with shorter wavelength.
  • the shortest wavelength of a convolution of an edge of the microwave line is longer than the wavelength of a highest transmitted over the microwave line useful signal frequency.
  • FIG. 1 shows a planar microwave line 10 which extends on a dielectric substrate 12 and has a first microstrip line 14 and two further microstrip lines 16 and 18.
  • FIG. 1 thus shows a coplanar line as microwave line 10.
  • the coplanar line is known to correspond to a planar coaxial line.
  • a first distance 20 between the first microstrip conductor 14 and a second microstrip conductor 16 as a further microstrip conductor is dimensioned so that an electromagnetic coupling between the first microstrip conductor 14 and the second microstrip conductor 16 occurs during the transmission of microwaves.
  • a second distance 22 between the first microstrip conductor 14 and a third microstrip conductor 18 as a further microstrip conductor is dimensioned such that an electromagnetic coupling between the first microstrip conductor 14 and the third microstrip conductor 18 occurs during the transmission of microwaves.
  • the first microstrip conductor 14 corresponds to the inner conductor of a coaxial line, and the further microstrip conductors 16 and 18 are to be compared with the outer conductor (shield) of a coaxial line.
  • the width of the first microstrip line 14, the distances 20 and 22, and the dielectric constant of the dielectric substrate 12 essentially determine the characteristic impedance Z of the microwave line 10.
  • Such coplanar microwave line 10 has very good high-frequency characteristics as long as it can be laid. In FIG. 1, the microwave line 10 is laid straight in a first area 24 in a first direction and in a second area 26 in a second direction.
  • the microwave line 10 of Figure 1 has the peculiarity that of the edges 30, 32, 34, 36, 38 and 40 at least adjacent edges 34 and 32 and 36 and 38 of the first microstrip line 14 and the second microstrip line 16 and the first microstrip line 14 and the third microstrip conductor 18 in the transition region 28 have an equal length and extend without crossing.
  • This embodiment of the length of the edges 34, 32 and 36, 38 is based on the recognition that the highest field strengths at the inner edges 32, 34, 36 and 38 of the microstrip conductors 14, 16 and 18 occur during the transport of high-frequency signals via the microwave line 10.
  • the lengths of the edges 34, 32, 36 and 38 are equal to each other, there are no differences in transit time of running along the edges 34, 32, 36 and 38 signals.
  • the same length of the edges 34, 32, 36 and 38 is achieved in the embodiment of Figure 1, characterized in that the distance between the first microstrip line 14 and the second microstrip line 16 and / or between the first microstrip line 14 and the third microstrip line 18 is a periodic Modulation around a mean around.
  • the mean value corresponds to the distance 20 and / or the distance 22 of the microstrip conductors 14 and 16, or 14 and 18 in the first region 24 and / or in the second region 26.
  • the modulation results in an inner edge, e.g.
  • the edge 34 periodically closer to an outer edge, e.g. led the edge 32 and led away from the outer edge.
  • the inner edge 32 is extended by the periodic approach and removal, which ideally compensates for their shortening by the smaller radius of curvature.
  • the length of the edge 36 is adjusted to the length of the edge 34, so that the edges 34, 32, 36 and 38 in the article of Figure 1 the same are.
  • mean values of distance maxima and distance minima in the transition region 28 should correspond to the associated constant distance in the first region 24 and / or second region 26.
  • FIG. 1 shows distance maxima 42 and distance minima 44, which lie in the transition region 28 and whose average values correspond to the distance 20 from the first region 24.
  • the lengths of all the edges 30, 32, 34, 36, 38 and 40 with each other are equal or the lengths of the edges 32, Vietnamese 40 are aligned with the length of the longest edge 30 due to their radius of curvature.
  • the alignment can be generated by a sinusoidal folding of the inner edges 32, ...., 40, in which each inner edge 32, ...., 40 carries the same number of waves. As a result, the further down an edge lies, the shorter the wavelength becomes.
  • each edge corresponds to the length of another edge results from the fact that the amplitude of the convolution increases with shorter wavelength.
  • the amplitude of the innermost edge 40 is greater than the amplitude of the edge 38, which in turn is greater than the amplitude of the inner edge 36 and so on.
  • FIG. 2 thus shows in particular a section through a coplanar line without accompanying ground on a side 46 of the substrate 12 facing away from the microwave line 10 ,
  • FIG. 3 shows an alternative planar microwave line 10.1, which has only a first microstrip line 14.1 and a further microstrip line 16.1.
  • a first distance 20.1 between the first microstrip conductor 14.1 and the second microstrip conductor 16.1 is dimensioned as a further microstrip conductor such that an electromagnetic coupling between the first microstrip conductor 14.1 and the second microstrip conductor 16.1 occurs during the transmission of microwaves.
  • the microwave line 10. 1 is laid straight in a first area 24. 1 in a first direction and in a second area 26. 1 in a second direction.
  • the direction change from the first direction to the second direction and vice versa takes place in a transition region 28.1, in which the microstrip conductors 14.1 and 16.1 of the microwave line 10.1 are laid in a curved manner.
  • edges 34.1 and 32.1 of the first microstrip conductor 14.1 and the second microstrip conductor 16.1 in the transition region 28.1 an equal length in conjunction with a crossing-free course.
  • the same length of the edges 34.1 and 32.1 is also achieved in the embodiment according to FIG. 3 in that the distance between the first microstrip conductor 14.1 and the second microstrip conductor 16.1 has a periodic modulation about an average value.
  • the mean value corresponds to the distance 20.1 of the microstrip conductors 14 and 16.1 in the first region 24.1 and / or in the second region 26.1. Due to the modulation, the edge 34.1 is periodically brought closer to the edge 32.1 and led away from it.
  • the edge 34.1 is relatively more extended by the periodic approach and removal, which ideally compensates for their relative shortening relative to the edge 32.1, which is due to the smaller radius of curvature.
  • mean values of distance maxima 42.1 and distance minima 44.1 in the transition region 28.1 should correspond to the associated constant distance 20.1 in the first region 24.1 and / or second region 26.1.
  • the periodic modulation thus essentially corresponds to the comparable periodic modulation in FIG. 1, but appears more clearly in the subject matter of FIG. 3.
  • the approximation of the lengths of the inner edges 34.1, 32.1 can again be generated by a sinusoidal convolution of the inner edges 34.1 32.1, in which each inner edge 34.1, 32.1 carries the same number of waves. In the embodiment of FIG. 3, these are each three half-waves. As a result, the further down an edge lies, the shorter the wavelength becomes.
  • the fact that the length of the edge 32.1 corresponds to the length of the edge 34.1 results from the fact that the amplitude of the convolution increases with shorter wavelength. In other words, the amplitude of the inner edge 34.1 is greater than the amplitude of the edge 32.1. In the embodiment of FIG. 3, the amplitudes differ approximately by a factor of 3.
  • outer edges 30.1 and 36.1 have their somewhat natural arc length in the embodiment of FIG. 3, ie they have different lengths. This is unproblematic in most cases, because the high-frequency signals propagate along the inner edges 32.1 and 34.1 which couple with one another. It is understood that these modifications also in the coplanar embodiment of FIG. 1 is usable.
  • the same length of the inner edges 34.1, 32.1 or the edges in Fig. 1 can be achieved not only by a sinusoidal convolution but also by other types of folding.
  • An example of another type of convolution results, for example, from the use of sections of straight lines, parabolic arcs or, more generally, arcs or sections of polynomials.

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  • Waveguides (AREA)

Claims (9)

  1. Ligne hyperfréquence planaire (10) comprenant un substrat diélectrique (12) et une disposition coplanaire d'une première microbande (14) et d'au moins une microbande supplémentaire (16, 18), dans laquelle un intervalle (20, 22) entre la première microbande (14) et la microbande supplémentaire (16, 18) permet un couplage électromagnétique, une première zone (24) dans laquelle la ligne hyperfréquence (10) présente une première direction, une deuxième zone (26), dans laquelle la ligne hyperfréquence (10) présente une deuxième direction, et une zone de transition (28) dans laquelle s'effectue un changement de la première direction vers la deuxième, caractérisée en ce que la première microbande (14) et la microbande supplémentaire (16, 18) s'étendent dans la zone de transition sans se croiser, et que des chants voisins (32,34 ; 36,38) de la première microbande (14) et de la microbande supplémentaire (16, 18) sont de même longueur dans la zone de transition (28).
  2. Ligne hyperfréquence (10) selon la revendication 1 comprenant une deuxième microbande (16) et une troisième microbande (18) comme microbandes supplémentaires (16, 18).
  3. Ligne hyperfréquence (10) selon la revendication 1 ou 2, caractérisée en ce qu'un intervalle (20, 22) entre la première microbande (14) et chaque microbande supplémentaire (16, 18) dans la première zone (24) et dans la deuxième zone (26) est à chaque fois constant et que dans la zone de transition (28), il présente une modulation périodique autour d'une valeur moyenne qui correspond à l'intervalle (20, 22) dans la première zone (24) et/ou dans la deuxième zone (26).
  4. Ligne hyperfréquence (10) selon la revendication 3, caractérisée en ce que la modulation périodique de l'intervalle résulte d'un pliage périodique d'un chant interne (32,34 ; 36,38) ayant une longueur d'onde définie.
  5. Ligne hyperfréquence (10) selon la revendication 4, caractérisée en ce que la modulation périodique de l'intervalle résulte d'un pliage de chants en regard (32,34 ; 36,38) de microbandes voisines (14, 16, 18) de longueurs d'ondes différentes.
  6. Ligne hyperfréquence (10) selon la revendication 4 ou 5, caractérisée en ce qu'un nombre de périodes de répétition de pliage sur un chant interne (32, 34, 36, 38) des microbandes (14, 16, 18) est égal à un nombre de périodes de répétition de pliage sur chaque autre chant interne (32,34 ; 36,38) des microbandes (14, 16, 18).
  7. Ligne hyperfréquence (10) selon au moins une des revendications 3 à 6, caractérisée en ce que les longueurs de tous les chants (32, 34, 36, 38, 40) de toutes les microbandes (14, 16, 18) sont identiques dans la zone de transition (28).
  8. Ligne hyperfréquence (10) selon au moins une des revendications 4 à 7, caractérisée en ce que l'amplitude du pliage augmente au fur et à mesure que la longueur d'onde du pliage diminue.
  9. Ligne hyperfréquence (10) selon au moins une des revendications 3 à 8, caractérisée en ce que la longueur d'onde la plus courte d'un pliage (32, 34, 36, 38, 40) de la ligne hyperfréquence (10) est plus longue que la longueur d'onde d'une fréquence de signal utile la plus élevée transmise par la ligne hyperfréquence (10).
EP05023458A 2004-10-29 2005-10-27 Ligne hyperfréquence planaire avec changement de direction Not-in-force EP1655800B1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE102004053517 2004-10-29
DE102005038456A DE102005038456A1 (de) 2004-10-29 2005-08-03 Planare Mikrowellenleitung mit Richtungsänderung

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EP1655800A1 EP1655800A1 (fr) 2006-05-10
EP1655800B1 true EP1655800B1 (fr) 2007-12-05

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Publication number Priority date Publication date Assignee Title
US20070222533A1 (en) * 2006-03-24 2007-09-27 Chun-Yu Lai Capacitance-compensated differential circuit line layout structure
EP2317600A1 (fr) * 2009-11-02 2011-05-04 Nxp B.V. Circuit électronique doté de plusieurs lignes de transmission
JP6237265B2 (ja) * 2014-01-24 2017-11-29 富士通株式会社 プリント基板および配線配置方法
WO2018128082A1 (fr) * 2017-01-05 2018-07-12 住友電工プリントサーキット株式会社 Carte de circuit imprimé flexible
JP7061459B2 (ja) * 2017-12-25 2022-04-28 日本航空電子工業株式会社 回路基板、コネクタ組立体及びケーブルハーネス
AU2019290034B2 (en) * 2018-06-21 2024-03-28 Bae Systems Australia Limited An electromagnetic coupler
CN115395195B (zh) * 2022-09-16 2023-09-15 安徽大学 一种非规则宽带槽线结构

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Publication number Priority date Publication date Assignee Title
NL7810942A (nl) 1978-11-03 1980-05-07 Philips Nv Ondersteunde microstriplijn voor de propagatie van een oneven golfmodus.
DE3638112C1 (en) * 1986-11-07 1987-12-17 Georg Dr-Ing Spinner Coaxial elbow
JP3252605B2 (ja) * 1994-07-04 2002-02-04 株式会社村田製作所 電子部品及びその製造方法
JP3125691B2 (ja) * 1995-11-16 2001-01-22 株式会社村田製作所 結合線路素子
US6347041B1 (en) * 2000-01-21 2002-02-12 Dell Usa, L.P. Incremental phase correcting mechanisms for differential signals to decrease electromagnetic emissions
JP2003289206A (ja) * 2002-03-28 2003-10-10 Asahi Glass Co Ltd 共平面伝送線路及び高周波アンテナ

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Publication number Publication date
DE102005038456A1 (de) 2006-05-04
US20060091973A1 (en) 2006-05-04
US7378919B2 (en) 2008-05-27
DE502005002148D1 (de) 2008-01-17
EP1655800A1 (fr) 2006-05-10

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