EP1519444A1 - Rekonfigurierbare Gruppenantenne mit niedrigem Verlust - Google Patents

Rekonfigurierbare Gruppenantenne mit niedrigem Verlust Download PDF

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Publication number
EP1519444A1
EP1519444A1 EP04292265A EP04292265A EP1519444A1 EP 1519444 A1 EP1519444 A1 EP 1519444A1 EP 04292265 A EP04292265 A EP 04292265A EP 04292265 A EP04292265 A EP 04292265A EP 1519444 A1 EP1519444 A1 EP 1519444A1
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EP
European Patent Office
Prior art keywords
phase
radiating elements
antenna according
signals
antenna
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP04292265A
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English (en)
French (fr)
Inventor
Hervé Legay
Béatrice Salome
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Alcatel Lucent SAS
Original Assignee
Alcatel CIT SA
Alcatel SA
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Filing date
Publication date
Application filed by Alcatel CIT SA, Alcatel SA filed Critical Alcatel CIT SA
Publication of EP1519444A1 publication Critical patent/EP1519444A1/de
Withdrawn legal-status Critical Current

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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/44—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the electric or magnetic characteristics of reflecting, refracting, or diffracting devices associated with the radiating element
    • H01Q3/46—Active lenses or reflecting arrays

Definitions

  • the invention relates to the field of network antennas, and more particularly the reflector array antennas.
  • Network antennas are generally divided into two large families, that of phase-controlled network antennas (or PAAs for "Phase Array Antenna”) and that of reflective network antennas (or RAAs for "ReflectArray Antenna”).
  • PAAs phase-controlled network antennas
  • RAAs ReflectArray Antenna
  • the network antennas To allow the passage of a coverage area (or “spot”) to another, the network antennas must be reconfigurable.
  • the reconfigurability can be achieved using a subdivision of the network into subnets each associated with an active phase control device.
  • the reconfigurability of the antenna then depends only on a constraint, namely the dimensions of each subnet, which depend on those of the coverage area to which the antenna should point.
  • the radiating elements intercept with minimal losses the waves comprising the signals to be transmitted, which are delivered by a source.
  • Gold the angle of incidence under which the radiating elements receive the waves varies according to their positions relative to the source. It can thus vary for some networks between 0 ° and 50 °. Such angular variation makes particularly difficult both the reception with a high gain, waves from the source, and the transmission (or emission) with a high gain, received waves, over the entire coverage area pointed.
  • Reflective network antennas therefore commonly use radiative elements with little direction, with a typical dimension between 0.6 ⁇ and 0.7 ⁇ , where ⁇ represents the operating wavelength.
  • the Reconfigurability of the antenna pattern with such an antenna requires therefore to equip each radiating element with a control device of phase. But, such a solution can lead to prohibitive costs.
  • the purpose of the invention is therefore to improve the situation in the case of reflector network antennas.
  • control means phase and the antenna distribution means are configurable from so that his pointing direction can vary.
  • a reflector array antenna A first comprises a source S, delivering at a chosen solid angle of main direction DPS, called pointing direction of the source, waves comprising signals to pass.
  • Antenna A also includes multiple SR subnets responsible for receiving, with a high gain, the waves delivered by the S source, and transmit them at a selected solid angle, direction DPA, referred to as the pointing direction of the antenna, to cover a selected area with a high gain.
  • Each radiating element ERi delivers the signals it has collected on an output O to which it is couple.
  • Each subnet SR also includes means of combination fed with signals collected by the different outputs O and summons them according to a first chosen phase law so that they correspond to the chosen direction of pointing of the DPS source.
  • Each subnet SR also comprises control means MCP phase powered signal summed by the means of combination MC and responsible for applying a chosen phase shift.
  • each subnet SR has distribution means MDs powered by the MCP phase control means in summed signals and out of phase and responsible for distributing them between the radiating elements ERi, via I inputs, depending on a second phase law chosen so that they radiate them in the pointing direction of the DPA antenna with the second polarization P2.
  • the SR sub-networks are preferably of the non-reciprocal type.
  • the combining means MC and the distribution means MD are distinct. They thus constitute two circuits separate power supply.
  • the network pitch is small enough (typically 0.6 ⁇ to 0.7 ⁇ ).
  • the dimensions of the SR subnet are then chosen according to the maximum sweep angle required for transmission in the direction of DPA antenna pointing, like a control network antenna active phase.
  • a nonreciprocal SR subnetwork may occur either in a planar form, or in a linear form.
  • planar subnetwork is understood to mean a sub-network SR of type of the one illustrated in FIG. 2.
  • each radiating element ERi delivers on its output O signals having a first polarization P1 vertical, and is arranged to emit signals summed with a second polarization P2 horizontal.
  • Each output O constitutes the end of an R1 branch of a first transmission line LT1 connected to the input of the means of MCP phase control and which constitutes the means of combination MC.
  • the configurations of the LT1 transmission line and its R1 branches are chosen to compensate for the differences between the paths followed by the waves between the source S and the different radiating elements ERi in accordance with the first phase law associated with the pointing direction the DPS source for the relevant SR subnet. This compensation is what was previously called the combination of signals.
  • the radiating elements ERi feed the means of MC combination in parallel.
  • the line of LT1 transmission consists of portions of lines that connect the radiating elements ERi to each other.
  • each entry I constitutes the end of a branch R2 of a second transmission line LT2 connected to the output of the means of MCP phase control and which constitutes the means of distribution MD.
  • the phase shift applied by the MCP phase control means and the configurations of the LT2 transmission line and its R2 ramifications are chosen in accordance with the second phase law associated with the direction of pointing of the DPA antenna.
  • the MD distribution means feed the radiating elements ERi in parallel.
  • the power supply is in series.
  • the LT2 transmission line consists of portions of lines that connect the radiating elements ERi to each other.
  • the first law phase applied by the combining means MC may vary from one subnetwork to each other because of their respective positions with respect to the source S.
  • the transmission lines LT1 and LT2 and their branches R1 and R2 are preferably carried out in microstrip technology (or "Microstrip"). But, in variants, the transmission lines LT1 and LT2 and their R1 and R2 branches can be realized in technology triplate or coplanar.
  • the means of MC combination (LT1 and R1) and the MD distribution means (LT2 and R2) are preferentially carried out on different levels of the structure of the SR subnet.
  • the transmission lines are coupled directly (by contact) to the radiating elements ERi.
  • the coupling is done via of slits.
  • the combination means MC and the means of MD distribution can be installed on two different levels of the face back.
  • Linear subnetwork is understood here to mean an SR sub-network of the type of that illustrated in Figure 4, or one of its variants illustrated on the Figures 5 to 10 and 15.
  • the radiating elements ERi are arranged one after another in a chosen direction OX.
  • This arrangement is particularly well adapted, although non-exclusive use, with synthetic aperture radar or SAR antennas (for "Synthetic Aperture Radar").
  • the combination means MC and MD distribution means do not intersect, unlike subnets in which the combination means MC and the MD distribution means intersect because they are different.
  • Radiant elements ERi of the sub-network SR feed in parallel with polarization signals P1 the combination means MC which combines them according to the first law of phase to supply the input of the MCP phase control means.
  • the MCP phase control means supply summed signals and the MD distribution means which are, for example, placed at the same level as the combination means MC and the means of MD distribution.
  • the MD distribution means distribute in parallel to the radiating elements ERi the summed and out of phase signals, in accordance with the second phase law.
  • phase control MCP Due to lack of space, the means of phase control MCP are installed at a different level from the one where the means are installed MC combination and the MD distribution means. This is the reason for which they are materialized in dotted lines.
  • each output O of an element radiating ERi constitutes the end of an R1 branch of a first line transmission LT1 connected to the input of the phase control means MCP through a first TR1 transition and which constitutes the combination means MC.
  • the configurations of the transmission line LT1 and its R1 branches are chosen to compensate for gaps between the paths followed by the waves between the source S and the different radiating elements ERi according to the first phase law associated with the pointing direction of the DPS source.
  • Each input I constitutes the end of an R2 branch of a second transmission line LT2 connected to the output of the means of MCP phase control via a second transition TR2 and which constitutes the MD distribution means. More precisely, the second transition TR2 is here connected to the output of the phase control means MCP via an LT3 auxiliary transmission line.
  • the configurations of the LT3 auxiliary transmission line and the LT2 transmission line and its R2 branches are chosen in accordance with the second phase law associated with the pointing direction of the DPA antenna.
  • the transmission lines LT1 and LT2 and their branches R1 and R2 are also preferentially carried out in microstrip technology (or microstrip) on the same layer as the one with the lower tiles radiative radiators ERi. But, in variants, the lines of LT1 and LT2 transmission and their R1 and R2 branches can be realized in triplate or coplanar technology.
  • the tiles of the radiating elements ERi are here of circular shape, but they could be square shaped.
  • phase control means MCP At the level of the combination means MC and means of MD distribution, one can for example use the configuration illustrated on the figure 5.
  • This variant takes all the constituents of the subnetwork of Figure 4, but differs from it in that, on the one hand, the outputs O radiating elements ER1 and ER2 are placed opposite one another, just like those of radiating elements ER3 and ER4, and secondly, that the MCP phase control means are placed at the same level as the combination means MC and MD distribution means.
  • the signals delivered by the elements radiators ER1 and ER2 (respectively ER3 and ER4) on their outputs O respective ones here have antiparallel polarizations.
  • a phase-shifter D responsible for applying a phase shift of 180 ° to the signals it receives before they are combined to the signals from the radiating element ER2 (respectively ER4).
  • FIGS. 6A and 6B makes it possible to better visualize the separation of the MCP phase control means, a share, and MC combination means and MD distribution means, on the other hand, mentioned above with reference to FIG.
  • the MD distribution means supply the radiating elements ERi in parallel with signals summed and out of phase to be transmitted with a second linear polarization vertical P2.
  • the inputs I of the radiating elements ER1 and ER2 are placed "down" of the lower pavers PI (relative to the vertical direction of the page), while the entries I of the elements radiators ER3 and ER4 are placed "at the top” of the lower PI pavers (by report to the vertical direction of the page). Therefore, the polarization of signals emitted by radiating elements ER3 and ER4 is antiparallel to that of the signals emitted by the radiating elements ER1 and ER2. This imposes so that the signals coming from ER1 and ER2 are shifted by 180 °, ER3 and ER4, as shown in FIG.
  • each radiating element ERi is here consisting, in particular, of a PI radiative block (or “patch”), which located at the level of the layer comprising the combination means MC and the MD distribution means, and an upper radiative pad PS (materialized in dotted lines), which is placed above a layer dielectric, itself placed above the layer with the cobblestones lower PI, the combination means MC and the distribution means MD.
  • a PI radiative block or "patch”
  • PS materialized in dotted lines
  • the MCP phase control means are implemented in a layer of the structure placed preferably at the rear of the ground plane (no shown), and the layer comprising the combining means MC and the MD distribution means (see Figure 6B). Moreover, the structure multilayer is surrounded by PM metal walls.
  • each output O of an element radiating ERi constitutes the end of an R1 branch of a first line transmission LT1 connected to the input of the phase control means MCP through a first TR1 transition and which constitutes the combination means MC.
  • the configurations of the transmission line LT1 and its R1 branches are chosen to compensate for gaps between the paths followed by the waves between the source S and the different radiating elements ERi according to the first phase law associated with the pointing direction of the DPS source.
  • all the radiating elements ERi feed the means of MC combination in parallel mode with signals having a first polarization P1 horizontal.
  • Each input I constitutes the end of an R2 branch of a second transmission line LT2 connected to the output of the means of MCP phase control via a second transition TR2 and which constitutes the MD distribution means. More precisely, the second transition TR2 is here connected to the output of the phase control means MCP via an LT3 auxiliary transmission line.
  • the configurations of the LT3 auxiliary transmission line and the LT2 transmission line and its R2 branches are chosen in accordance with the second phase law associated with the pointing direction of the DPA antenna.
  • the transmission lines LT1 and LT2 and their branches R1 and R2 are also preferentially carried out in microstrip technology (or microstrip) on the same layer as that comprising the lower pavers PI. But, in variants, the transmission lines LT1 and LT2 and their R1 and R2 branches can be made in triplate technology or coplanar.
  • the combination means MC and the distribution means MD can be placed behind the plane of mass.
  • each radiating element ERi is fed by two vertical transitions connected to its excitation points.
  • This mode of realization requires free space in the center to install MCP phase control means, which imposes a configuration excitation similar to that of Figure 5 and therefore the use of phase shifters 180 ° MM.
  • the output (O) of the first radiating element ER1 feeds a first portion P1 of the line transmission cable LT1 connected to the second radiating element ER2, whose output feeds a second portion P2 of the LT1 transmission line connected to the third radiating element ER3, the output of which feeds a third portion of the transmission line LT1, and the output of the fourth radiating element ER4 feeds here a fourth portion P4 of the line of transmission LT1, arranged differently from the other portions P1 to P3 in order to to compensate the antiparallel excitation of the fourth radiating element ER4.
  • the transmission line LT1 supplies the MCP phase control means, that feed the LT2 transmission line whose ramifications are connected to the inputs (I) of the radiating elements ERi.
  • This embodiment is particularly interesting when has "reversible" MCP phase control means because it allows the antenna A to operate in two polarization modes.
  • the radiating elements ERi can supply the transmission line LT2 in parallel with summed signals and out of phase to be emitted with a second vertical bias P2.
  • the transmission line LT1 serially feeds the elements radiators ERi with polarization signals P1 horizontal.
  • the first subnetwork variant SR differs from the subnetwork in Figure 7 by using modules of MCT switching on the branches of the LT1 transmission line and on the LT2 transmission line. More specifically, in the illustrated configuration, the MCT switching modules (which are everywhere doubled to allow functioning in both directions) are placed in a first position that allows the application of the phase law associated with the direction of pointing of the DPA antenna. The signals are then collected in parallel having a first vertical polarization P1 and series of summed and out of phase signals to be transmitted with a second horizontal polarization P2. On the other hand, when all modules of switching MCT are in a second position, we can apply the law of phase associated with the pointing direction of the DPS source. This allows to adapt the polarization to that of the source S. The signals having a first horizontal polarization are then collected in series, while one distributes parallel summed and out of phase signals to be transmitted with a second vertical polarization.
  • the second subnetwork variant SR illustrated in FIG. differs from the subnetwork of Figure 7 by feeding the cobblestones radiating elements ERi either on their sides, but in their corners, of to simultaneously excite the two polarizations, and by the use of MCT switching modules in the radiating elements ERi in order to select one of the two polarizations excited, both in collection and program.
  • double polarization is not obligatorily of linear type. It can indeed be of circular type.
  • the radiating elements ERi can be, for example, microstrip resonators truncated according to their diagonal or slightly rectangular microstrip resonators.
  • the MCT switches allowing the operation in double polarization were not represented. But, in reality, they are placed at the inlet and the outlet of the radiating elements ERi, as is the case in the embodiment of Figure 8.
  • Such a band B is schematically illustrated in FIG. the case of linear SR subnetworks.
  • the subnetworks SR of a B-band are placed against each other parallel to their extension direction (here OX).
  • Antenna A is then reconfigurable according to the direction OY (or elevation), that is to say in the plane perpendicular to the direction OX.
  • antenna A can have multiple parallel B bands of planar subnets so that it be reconfigurable at the same time according to the direction OY (or elevation), that is to say in the plane perpendicular to the direction OX, and following the direction OX, that is to say in the plane perpendicular to the direction OY.
  • the radiating elements ERi are preferentially made in the form of a multilayer structure conventional comprising, in particular, a lower radiating conductive pad PI, coupled, on the one hand, to the input I and / or the output O, and on the other hand, to a pad upper radiative conductor PS responsible for collecting the waves from the source S and emit the waves collected after transformation.
  • the coupling between the upper radiator blocks PS and lower PI of an element radiating ERi can be performed either directly by conduction, via a conductive layer or bushings, either electromagnetically via a layer of dielectric material.
  • symmetrical slots FS is preferable because it provides better isolation between the two polarizations and does not generate high levels of cross polarization.
  • the S substrate which supports power circuits and cobblestones radiative PI
  • the S substrate which supports power circuits and cobblestones radiative PI
  • the S substrate can be realized in PTFE type material having a dielectric constant of about 3.2, a loss tangent from about 0.003 to 10 GHz, a thickness of about 0.79 mm and a thickness about 17 ⁇ m copper.
  • Separators placed between the pavers radiative and FA or FS slots can for example be realized in a Rohacell type material 31 having a dielectric constant of about 1.05, a loss tangent of about 0.0002 to 2.5 GHz and a thickness about 2 mm.
  • the network pitch that is, the distance between the radiating elements ERi
  • the network pitch is chosen substantially equal to 20 mm, which corresponds to 0.65 ⁇ when the frequency is equal to 9.8 GHz.
  • the MCP phase control means of each SRi subnetwork are preferably made in the form of phase shifters, and more preferentially still in the form of configuration delay lines different (so as to apply different phase shifts), coupled to at least one micron electromechanical system of the MEMS type, ensuring the switch function.
  • These systems are particularly advantageous because they have very low insertion losses, typically 0.1 dB for frequencies up to about 40 GHz.
  • the state of the MEMS is controlled by electrical voltages.
  • Each subnet SR may also include, as illustrated in FIG. 15, low noise amplification means (or LNA for “Low”).
  • Amplifier and / or power amplifier means (or HPA for "High Power Amplifier”) to provide near-optical amplification summed waves, before or after phase shift by means of MCP phase control.
  • the subnet SR comprises a circulator CR connected, on the one hand, to the transmission line LT2, and other on the other hand, the amplification means LNA and HPA, which are also connected to an MCT switch, itself connected to the means of MCP phase control.
  • the signals reach either the LNA to be amplified before “back up” towards the MCP phase control means then towards the elements radiating ERi (which allows operation of the antenna in reception), to the HPA to be amplified before “down” to the elements ERi (which allows the antenna to transmission).
  • LNA and HPA may for example be performed in the form of amplifying chips, such as MMICs.
  • the number of radiating elements belonging to each sub-network can be any, since it is at least two.
  • the number of subnets of an antenna can be whatever, since it is at least two.
  • subnetwork embodiments have been described in which the radiating elements consisted of a structure multilayer comprising radiative pavers. But, the invention is not limited to this single type of radiating element. It also concerns subnetworks equipped with radiating elements such as microstrip resonators, slots, or dielectric resonators.

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  • Variable-Direction Aerials And Aerial Arrays (AREA)
  • Aerials With Secondary Devices (AREA)
  • Waveguide Aerials (AREA)
EP04292265A 2003-09-23 2004-09-21 Rekonfigurierbare Gruppenantenne mit niedrigem Verlust Withdrawn EP1519444A1 (de)

Applications Claiming Priority (2)

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FR0311109 2003-09-23
FR0311109A FR2860107B1 (fr) 2003-09-23 2003-09-23 Antenne reseau reflecteur reconfigurable a faibles pertes

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CA (1) CA2480588C (de)
FR (1) FR2860107B1 (de)

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US20050122273A1 (en) 2005-06-09
US7142164B2 (en) 2006-11-28
FR2860107A1 (fr) 2005-03-25
FR2860107B1 (fr) 2006-01-13
CA2480588A1 (fr) 2005-03-23
CA2480588C (fr) 2012-03-06

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