EP1519444A1 - Antenne réseau réflecteur reconfigurable à faibles pertes - Google Patents
Antenne réseau réflecteur reconfigurable à faibles pertes Download PDFInfo
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- EP1519444A1 EP1519444A1 EP04292265A EP04292265A EP1519444A1 EP 1519444 A1 EP1519444 A1 EP 1519444A1 EP 04292265 A EP04292265 A EP 04292265A EP 04292265 A EP04292265 A EP 04292265A EP 1519444 A1 EP1519444 A1 EP 1519444A1
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- phase
- radiating elements
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
- H01Q3/44—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the electric or magnetic characteristics of reflecting, refracting, or diffracting devices associated with the radiating element
- H01Q3/46—Active lenses or reflecting arrays
Definitions
- the invention relates to the field of network antennas, and more particularly the reflector array antennas.
- Network antennas are generally divided into two large families, that of phase-controlled network antennas (or PAAs for "Phase Array Antenna”) and that of reflective network antennas (or RAAs for "ReflectArray Antenna”).
- PAAs phase-controlled network antennas
- RAAs ReflectArray Antenna
- the network antennas To allow the passage of a coverage area (or “spot”) to another, the network antennas must be reconfigurable.
- the reconfigurability can be achieved using a subdivision of the network into subnets each associated with an active phase control device.
- the reconfigurability of the antenna then depends only on a constraint, namely the dimensions of each subnet, which depend on those of the coverage area to which the antenna should point.
- the radiating elements intercept with minimal losses the waves comprising the signals to be transmitted, which are delivered by a source.
- Gold the angle of incidence under which the radiating elements receive the waves varies according to their positions relative to the source. It can thus vary for some networks between 0 ° and 50 °. Such angular variation makes particularly difficult both the reception with a high gain, waves from the source, and the transmission (or emission) with a high gain, received waves, over the entire coverage area pointed.
- Reflective network antennas therefore commonly use radiative elements with little direction, with a typical dimension between 0.6 ⁇ and 0.7 ⁇ , where ⁇ represents the operating wavelength.
- the Reconfigurability of the antenna pattern with such an antenna requires therefore to equip each radiating element with a control device of phase. But, such a solution can lead to prohibitive costs.
- the purpose of the invention is therefore to improve the situation in the case of reflector network antennas.
- control means phase and the antenna distribution means are configurable from so that his pointing direction can vary.
- a reflector array antenna A first comprises a source S, delivering at a chosen solid angle of main direction DPS, called pointing direction of the source, waves comprising signals to pass.
- Antenna A also includes multiple SR subnets responsible for receiving, with a high gain, the waves delivered by the S source, and transmit them at a selected solid angle, direction DPA, referred to as the pointing direction of the antenna, to cover a selected area with a high gain.
- Each radiating element ERi delivers the signals it has collected on an output O to which it is couple.
- Each subnet SR also includes means of combination fed with signals collected by the different outputs O and summons them according to a first chosen phase law so that they correspond to the chosen direction of pointing of the DPS source.
- Each subnet SR also comprises control means MCP phase powered signal summed by the means of combination MC and responsible for applying a chosen phase shift.
- each subnet SR has distribution means MDs powered by the MCP phase control means in summed signals and out of phase and responsible for distributing them between the radiating elements ERi, via I inputs, depending on a second phase law chosen so that they radiate them in the pointing direction of the DPA antenna with the second polarization P2.
- the SR sub-networks are preferably of the non-reciprocal type.
- the combining means MC and the distribution means MD are distinct. They thus constitute two circuits separate power supply.
- the network pitch is small enough (typically 0.6 ⁇ to 0.7 ⁇ ).
- the dimensions of the SR subnet are then chosen according to the maximum sweep angle required for transmission in the direction of DPA antenna pointing, like a control network antenna active phase.
- a nonreciprocal SR subnetwork may occur either in a planar form, or in a linear form.
- planar subnetwork is understood to mean a sub-network SR of type of the one illustrated in FIG. 2.
- each radiating element ERi delivers on its output O signals having a first polarization P1 vertical, and is arranged to emit signals summed with a second polarization P2 horizontal.
- Each output O constitutes the end of an R1 branch of a first transmission line LT1 connected to the input of the means of MCP phase control and which constitutes the means of combination MC.
- the configurations of the LT1 transmission line and its R1 branches are chosen to compensate for the differences between the paths followed by the waves between the source S and the different radiating elements ERi in accordance with the first phase law associated with the pointing direction the DPS source for the relevant SR subnet. This compensation is what was previously called the combination of signals.
- the radiating elements ERi feed the means of MC combination in parallel.
- the line of LT1 transmission consists of portions of lines that connect the radiating elements ERi to each other.
- each entry I constitutes the end of a branch R2 of a second transmission line LT2 connected to the output of the means of MCP phase control and which constitutes the means of distribution MD.
- the phase shift applied by the MCP phase control means and the configurations of the LT2 transmission line and its R2 ramifications are chosen in accordance with the second phase law associated with the direction of pointing of the DPA antenna.
- the MD distribution means feed the radiating elements ERi in parallel.
- the power supply is in series.
- the LT2 transmission line consists of portions of lines that connect the radiating elements ERi to each other.
- the first law phase applied by the combining means MC may vary from one subnetwork to each other because of their respective positions with respect to the source S.
- the transmission lines LT1 and LT2 and their branches R1 and R2 are preferably carried out in microstrip technology (or "Microstrip"). But, in variants, the transmission lines LT1 and LT2 and their R1 and R2 branches can be realized in technology triplate or coplanar.
- the means of MC combination (LT1 and R1) and the MD distribution means (LT2 and R2) are preferentially carried out on different levels of the structure of the SR subnet.
- the transmission lines are coupled directly (by contact) to the radiating elements ERi.
- the coupling is done via of slits.
- the combination means MC and the means of MD distribution can be installed on two different levels of the face back.
- Linear subnetwork is understood here to mean an SR sub-network of the type of that illustrated in Figure 4, or one of its variants illustrated on the Figures 5 to 10 and 15.
- the radiating elements ERi are arranged one after another in a chosen direction OX.
- This arrangement is particularly well adapted, although non-exclusive use, with synthetic aperture radar or SAR antennas (for "Synthetic Aperture Radar").
- the combination means MC and MD distribution means do not intersect, unlike subnets in which the combination means MC and the MD distribution means intersect because they are different.
- Radiant elements ERi of the sub-network SR feed in parallel with polarization signals P1 the combination means MC which combines them according to the first law of phase to supply the input of the MCP phase control means.
- the MCP phase control means supply summed signals and the MD distribution means which are, for example, placed at the same level as the combination means MC and the means of MD distribution.
- the MD distribution means distribute in parallel to the radiating elements ERi the summed and out of phase signals, in accordance with the second phase law.
- phase control MCP Due to lack of space, the means of phase control MCP are installed at a different level from the one where the means are installed MC combination and the MD distribution means. This is the reason for which they are materialized in dotted lines.
- each output O of an element radiating ERi constitutes the end of an R1 branch of a first line transmission LT1 connected to the input of the phase control means MCP through a first TR1 transition and which constitutes the combination means MC.
- the configurations of the transmission line LT1 and its R1 branches are chosen to compensate for gaps between the paths followed by the waves between the source S and the different radiating elements ERi according to the first phase law associated with the pointing direction of the DPS source.
- Each input I constitutes the end of an R2 branch of a second transmission line LT2 connected to the output of the means of MCP phase control via a second transition TR2 and which constitutes the MD distribution means. More precisely, the second transition TR2 is here connected to the output of the phase control means MCP via an LT3 auxiliary transmission line.
- the configurations of the LT3 auxiliary transmission line and the LT2 transmission line and its R2 branches are chosen in accordance with the second phase law associated with the pointing direction of the DPA antenna.
- the transmission lines LT1 and LT2 and their branches R1 and R2 are also preferentially carried out in microstrip technology (or microstrip) on the same layer as the one with the lower tiles radiative radiators ERi. But, in variants, the lines of LT1 and LT2 transmission and their R1 and R2 branches can be realized in triplate or coplanar technology.
- the tiles of the radiating elements ERi are here of circular shape, but they could be square shaped.
- phase control means MCP At the level of the combination means MC and means of MD distribution, one can for example use the configuration illustrated on the figure 5.
- This variant takes all the constituents of the subnetwork of Figure 4, but differs from it in that, on the one hand, the outputs O radiating elements ER1 and ER2 are placed opposite one another, just like those of radiating elements ER3 and ER4, and secondly, that the MCP phase control means are placed at the same level as the combination means MC and MD distribution means.
- the signals delivered by the elements radiators ER1 and ER2 (respectively ER3 and ER4) on their outputs O respective ones here have antiparallel polarizations.
- a phase-shifter D responsible for applying a phase shift of 180 ° to the signals it receives before they are combined to the signals from the radiating element ER2 (respectively ER4).
- FIGS. 6A and 6B makes it possible to better visualize the separation of the MCP phase control means, a share, and MC combination means and MD distribution means, on the other hand, mentioned above with reference to FIG.
- the MD distribution means supply the radiating elements ERi in parallel with signals summed and out of phase to be transmitted with a second linear polarization vertical P2.
- the inputs I of the radiating elements ER1 and ER2 are placed "down" of the lower pavers PI (relative to the vertical direction of the page), while the entries I of the elements radiators ER3 and ER4 are placed "at the top” of the lower PI pavers (by report to the vertical direction of the page). Therefore, the polarization of signals emitted by radiating elements ER3 and ER4 is antiparallel to that of the signals emitted by the radiating elements ER1 and ER2. This imposes so that the signals coming from ER1 and ER2 are shifted by 180 °, ER3 and ER4, as shown in FIG.
- each radiating element ERi is here consisting, in particular, of a PI radiative block (or “patch”), which located at the level of the layer comprising the combination means MC and the MD distribution means, and an upper radiative pad PS (materialized in dotted lines), which is placed above a layer dielectric, itself placed above the layer with the cobblestones lower PI, the combination means MC and the distribution means MD.
- a PI radiative block or "patch”
- PS materialized in dotted lines
- the MCP phase control means are implemented in a layer of the structure placed preferably at the rear of the ground plane (no shown), and the layer comprising the combining means MC and the MD distribution means (see Figure 6B). Moreover, the structure multilayer is surrounded by PM metal walls.
- each output O of an element radiating ERi constitutes the end of an R1 branch of a first line transmission LT1 connected to the input of the phase control means MCP through a first TR1 transition and which constitutes the combination means MC.
- the configurations of the transmission line LT1 and its R1 branches are chosen to compensate for gaps between the paths followed by the waves between the source S and the different radiating elements ERi according to the first phase law associated with the pointing direction of the DPS source.
- all the radiating elements ERi feed the means of MC combination in parallel mode with signals having a first polarization P1 horizontal.
- Each input I constitutes the end of an R2 branch of a second transmission line LT2 connected to the output of the means of MCP phase control via a second transition TR2 and which constitutes the MD distribution means. More precisely, the second transition TR2 is here connected to the output of the phase control means MCP via an LT3 auxiliary transmission line.
- the configurations of the LT3 auxiliary transmission line and the LT2 transmission line and its R2 branches are chosen in accordance with the second phase law associated with the pointing direction of the DPA antenna.
- the transmission lines LT1 and LT2 and their branches R1 and R2 are also preferentially carried out in microstrip technology (or microstrip) on the same layer as that comprising the lower pavers PI. But, in variants, the transmission lines LT1 and LT2 and their R1 and R2 branches can be made in triplate technology or coplanar.
- the combination means MC and the distribution means MD can be placed behind the plane of mass.
- each radiating element ERi is fed by two vertical transitions connected to its excitation points.
- This mode of realization requires free space in the center to install MCP phase control means, which imposes a configuration excitation similar to that of Figure 5 and therefore the use of phase shifters 180 ° MM.
- the output (O) of the first radiating element ER1 feeds a first portion P1 of the line transmission cable LT1 connected to the second radiating element ER2, whose output feeds a second portion P2 of the LT1 transmission line connected to the third radiating element ER3, the output of which feeds a third portion of the transmission line LT1, and the output of the fourth radiating element ER4 feeds here a fourth portion P4 of the line of transmission LT1, arranged differently from the other portions P1 to P3 in order to to compensate the antiparallel excitation of the fourth radiating element ER4.
- the transmission line LT1 supplies the MCP phase control means, that feed the LT2 transmission line whose ramifications are connected to the inputs (I) of the radiating elements ERi.
- This embodiment is particularly interesting when has "reversible" MCP phase control means because it allows the antenna A to operate in two polarization modes.
- the radiating elements ERi can supply the transmission line LT2 in parallel with summed signals and out of phase to be emitted with a second vertical bias P2.
- the transmission line LT1 serially feeds the elements radiators ERi with polarization signals P1 horizontal.
- the first subnetwork variant SR differs from the subnetwork in Figure 7 by using modules of MCT switching on the branches of the LT1 transmission line and on the LT2 transmission line. More specifically, in the illustrated configuration, the MCT switching modules (which are everywhere doubled to allow functioning in both directions) are placed in a first position that allows the application of the phase law associated with the direction of pointing of the DPA antenna. The signals are then collected in parallel having a first vertical polarization P1 and series of summed and out of phase signals to be transmitted with a second horizontal polarization P2. On the other hand, when all modules of switching MCT are in a second position, we can apply the law of phase associated with the pointing direction of the DPS source. This allows to adapt the polarization to that of the source S. The signals having a first horizontal polarization are then collected in series, while one distributes parallel summed and out of phase signals to be transmitted with a second vertical polarization.
- the second subnetwork variant SR illustrated in FIG. differs from the subnetwork of Figure 7 by feeding the cobblestones radiating elements ERi either on their sides, but in their corners, of to simultaneously excite the two polarizations, and by the use of MCT switching modules in the radiating elements ERi in order to select one of the two polarizations excited, both in collection and program.
- double polarization is not obligatorily of linear type. It can indeed be of circular type.
- the radiating elements ERi can be, for example, microstrip resonators truncated according to their diagonal or slightly rectangular microstrip resonators.
- the MCT switches allowing the operation in double polarization were not represented. But, in reality, they are placed at the inlet and the outlet of the radiating elements ERi, as is the case in the embodiment of Figure 8.
- Such a band B is schematically illustrated in FIG. the case of linear SR subnetworks.
- the subnetworks SR of a B-band are placed against each other parallel to their extension direction (here OX).
- Antenna A is then reconfigurable according to the direction OY (or elevation), that is to say in the plane perpendicular to the direction OX.
- antenna A can have multiple parallel B bands of planar subnets so that it be reconfigurable at the same time according to the direction OY (or elevation), that is to say in the plane perpendicular to the direction OX, and following the direction OX, that is to say in the plane perpendicular to the direction OY.
- the radiating elements ERi are preferentially made in the form of a multilayer structure conventional comprising, in particular, a lower radiating conductive pad PI, coupled, on the one hand, to the input I and / or the output O, and on the other hand, to a pad upper radiative conductor PS responsible for collecting the waves from the source S and emit the waves collected after transformation.
- the coupling between the upper radiator blocks PS and lower PI of an element radiating ERi can be performed either directly by conduction, via a conductive layer or bushings, either electromagnetically via a layer of dielectric material.
- symmetrical slots FS is preferable because it provides better isolation between the two polarizations and does not generate high levels of cross polarization.
- the S substrate which supports power circuits and cobblestones radiative PI
- the S substrate which supports power circuits and cobblestones radiative PI
- the S substrate can be realized in PTFE type material having a dielectric constant of about 3.2, a loss tangent from about 0.003 to 10 GHz, a thickness of about 0.79 mm and a thickness about 17 ⁇ m copper.
- Separators placed between the pavers radiative and FA or FS slots can for example be realized in a Rohacell type material 31 having a dielectric constant of about 1.05, a loss tangent of about 0.0002 to 2.5 GHz and a thickness about 2 mm.
- the network pitch that is, the distance between the radiating elements ERi
- the network pitch is chosen substantially equal to 20 mm, which corresponds to 0.65 ⁇ when the frequency is equal to 9.8 GHz.
- the MCP phase control means of each SRi subnetwork are preferably made in the form of phase shifters, and more preferentially still in the form of configuration delay lines different (so as to apply different phase shifts), coupled to at least one micron electromechanical system of the MEMS type, ensuring the switch function.
- These systems are particularly advantageous because they have very low insertion losses, typically 0.1 dB for frequencies up to about 40 GHz.
- the state of the MEMS is controlled by electrical voltages.
- Each subnet SR may also include, as illustrated in FIG. 15, low noise amplification means (or LNA for “Low”).
- Amplifier and / or power amplifier means (or HPA for "High Power Amplifier”) to provide near-optical amplification summed waves, before or after phase shift by means of MCP phase control.
- the subnet SR comprises a circulator CR connected, on the one hand, to the transmission line LT2, and other on the other hand, the amplification means LNA and HPA, which are also connected to an MCT switch, itself connected to the means of MCP phase control.
- the signals reach either the LNA to be amplified before “back up” towards the MCP phase control means then towards the elements radiating ERi (which allows operation of the antenna in reception), to the HPA to be amplified before “down” to the elements ERi (which allows the antenna to transmission).
- LNA and HPA may for example be performed in the form of amplifying chips, such as MMICs.
- the number of radiating elements belonging to each sub-network can be any, since it is at least two.
- the number of subnets of an antenna can be whatever, since it is at least two.
- subnetwork embodiments have been described in which the radiating elements consisted of a structure multilayer comprising radiative pavers. But, the invention is not limited to this single type of radiating element. It also concerns subnetworks equipped with radiating elements such as microstrip resonators, slots, or dielectric resonators.
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Abstract
Description
- au moins deux éléments rayonnants chargés, d'une part, de collecter des signaux délivrés par une source et présentant au moins une première polarisation choisie, et d'autre part, d'émettre des signaux déphasés présentant au moins une seconde polarisation choisie, orthogonale à la première,
- des moyens de combinaison chargés de sommer les signaux collectés en fonction d'une première loi de phase choisie afin qu'ils correspondent à une direction choisie de pointage de la source,
- des moyens de contrôle de phase chargés d'appliquer un déphasage choisi aux signaux sommés, et
- des moyens de distribution chargés de distribuer les signaux déphasés entre les éléments rayonnants, en fonction d'une seconde loi de phase choisie de sorte qu'ils les rayonnent dans une direction de pointage d'une zone choisie.
- ses moyens de contrôle de phase peuvent être des déphaseurs comportant des lignes à retard de configurations différentes et au moins un commutateur, comme par exemple un système électromécanique micronique de type MEMS,
- ses moyens de combinaison et ses moyens de distribution peuvent être
distincts de sorte que les sous-réseaux soient de type non réciproque.
Dans ce cas : - les moyens de combinaison peuvent comprendre une ligne de transmission présentant des ramifications, couplées aux éléments rayonnants de manière à collecter en parallèle les signaux qui présentent la première polarisation, et conformées de manière à définir la première loi de phase. En variante, les moyens de combinaison peuvent comprendre une ligne de transmission constituée de portions de lignes, raccordant les éléments rayonnants les uns aux autres de manière à collecter en série les signaux présentant la première polarisation, et conformées de manière à définir la première loi de phase,
-
- chaque sous-réseau peut être de type planaire,
- chaque sous-réseau peut être de type linéaire, ses éléments rayonnants étant alignés suivant une direction choisie,
- ils peuvent être installés en parallèle de manière à constituer une bande d'au moins deux sous-réseaux. Bien entendu, l'antenne peut comporter plusieurs bandes parallèles entre elles,
- ses éléments rayonnants peuvent être agencés de manière à collecter des
signaux présentant les première et seconde polarisations choisies. Dans ce
cas :
-
-
- chaque ligne de transmission peut être réalisée dans une technologie choisie parmi au moins les technologies microruban, coplanaire et triplaque,
- ses éléments rayonnants peuvent être couplés aux moyens de combinaison et aux moyens de distribution par contact direct. En variante, les éléments rayonnants peuvent être couplés de façon électromagnétique aux moyens de combinaison et aux moyens de distribution,
- ses éléments rayonnants peuvent être par exemple des structures multicouches à pavés radiatifs, des résonateurs microruban, des fentes ou des résonateurs diélectriques,
- des moyens d'amplification chargés d'amplifier les ondes sommées avant qu'elles ne soient émises et/ou une fois collectées.
- la figure 1 est un schéma de principe d'un sous-réseau d'une antenne réseau réflecteur selon l'invention,
- la figure 2 illustre de façon schématique un exemple de réalisation d'un sous-réseau non réciproque de type planaire,
- la figure 3 illustre dans une vue en coupe transversale une antenne réseau réflecteur selon l'invention comprenant deux sous-réseaux non réciproques de type planaire,
- la figure 4 illustre de façon schématique un premier exemple de réalisation d'un sous-réseau non réciproque de type linéaire,
- la figure 5 illustre de façon schématique un deuxième exemple de réalisation d'un sous-réseau non réciproque de type linéaire,
- les figures 6A et 6B illustrent de façon schématique deux parties d'un troisième exemple de réalisation d'un sous-réseau non réciproque de type linéaire,
- la figure 7 illustre de façon schématique un quatrième exemple de réalisation d'un sous-réseau non réciproque de type linéaire,
- la figure 8 illustre de façon schématique un cinquième exemple de réalisation d'un sous-réseau non réciproque de type linéaire, adapté à une double polarisation,
- la figure 9 illustre de façon schématique un sixième exemple de réalisation d'un sous-réseau non réciproque de type linéaire, adapté à une double polarisation,
- la figure 10 illustre de façon schématique un septième exemple de réalisation d'un sous-réseau non réciproque de type linéaire, adapté à une double polarisation,
- la figure 11 illustre de façon schématique un exemple de bande de sous-réseaux non réciproques de type linéaire,
- la figure 12 illustre de façon schématique un exemple de combinaison de bandes de sous-réseaux non réciproques de type planaire,
- la figure 13 illustre de façon schématique un exemple de réalisation d'un élément rayonnant comportant des fentes asymétriques,
- la figure 14 illustre de façon schématique un exemple de réalisation d'un élément rayonnant comportant des fentes symétriques, et
- la figure 15 est une variante de la figure 7 comportant des moyens d'amplification de signaux.
- "Dual-polarised wideband microstrip antenna", S.C. GAO et al, Electronics Letters, 30 août 2001, Vol. 37, n°18,
- « Aperture coupled patch antennas with wide-bandwidth and dual polarization capabilities », C.M. TAO et al, Antennas and Propagation Society International Symposium, 1988, AP-S, Digest, juin 1988, Vol.3, pages 936-939,
- "Dual-polarized array for signal-processing applications in wireless communications", B. LINDMARK et al, IEEE Transactions on Antennas and Propagation, Vol.46, Issue: 6, juin 1998, pages 758-763,
- "Wideband dual-polarised microstrip patch antenna", S.C. GAO et al, Electronics Letters, 27 septembre 2001, Vol. 37, n°20,
- "Investigations into a power-combining structure using a reflect array of dual feed aperture-coupled microstrip patch antennas", Marek E. Bialkowsksi, IEEE Transactions on Antennas and Propagation, Vol. 50, Issue: 6, juin 2002, pages 841-849.
Claims (19)
- Antenne réseau réflecteur (A), caractérisée en ce qu'elle est subdivisée en sous-réseaux (SR) indépendants comportant chacun :au moins deux éléments rayonnants (ER) agencés, d'une part, pour collecter des signaux délivrés par une source (S) et présentant au moins une première polarisation choisie, et d'autre part, pour émettre des signaux déphasés présentant au moins une seconde polarisation choisie, orthogonale à la première,des moyens de combinaison (MC) agencés pour sommer lesdits signaux collectés en fonction d'une première loi de phase choisie de sorte qu'ils correspondent à une direction choisie de pointage de la source (DPS),des moyens de contrôle de phase (MCP) agencés pour appliquer un déphasage choisi aux signaux sommés, etdes moyens de distribution (MD) agencés pour distribuer lesdits signaux déphasés entre lesdits éléments rayonnants, en fonction d'une seconde loi de phase choisie de sorte que lesdits éléments rayonnants (ER) de chaque sous-réseau (SR) les rayonnent dans une direction de pointage d'une zone choisie (DPA)et en ce que lesdits moyens de combinaison (MC) et lesdits moyens de distribution (MD) sont distincts de sorte que lesdits sous-réseaux (SR) soient de type non réciproque.
- Antenne selon la revendication 1, caractérisée en ce que lesdits moyens de contrôle de phase (MCP) et lesdits moyens de distribution (MD) sont configurables de sorte que ladite direction de pointage de la zone choisie (DPA) soit variable.
- Antenne selon l'une des revendications 1 et 2, caractérisée en ce que lesdits moyens de contrôle de phase (MCP) sont des déphaseurs.
- Antenne selon la revendication 3, caractérisée en ce que lesdits déphaseurs (MCP) comportent au moins deux lignes à retard de configurations différentes et au moins un système électromécanique micronique de type MEMS.
- Antenne selon l'une des revendications 1 à 4, caractérisée en ce que lesdits moyens de combinaison (MC) comprennent une ligne de transmission (LT1) présentant des ramifications (R1) couplées auxdits éléments rayonnants (ER) de manière à collecter en parallèle les signaux présentant ladite première polarisation et conformées de manière à définir ladite première loi de phase.
- Antenne selon l'une des revendications 1 à 4, caractérisée en ce que lesdits moyens de combinaison (MC) comprennent une ligne de transmission (LT1) constituée de portions de ligne (P) raccordant lesdits éléments rayonnants (ER) les uns aux autres, de manière à collecter en série les signaux présentant ladite première polarisation et conformées de manière à définir ladite première loi de phase.
- Antenne selon l'une des revendications 1 à 6, caractérisée en ce que lesdits moyens de distribution (MD) comprennent une ligne de transmission (LT2) présentant des ramifications (R2) couplées auxdits éléments rayonnants (ER) de manière à distribuer en parallèle les signaux déphasés et conformées de manière à définir ladite seconde loi de phase.
- Antenne selon l'une des revendications 1 à 6, caractérisée en ce que lesdits moyens de distribution (MD) comprennent une ligne de transmission (LT2) constituée de portions de lignes (P) raccordant lesdits éléments rayonnants (ER) les uns aux autres de manière à distribuer en série les signaux déphasés et conformées de manière à définir ladite seconde loi de phase.
- Antenne selon l'une des revendications 1 à 8, caractérisée en ce que chaque sous-réseau (SR) est de type planaire.
- Antenne selon l'une des revendications 1 à 8, caractérisée en ce que chaque sous-réseau (SR) est de type linéaire, ses éléments rayonnants (ER) étant alignés suivant une direction choisie (OX).
- Antenne selon l'une des revendications 9 et 10, caractérisée en ce que lesdits sous-réseaux (SR) sont installés en parallèle de manière à constituer une bande (B), d'au moins deux sous-réseaux.
- Antenne selon la revendication 11, caractérisée en ce qu'elle comprend au moins deux bandes (B) parallèles entre elles.
- Antenne selon l'une des revendications 1 à 12, caractérisée en ce que lesdits éléments rayonnants (ER) sont agencés pour collecter des signaux présentant lesdites première et seconde polarisations choisies, et en ce qu'elle comprend des premiers moyens de sélection de phase (MCT), intercalés entre lesdits éléments rayonnants (ER) et lesdits moyens de combinaison (MC), et des seconds moyens de sélection de polarisation (MCT), intercalés entre lesdits moyens de distribution (MD) et lesdits éléments rayonnants (ER), lesdits premier et second moyens de sélection de polarisation étant agencés de manière à sélectionner sur ordre l'une desdites première et seconde polarisations, de sorte que ladite antenne (A) puisse fonctionner selon deux modes de polarisation différents.
- Antenne selon l'une des revendications 1 à 12, caractérisée en ce que lesdits éléments rayonnants (ER) sont agencés pour collecter des signaux présentant lesdites première et seconde polarisations choisies, et comportent des moyens de sélection de polarisation (MS) agencés de manière à sélectionner sur ordre l'une desdites première et seconde polarisations, de sorte que ladite antenne (A) puisse fonctionner selon deux modes de polarisation différents.
- Antenne selon l'une des revendications 5 à 14, caractérisée en ce que chaque ligne de transmission (LT1, LT2) est réalisée dans une technologie choisie dans un groupe comprenant au moins une technologie microruban, une technologie coplanaire et une technologie triplaque.
- Antenne selon l'une des revendications 1 à 15, caractérisée en ce que lesdits éléments rayonnants (ER) sont choisis dans un groupe comprenant des structures multicouches à pavés radiatifs, des résonateurs microruban, des fentes et des résonateurs diélectriques.
- Antenne selon l'une des revendications 1 à 16, caractérisée en ce que lesdits éléments rayonnants (ER) sont couplés auxdits moyens de combinaison (MC) et auxdits moyens de distribution (MD) par contact direct.
- Antenne selon l'une des revendications 1 à 16, caractérisée en ce que lesdits éléments rayonnants (ER) sont couplés de façon électromagnétique auxdits moyens de combinaison (MC) et auxdits moyens de distribution (MD).
- Antenne selon l'une des revendications 1 à 18, caractérisée en ce que chaque sous-réseau (SR) comprend des moyens d'amplification (LNA, HPA) agencés de manière à amplifier lesdites ondes sommées avant qu'elles ne soient émises et/ou une fois collectées.
Applications Claiming Priority (2)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
FR0311109 | 2003-09-23 | ||
FR0311109A FR2860107B1 (fr) | 2003-09-23 | 2003-09-23 | Antenne reseau reflecteur reconfigurable a faibles pertes |
Publications (1)
Publication Number | Publication Date |
---|---|
EP1519444A1 true EP1519444A1 (fr) | 2005-03-30 |
Family
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Family Applications (1)
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EP04292265A Withdrawn EP1519444A1 (fr) | 2003-09-23 | 2004-09-21 | Antenne réseau réflecteur reconfigurable à faibles pertes |
Country Status (4)
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US (1) | US7142164B2 (fr) |
EP (1) | EP1519444A1 (fr) |
CA (1) | CA2480588C (fr) |
FR (1) | FR2860107B1 (fr) |
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US7145515B1 (en) * | 2004-01-02 | 2006-12-05 | Duk-Yong Kim | Antenna beam controlling system for cellular communication |
FR2894080B1 (fr) * | 2005-11-28 | 2009-10-30 | Alcatel Sa | Antenne reseau a maillage irregulier et eventuelle redondance froide |
US8217847B2 (en) * | 2007-09-26 | 2012-07-10 | Raytheon Company | Low loss, variable phase reflect array |
US8803757B2 (en) * | 2008-09-15 | 2014-08-12 | Tenxc Wireless Inc. | Patch antenna, element thereof and feeding method therefor |
FR2936906B1 (fr) * | 2008-10-07 | 2011-11-25 | Thales Sa | Reseau reflecteur a arrangement optimise et antenne comportant un tel reseau reflecteur |
US8149179B2 (en) * | 2009-05-29 | 2012-04-03 | Raytheon Company | Low loss variable phase reflect array using dual resonance phase-shifting element |
JP4957980B2 (ja) * | 2010-01-05 | 2012-06-20 | ソニー株式会社 | アンテナ装置及び通信装置 |
US9547076B2 (en) * | 2012-10-17 | 2017-01-17 | Raytheon Company | Elevation monopulse antenna synthesis for azimuth connected phase array antennas and method |
US9391375B1 (en) | 2013-09-27 | 2016-07-12 | The United States Of America As Represented By The Secretary Of The Navy | Wideband planar reconfigurable polarization antenna array |
US10374315B2 (en) | 2015-10-28 | 2019-08-06 | Rogers Corporation | Broadband multiple layer dielectric resonator antenna and method of making the same |
US10476164B2 (en) | 2015-10-28 | 2019-11-12 | Rogers Corporation | Broadband multiple layer dielectric resonator antenna and method of making the same |
US11367959B2 (en) | 2015-10-28 | 2022-06-21 | Rogers Corporation | Broadband multiple layer dielectric resonator antenna and method of making the same |
US10355361B2 (en) | 2015-10-28 | 2019-07-16 | Rogers Corporation | Dielectric resonator antenna and method of making the same |
US10601137B2 (en) | 2015-10-28 | 2020-03-24 | Rogers Corporation | Broadband multiple layer dielectric resonator antenna and method of making the same |
US11283189B2 (en) | 2017-05-02 | 2022-03-22 | Rogers Corporation | Connected dielectric resonator antenna array and method of making the same |
US11876295B2 (en) | 2017-05-02 | 2024-01-16 | Rogers Corporation | Electromagnetic reflector for use in a dielectric resonator antenna system |
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CN108226876A (zh) * | 2017-12-28 | 2018-06-29 | 北京融创远大网络科技有限公司 | 一种降低极化损耗的智能车载雷达装置 |
US10910722B2 (en) | 2018-01-15 | 2021-02-02 | Rogers Corporation | Dielectric resonator antenna having first and second dielectric portions |
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US11616302B2 (en) | 2018-01-15 | 2023-03-28 | Rogers Corporation | Dielectric resonator antenna having first and second dielectric portions |
US11303020B2 (en) * | 2018-07-23 | 2022-04-12 | Metawave Corporation | High gain relay antenna system with multiple passive reflect arrays |
US11552390B2 (en) | 2018-09-11 | 2023-01-10 | Rogers Corporation | Dielectric resonator antenna system |
US11031697B2 (en) | 2018-11-29 | 2021-06-08 | Rogers Corporation | Electromagnetic device |
CN113169455A (zh) | 2018-12-04 | 2021-07-23 | 罗杰斯公司 | 电介质电磁结构及其制造方法 |
US11482790B2 (en) | 2020-04-08 | 2022-10-25 | Rogers Corporation | Dielectric lens and electromagnetic device with same |
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CN113991312A (zh) * | 2021-10-26 | 2022-01-28 | 东南大学 | 双极化3bit相位独立可调的可重构智能超表面单元 |
CN114040478A (zh) * | 2021-10-29 | 2022-02-11 | 清华大学 | 低功耗的智能超表面硬件结构、预编码方法及装置 |
CN114188726B (zh) * | 2021-10-29 | 2024-04-26 | 电子科技大学长三角研究院(湖州) | 一种有源智能反射表面 |
EP4415175A1 (fr) * | 2023-02-08 | 2024-08-14 | Siemens AG Österreich | Reflecteur a commande electronique et systeme |
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Also Published As
Publication number | Publication date |
---|---|
FR2860107B1 (fr) | 2006-01-13 |
US20050122273A1 (en) | 2005-06-09 |
CA2480588C (fr) | 2012-03-06 |
US7142164B2 (en) | 2006-11-28 |
FR2860107A1 (fr) | 2005-03-25 |
CA2480588A1 (fr) | 2005-03-23 |
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