EP1166393B1 - Procede et dispositif de mise en forme de faisceau - Google Patents

Procede et dispositif de mise en forme de faisceau Download PDF

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Publication number
EP1166393B1
EP1166393B1 EP00913950A EP00913950A EP1166393B1 EP 1166393 B1 EP1166393 B1 EP 1166393B1 EP 00913950 A EP00913950 A EP 00913950A EP 00913950 A EP00913950 A EP 00913950A EP 1166393 B1 EP1166393 B1 EP 1166393B1
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Prior art keywords
downlink
antenna
uplink
aps
angle spectrum
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German (de)
English (en)
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EP1166393A1 (fr
Inventor
Ernst Bonek
Klaus Hugl
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Nokia Oyj
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Nokia Oyj
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q25/00—Antennas or antenna systems providing at least two radiating patterns
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
    • H01Q3/2605—Array of radiating elements provided with a feedback control over the element weights, e.g. adaptive arrays
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
    • H01Q3/2605—Array of radiating elements provided with a feedback control over the element weights, e.g. adaptive arrays
    • H01Q3/2611—Means for null steering; Adaptive interference nulling
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
    • H01Q3/2605—Array of radiating elements provided with a feedback control over the element weights, e.g. adaptive arrays
    • H01Q3/2611—Means for null steering; Adaptive interference nulling
    • H01Q3/2617—Array of identical elements
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
    • H01Q3/2605—Array of radiating elements provided with a feedback control over the element weights, e.g. adaptive arrays
    • H01Q3/2647—Retrodirective arrays

Definitions

  • the invention relates to a method for beam shaping for an adaptive antenna group containing several antenna elements in the downlink of frequency duplex systems, where for the antenna elements antenna weights for transmission in the Downlink based on direction information of the uplink be determined.
  • the invention relates to a device for Beamforming for one containing several antenna elements adaptive antenna group in the downlink of frequency duplex systems, with a signal processor unit for determining Antenna weights for the antenna elements for transmission in the Downlink based on direction information of the uplink.
  • Adaptive antennas were first used in radar technology, and for some time now its use in cellular examined.
  • the use of adaptive antennas can be one Reduction of the received interference by directed reception, to reduce the interference generated by directed Send and a reduction in the time dispersion of the mobile radio channel and thus reducing the intersymbol interference that the Bit error rate significantly determined, lead.
  • Radio channel is by its frequency and / or its time slot (in time multiplex - TDMA - Time Division Multiple Access) or its Code (in code division multiplex - CDMA - Code Division Multiple Access) established.
  • TDMA and FDMA Frequency Division Multiple Access
  • the Directionally selective sending / receiving can also be done in CDMA systems used to determine the possible number of participants to increase a frequency and thus the spectral efficiency and to increase the capacity of a cellular mobile radio system. It with constant interference, the possible number the subscriber on a traffic channel raised by the base station with the linear, adaptive antenna group in the Uplink detected and supplied in the downlink can be.
  • Co-channel interference suppression and its detection are three basic methods known: (1) procedures based on the Knowledge of the spatial structure of the antenna group (so-called spatial-reference method), cf. R. Roy and R. Kailath, "ESPRIT - Estimation of Signal Parameters via Rotational Invariance Techniques ", IEEE Trans. Acoust., Speech and Signal Processing, Vol. 37, July 1989, pp. 984-995; (2) Methods based on knowledge of a known signal sequence (so-called temporal-reference method), cf. in S. Ratnavel, A. Paulraj and A.B. Constantinides, "MMSE Space-Time Equalization for GSM Cellular Systems ", Proc.
  • FDD systems frequency division duplex systems
  • FDD systems use the signals in the uplink and in the downlink broadcast on different frequencies, and thereby the necessary separation between sent and received data at the mobile and at the base station.
  • the antenna directional diagram is due to the frequency difference Using the same physical antenna group and the same Antenna weights (amplitude and phase) with different Frequencies different. That is why it is not advisable same antenna weights for sending and receiving at the base station to use a cellular mobile radio system.
  • No. 5,848,060 A describes that the spatial covariance matrix is estimated from the received signals of the uplink; the occurring relative phases of the matrix elements are then scaled with the ratio of the transmission frequency to the reception frequency (f S / f E ). Due to the multipath propagation of the individual signals, however, the frequency is non-linear in the phase relationship of the individual antenna elements. Therefore, this application is limited to cases with a direct line of sight between the transmitter and receiver without reflections from different directions, such as in satellite communication.
  • the proposal also includes a compensation matrix on the covariance matrix the upward route.
  • This compensation matrix is only valid for very small relative duplex spacings 2 (f S -f E ) / (f S + f E ) and is averaged over the entire application angle range of the adaptive antenna.
  • This method does not correct the frequency difference, but only reduces the deviation and "smears" the spatial structure of the mobile radio channel contained in the covariance matrix over the entire angular range. For this reason, this method cannot be used under any circumstances.
  • the covariance matrix has already been proposed to decompose the uplink into Fourier coefficients and at to restore the transmission frequency, cf. J.M. Goldberg and J.R. Fonollosa, "Downlink beamforming for spatially distributed sources in cellular mobile communications ", signal processing Vol.65, No.2, March 1998, pp. 181-199.
  • This method tries the exact phase relationship of the individual signal paths on the transmission frequency to restore, but also smears the spatial structure of the covariance matrix.
  • the aim of the invention is now a method and a device to be provided as indicated at the beginning, with the or in an efficient manner with FDD systems Beamforming in the downlink allows the Interference also with those transmitted by the base station the signals received by the mobile stations are reduced and an increase in the number of users that can be served, i.e. Mobile stations is made possible.
  • the method according to the invention is the one mentioned at the beginning Kind characterized in that the antenna weights for transmission in the downlink based on the power angle spectrum the uplink of each user are determined, the power angle spectrum by Hiding unwanted areas is modified.
  • the device according to the invention is correspondingly of the type mentioned above, characterized in that the Signal processor unit for determining the antenna weights for the transmission in the downlink on the basis of the power angle spectrum the uplink of each user under its modification by hiding unwanted Areas is set up.
  • beam shaping is thus used in the downlink the power angle spectrum of the
  • the upward link of the individual user is used, whereby undesirable angular ranges in this power angle spectrum are hidden, i.e. any interferers are in the power angle spectrum hidden for optimal alignment of the Main club in the direction of the respective user.
  • the power angle spectrum using a known signal sequence of the transmission signal is estimated. It is also from Advantage if the power angle spectrum of the uplink based on the spatial covariance matrices of the uplink of the individual users or, if applicable, of mean values the same is estimated. Furthermore, it has proven to be cheap proven if based on the modified power-angle spectrum of the individual user or of its mean value the respective spatial covariance matrix of the downlink is determined becomes. Finally, it is advantageous if the spatial covariance matrix the downlink or its mean value for calculation the antenna weights are used for transmission.
  • the invention Technology is unrestricted by the spreading conditions of electromagnetic waves applicable. It is subject to no restrictions on a single dominant Direction of incidence per participant and is without additional Hardware expenditure can be used. There are no assumptions about that Frequency difference between transmission and reception, and therefore the technique described here also works independently of relative duplex spacing. It is neither expensive iterative approximation methods or high-resolution direction estimation algorithms needed, so a very computationally efficient Solution is achieved.
  • the task of beamforming in the downlink from cellular mobile radio systems with adaptive antennas at the base station consists of the signals of each user to send from the base station that most of the energy from the desired one Users receive and as little energy as possible to others To users who appear as interference becomes.
  • Bit error rate BER To achieve this goal you have to put the main lobe of the antenna pattern into the Direction of the desired user and zeros in the antenna diagram towards those users who are on the same Frequency are supplied. This principle is illustrated in Fig. 1.
  • FIG. 1 1 An adaptive antenna is shown schematically in detail in FIG. 1 1 shown with beamforming in the downlink, with a Signal processor 2, the individual antenna elements 1.1, 1.2 to 1.M controlled with different phases and amplitudes thus the desired antenna pattern 3 or 4 is generated.
  • the Main lobes 5 and 6 of antenna pattern 3 and 4 show in Direction of a respective user 7 or 8, with zeros 9 or 10 in the antenna diagram 3 or 4 in the direction of the show other user 8 or 7.
  • the antenna group 1 is the shape of the antenna pattern 3 or 4 set. This is illustrated below using a linear example Antenna group explained with reference to FIG. 2. 2 shows schematically one from a direction ⁇ on the antenna elements 1.1, 1.2, 1.3 ... 1.M incident wave.
  • d is also the distance between the individual Antenna elements and with ⁇ L the path difference of the wave from an antenna element, e.g. 1.2, to the next antenna element, e.g. 1.3.
  • the distance d lies here for example in the order of the wavelength and is preferably less than the wavelength (e.g. approximately the same half the wavelength).
  • f further denotes the carrier frequency of the transmitted signal and c the speed of light.
  • the group response is the antenna group 1 both from the direction of incidence of the wave as well as depending on the carrier frequency.
  • a base station 11 with a adaptive antenna 1 with nine antenna elements 1.1 ... 1.9 and with multipath propagation between base station 11 and mobile stations (MS) 7, 8 illustrates where multipath propagation for example due to reflections on buildings 12 comes about.
  • the individual signals overlap in the uplink on the antenna elements 1.1 to 1.9 of the linear antenna group 1 and in the downlink on the antenna of the respective mobile phone 7, 8. Whether the individual signals overlap constructively or destructively depends on the phase relationship of the individual waves to one another from. Since different carrier frequencies are used in an FDD system for the uplink and the downlink, the phase relationships of the waves to one another also change. For this reason, the shrinkage (the constructive and destructive overlay) in the up and down sections is absolutely uncorrelated. But not only the fading also the antenna pattern changes due to the frequency shift. Both the position of the main lobe and the position of the zeros and their shape in the group directivity change very strongly, as illustrated in FIGS. 4A and 4B. FIG.
  • FIG. 4A shows an antenna diagram for the frequency of the uplink and FIG. 4B shows a corresponding antenna diagram for the frequency of the downlink.
  • the signals come from the directions -20 ° and 40 ° for a user B1 and from the directions -50 ° and 10 ° for a user B2.
  • the influence on The main mace is not as strong as it is anyway are wide and therefore only a maximum of 0.5dB smaller Antenna gain results.
  • the zeros in the direction of each other users, however, are very narrow and in use the same antenna weights for the downlink as for the Upward path is the generated disturbance for the other User increased dramatically. Because of this, it is not advisable to use the same antenna weights for receiving and for to use the transmission at the base station 11.
  • the fading is between Sending and receiving case uncorrelated, and there is a different antenna pattern when using the same antenna weights.
  • a signal processor unit is used in base station 11 for this signal shaping 2 used, cf. Fig. 3, based on the received signals for driving the antenna elements 1.1 up to 1.M antenna weights especially for the downlink determined.
  • the antenna group 1 generally formulated, consists of M antenna elements 1.1 to 1.M.
  • the received signals are at 13 band-limited (filtering with channel selection filter) and at 14 mixed into the baseband, amplified at 15 and digitized at 16, and in the signal processor unit 2, the signals detected using adaptive algorithms.
  • the signals are then weighted and modulated accordingly (at 14) and radiated by the antenna 1.
  • 3 is the signal exchange between the base station is schematic 11 and the access network 17 additionally illustrated.
  • Fig. 5 a flow chart is shown that the evaluation from the input signals to the determination of the antenna weights for the desired beam formation in the downlink schematically illustrated.
  • a matrix X of noisy input signals of a plurality of co-channel signals serves as an input data set which is to be processed further in the signal processor unit 2.
  • the matrix X contains N samples with critical sampling (sampling rate 1 / T) of K co-channel signals which are derived from the M individual elements of the array antenna 1, and interference signals from neighboring cells which use the same frequencies.
  • a known signal sequence S k block 31 in Fig. 5
  • the channel impulse responses of each of the K users B1 to BK estimated on each antenna element 1.1 to 1.M in step 30 (“subscriber recognition").
  • the channel impulse responses of each subscriber B1 to BK can be estimated independently of one another using methods known per se (for example by correlation with the known signal sequence S k ) or all in one step (for example using the method of least squares).
  • the channel impulse responses are estimated in more detail from the received data X and the known signal sequence S k (preamble, midamble in TDMA, or spreading code in CDMA systems), the received signal can be represented as follows: h k (t, ⁇ ) and S k (t) denote the time-variant impulse response at time t and the transmitted signal of the k-th user; and N (t) denotes the vector with the thermal noise on the antenna elements 1.1 to 1.M.
  • the summation takes into account that the signals are received from all K users B1 to BK. From this relationship, the channel impulse responses of users B1 to BK can now be estimated.
  • the joint estimate can be made as follows:
  • the output signal one is used the spread code used for the signal-adapted filter.
  • This matched filter is a standard receiver component of CDMA systems; a description of the corresponding relationships for the estimation can be superfluous here.
  • the channel impulse response matrices H k with k 1 to K (for users B1 to BK) contain all the information required for the beam shaping process.
  • a signal that is incident on antenna group 1 from a direction ⁇ results in a group response that is equal to the array steering vector a ( ⁇ , f) already mentioned.
  • the channel impulse response contains all signals with the group responses and the associated signal strengths. For this reason and by replacing the formation of the expected value with the temporal mean (in the discrete-time mean of the samples), the spatial covariance matrix can be represented as follows
  • the spatial covariance matrix R k is also frequency-dependent.
  • the spatial covariance matrix R k of the uplink is generally used to calculate the complex antenna weights for reception with adaptive antennas.
  • the use of these antenna weights for the downlink shifts the zeros, as already explained. For this reason, one must try to transform the spatial covariance matrix R k from the reception frequency f E of the base station to the transmission frequency f S in order to be able to calculate the antenna weights for the downlink.
  • This frequency transformation is indicated in FIG. 5 at step 50, the frequency transformation the spatial structure of the mobile radio channel, which is contained in the spatial covariance matrix R k , from the reception frequency of the base station (frequency of the uplink) f E to the transmission frequency of the base station (frequency the downlink) f S is transformed.
  • This technique is shown in more detail in Fig. 6 and will be described in more detail below.
  • the estimated spatial covariance matrices R k of the K users of the downlink are formed so that they are hermitic. This means that all directions of incidence are considered to be independent of each other.
  • the covariance matrices R k (f S ) at the transmission frequency f S which are obtained at the end of step 50, are used to calculate the optimal antenna weights for transmission in the downlink. This is done in step 60 in FIG. 5. All beam shaping algorithms based on knowledge of the spatial covariance matrix can be used for this.
  • the signals for the individual users are now multiplied (weighted) by their antenna weights and sent by the base station 11.
  • FIG. 6 shows the power-angle spectrum estimate at block 52, starting from the covariance matrices R k (f E ) of the uplink for the k-th user.
  • R k (f E ) the covariance matrices
  • the power angle spectrum APS k of each of the K users is estimated.
  • this step can also be carried out using other, similar methods of spectral search.
  • the power angle spectrum APS k does not contain any phase relationships of the individual signal paths of the mobile radio channel to one another, which is neither necessary nor meaningful, since the fading and the phase relationships due to the multipath propagation are absolutely uncorrelated due to the different transmission and reception frequencies in a frequency duplex system.
  • FIG. 7 shows an example of an estimated power angle spectrum APS k of a user Bk who is in the + 10 ° direction from the base station 11.
  • the dashed line in Fig. 7 outlines the estimated power-angle spectrum of some co-channel interferers, which are at -30 °, + 12 ° and 50 °.
  • step 54 in FIG. 6 the dominant regions of the power angle spectrum APS k are then extracted.
  • the entire power angle spectrum APS k does not necessarily have to be used to reconstruct the spatial covariance matrix, but only those angle ranges can be used from which the majority of the signals in the uplink are received, with the antenna lobes therefore being directed into these angle ranges are or in relation to the interference only in such angular ranges zero points are placed in the antenna diagram.
  • This technique of masking out some angular ranges e.g.
  • FIG. 8 in order to only set zeros in the direction of the dominant interferers or to avoid zeros in the direction of those interferers that lie approximately in the same direction as the desired user and thereby negatively influence the antenna diagram, is exemplified in FIG 8 (in conjunction with Fig. 7) and illustrated in Figs. 9 and 10. While FIG. 7 shows the estimated power angle spectrum of the desired user and the interferer, FIG. 8 illustrates the antenna directivity for this scenario.
  • step 56 of FIG. 6 the estimated, modified power angle spectrum APS k, mod is used to reconstruct the spatial covariance matrix (correlation matrix) R k (f S ) of the mobile radio channel of the downlink of the K users. This is done according to the following procedure:
  • the power angle spectrum can of course not be determined continuously, but only discretely with a certain angular resolution. Extensive computer simulations have shown that a resolution of around one degree is sufficient. This means that the above integral can be replaced by a discrete sum with relatively few summands. The discrete total looks like this: P k, mod ( ⁇ ) here designates the modified power angle spectrum of the kth user.
  • the method described is characterized in that the entire direction information of the mobile radio channel for the Beamforming is used in the downlink without one To commit errors by the duplex frequency, and therefore the same Gain in the downlink of cellular cellular systems with frequency duplex is possible as in time duplex systems.
  • the described technique can be used without restrictions.
  • the spatial covariance matrix or the channel impulse responses used to shape the downlink beam which are also required for detection in the uplink and therefore do not have to be charged extra.
  • the covariance matrices R k of the downlink (R k (f S )) for the k-th subscriber are thus obtained, and these are finally obtained in step 60 according to FIG. 5 of the beam shaping, ie the determination of the antenna weights for the downlink.
  • all known algorithms for beam shaping can be used which are based on the knowledge of the spatial covariance matrix.
  • an algorithm is explained as an example, which is a standard algorithm in the literature for calculating the antenna weights in the uplink (see, for example, P. Zetterberg, and B. Ottersten: "The Spectrum Efficiency of a Basestation Antenna Array System for Spatially Selective Transmission ", IEEE Transactions on Vehicular Technology, Vol. 44, pp. 651-660, August 1995).
  • R k (f S ) denotes the covariance matrix of the kth user and Q k (f S ) the covariance matrix of the interference for the kth user at the transmission frequency f S.
  • the weight vector is calculated from this information as the dominant generalized eigenvector of the matrix pair [R k (f S ), Q k (f S )].
  • this method maximizes the ratio of received interference power ratio SNIR k .
  • the ratio of signal power generated for the desired user to interference power generated for the other users is maximized. This problem can be represented mathematically as follows:
  • the covariance matrices are used for detection in the uplink at the receiving frequency and for computing the antenna weights for the downlink the frequency-transformed Covariance matrices (at the transmission frequency of the base station). However, it uses the same algorithm for calculation the complex antenna weights for receiving and transmitting used with the adaptive antenna 1. Because of this, and because the spatial covariance matrix for reception in the uplink Generally used is this procedure for beam shaping for the downlink of systems with frequency duplex very simple, and compared to Upward distance only the frequency transformation of the spatial Additional covariance matrix, as shown schematically in FIG. 11 at 70 is shown.
  • FIG. 11 shows the structure of the signal processor unit 2 for calculating the antenna weights for the adaptive antenna 1, the received signals being indicated schematically at 71.
  • the unit for estimating the upward covariance matrices R k is illustrated and the beam shaping unit is shown at 73.
  • the antenna weights determined are designated W k (f S ) for the downlink and W k (f E ) for the uplink.

Claims (14)

  1. Procédé de mise en forme de faisceau pour un réseau d'antennes adaptatif contenant plusieurs éléments d'antenne (1.1 à 1.M) dans la voie descendante de systèmes duplex en fréquence, des pondérations d'antennes (Wk (fS)) pour les éléments d'antenne (1.1 à 1.M) pour l'émission dans la voie descendante étant déterminées à l'aide de l'information de direction de la voie montante, caractérisé en ce que les pondérations d'antennes (Wk (fS)) pour l'émission dans la voie descendante sont déterminées à l'aide du spectre angulaire de puissance (APSk) de la voie montante des différents utilisateurs (B1 à BK), le spectre angulaire de puissance (APSk) étant modifié par la suppression de plages angulaires non souhaitées.
  2. Procédé selon la revendication 1, caractérisé en ce que le spectre angulaire de puissance (APSk) est estimé en utilisant une séquence de signal connue (Sk) du signal d'émission, par exemple le code d'étalement ou le mi-ambule.
  3. Procédé selon la revendication 1 ou 2, caractérisé en ce que le spectre angulaire de puissance (APSk) est estimé à l'aide des matrices de covariances spatiales (Rk (fE)) de la voie montante des différents utilisateurs (B1 à BK).
  4. Procédé selon la revendication 3, caractérisé en ce que le spectre angulaire de puissance (APSk) est estimé à l'aide des moyennes des matrices de covariances spatiales (Rk (fE)) de la voie montante des différents utilisateurs.
  5. Procédé selon l'une des revendications 1 à 4, caractérisé en ce que la matrice de covariance spatiale (Rk (fS)) respective de la voie descendante est déterminée à l'aide du spectre angulaire de puissance (APSk) modifié des différents utilisateurs.
  6. Procédé selon la revendication 5, caractérisé en ce que la matrice de covariance spatiale (Rk (fS)) de la voie descendante est déterminée à l'aide de la moyenne du spectre angulaire de puissance (APSk) modifié.
  7. Procédé selon la revendication 5, caractérisé en ce que la moyenne de la matrice de covariance spatiale (Rk (fS)) de la voie descendante est utilisée pour le calcul des pondérations d'antennes (Wk (fS)) pour l'émission.
  8. Dispositif de mise en forme de faisceau pour un réseau d'antennes adaptatif contenant plusieurs éléments d'antenne (1.1 à 1.M) dans la voie descendante de systèmes duplex en fréquence, avec une unité à processeur de signal (2) destinée à déterminer des pondérations d'antennes (Wk (fS)) pour les éléments d'antenne (1.1 à 1.M) pour l'émission dans la voie descendante à l'aide de l'information de direction de la voie montante, caractérisé en ce que l'unité à processeur de signal (2) est conçue pour déterminer les pondérations d'antennes (Wk (fS)) pour l'émission dans la voie descendante à l'aide du spectre angulaire de puissance (APSk) de la voie montante des différents utilisateurs (B1 à BK) tout en modifiant ledit spectre angulaire de puissance par la suppression de plages angulaires non souhaitées.
  9. Dispositif selon la revendication 8, caractérisé en ce que l'unité à processeur de signal (2) reçoit pour l'estimation du spectre angulaire de puissance (APSk) une séquence de signal connue (Sk) du signal d'émission, par exemple le code d'étalement ou le mi-ambule.
  10. Dispositif selon la revendication 8 ou 9, caractérisé en ce que l'unité à processeur de signal (2) est conçue pour l'estimation du spectre angulaire de puissance (APSk) à l'aide des matrices de covariances spatiales (Rk (fE)) de la voie montante des différents utilisateurs (B1 à BK).
  11. Dispositif selon la revendication 10, caractérisé en ce que l'unité à processeur de signal (2) forme les moyennes des matrices de covariances spatiales (Rk (fE)) de la voie montante.
  12. Dispositif selon l'une des revendications 8 à 11, caractérisé en ce que l'unité à processeur de signal (2) est conçue pour la détermination de la matrice de covariance spatiale (Rk (fS)) respective de la voie descendante à l'aide du spectre angulaire de puissance (APSk) modifié des différents utilisateurs (B1 à BK).
  13. Dispositif selon la revendication 12, caractérisé en ce que l'unité à processeur de signal (2) forme, pour la détermination de la matrice de covariance spatiale (Rk (fS)) respective de la voie descendante, la moyenne du spectre angulaire de puissance (APSk) modifié.
  14. Dispositif selon la revendication 12, caractérisé en ce que l'unité à processeur de signal (2) forme, pour le calcul des pondérations d'antennes (Wk (fS)) pour l'émission, la moyenne de la matrice de covariance spatiale (Rk (fS)) de la voie descendante.
EP00913950A 1999-03-26 2000-03-24 Procede et dispositif de mise en forme de faisceau Expired - Lifetime EP1166393B1 (fr)

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AT56599 1999-03-26
AT0056599A AT407807B (de) 1999-03-26 1999-03-26 Verfahren und vorrichtung zur strahlformung
PCT/AT2000/000072 WO2000059072A1 (fr) 1999-03-26 2000-03-24 Procede et dispositif de mise en forme de faisceau

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EP1166393A1 EP1166393A1 (fr) 2002-01-02
EP1166393B1 true EP1166393B1 (fr) 2004-07-14

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US7054664B2 (en) * 2003-10-30 2006-05-30 Lucent Technologies Inc. Method and apparatus for providing user specific downlink beamforming in a fixed beam network
US7324582B2 (en) * 2004-01-07 2008-01-29 General Dynamics C4 Systems, Inc. System and method for the directional reception and despreading of direct-sequence spread-spectrum signals
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CN100423602C (zh) * 2005-05-17 2008-10-01 上海原动力通信科技有限公司 应用于同频组网的波束赋形实现方法
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CN102377465B (zh) * 2010-08-10 2014-04-09 鼎桥通信技术有限公司 下行波束赋形方法及装置
JP5667887B2 (ja) * 2011-01-07 2015-02-12 日本電産エレシス株式会社 アンテナ装置及びレーダ装置
CN102394679B (zh) * 2011-09-29 2014-07-02 西安空间无线电技术研究所 一种星载多波束天线系统发射通道实时校准系统和方法
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JP2002540706A (ja) 2002-11-26
AU3543100A (en) 2000-10-16
AT407807B (de) 2001-06-25
WO2000059072A1 (fr) 2000-10-05
EP1166393A1 (fr) 2002-01-02
BR0009306A (pt) 2001-12-18
CN1346525A (zh) 2002-04-24
ATA56599A (de) 2000-10-15
US6606058B1 (en) 2003-08-12
DE50007073D1 (de) 2004-08-19

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