Classifications

• • G—PHYSICS
  • G06—COMPUTING; CALCULATING OR COUNTING
  • G06K—GRAPHICAL DATA READING; PRESENTATION OF DATA; RECORD CARRIERS; HANDLING RECORD CARRIERS
  • G06K19/00—Record carriers for use with machines and with at least a part designed to carry digital markings
  • G06K19/06—Record carriers for use with machines and with at least a part designed to carry digital markings characterised by the kind of the digital marking, e.g. shape, nature, code
  • G06K19/067—Record carriers with conductive marks, printed circuits or semiconductor circuit elements, e.g. credit or identity cards also with resonating or responding marks without active components
  • G06K19/07—Record carriers with conductive marks, printed circuits or semiconductor circuit elements, e.g. credit or identity cards also with resonating or responding marks without active components with integrated circuit chips
• • G—PHYSICS
  • G06—COMPUTING; CALCULATING OR COUNTING
  • G06K—GRAPHICAL DATA READING; PRESENTATION OF DATA; RECORD CARRIERS; HANDLING RECORD CARRIERS
  • G06K7/00—Methods or arrangements for sensing record carriers, e.g. for reading patterns
  • G06K7/10—Methods or arrangements for sensing record carriers, e.g. for reading patterns by electromagnetic radiation, e.g. optical sensing; by corpuscular radiation
  • G06K7/10009—Methods or arrangements for sensing record carriers, e.g. for reading patterns by electromagnetic radiation, e.g. optical sensing; by corpuscular radiation sensing by radiation using wavelengths larger than 0.1 mm, e.g. radio-waves or microwaves
  • G06K7/10316—Methods or arrangements for sensing record carriers, e.g. for reading patterns by electromagnetic radiation, e.g. optical sensing; by corpuscular radiation sensing by radiation using wavelengths larger than 0.1 mm, e.g. radio-waves or microwaves using at least one antenna particularly designed for interrogating the wireless record carriers
  • G06K7/10336—Methods or arrangements for sensing record carriers, e.g. for reading patterns by electromagnetic radiation, e.g. optical sensing; by corpuscular radiation sensing by radiation using wavelengths larger than 0.1 mm, e.g. radio-waves or microwaves using at least one antenna particularly designed for interrogating the wireless record carriers the antenna being of the near field type, inductive coil
• • G—PHYSICS
  • G06—COMPUTING; CALCULATING OR COUNTING
  • G06K—GRAPHICAL DATA READING; PRESENTATION OF DATA; RECORD CARRIERS; HANDLING RECORD CARRIERS
  • G06K19/00—Record carriers for use with machines and with at least a part designed to carry digital markings
  • G06K19/06—Record carriers for use with machines and with at least a part designed to carry digital markings characterised by the kind of the digital marking, e.g. shape, nature, code
  • G06K19/067—Record carriers with conductive marks, printed circuits or semiconductor circuit elements, e.g. credit or identity cards also with resonating or responding marks without active components
  • G06K19/07—Record carriers with conductive marks, printed circuits or semiconductor circuit elements, e.g. credit or identity cards also with resonating or responding marks without active components with integrated circuit chips
  • G06K19/0723—Record carriers with conductive marks, printed circuits or semiconductor circuit elements, e.g. credit or identity cards also with resonating or responding marks without active components with integrated circuit chips the record carrier comprising an arrangement for non-contact communication, e.g. wireless communication circuits on transponder cards, non-contact smart cards or RFIDs
• • G—PHYSICS
  • G07—CHECKING-DEVICES
  • G07B—TICKET-ISSUING APPARATUS; FARE-REGISTERING APPARATUS; FRANKING APPARATUS
  • G07B15/00—Arrangements or apparatus for collecting fares, tolls or entrance fees at one or more control points
• • G—PHYSICS
  • G07—CHECKING-DEVICES
  • G07C—TIME OR ATTENDANCE REGISTERS; REGISTERING OR INDICATING THE WORKING OF MACHINES; GENERATING RANDOM NUMBERS; VOTING OR LOTTERY APPARATUS; ARRANGEMENTS, SYSTEMS OR APPARATUS FOR CHECKING NOT PROVIDED FOR ELSEWHERE
  • G07C9/00—Individual registration on entry or exit
  • G07C9/20—Individual registration on entry or exit involving the use of a pass
  • G07C9/28—Individual registration on entry or exit involving the use of a pass the pass enabling tracking or indicating presence

Definitions

• the invention relates to contactless communication techniques between a portable object and a terminal.
• each user is provided with a portable object of the "contactless card” or “contactless badge” type, which is an object capable of exchanging information with a fixed (or possibly mobile) "terminal". approaching the badge of the latter so as to allow a non-galvanic mutual coupling ("terminal" will be the term used in the present description to designate the data transmitter / receiver terminal able to cooperate with portable objects).
• this coupling is carried out by varying a magnetic field produced by an induction coil (technique naked under the name of "induction process").
• the terminal includes an inductive circuit excited by an alternating signal which produces an alternating magnetic field in the surrounding space.
• the portable object in this space detects this field and return modulates the load of the portable object coupled to the terminal; this variation is detected by the terminal, thus establishing the bidirectional communication sought.
• EP-A-0 424 726 describes such a mixed card capable of communication with or without contact. In this card, communication is established selectively via contact pads or via coils, depending on the presence of an electrical voltage on the pads or on the coils.
• a disadvantage of this system is that piloting as a function of the presence of a voltage proves difficult to apply in practice.
• the appearance of parasites can disturb its operation.
• a parasitic depletion of the supply voltage to the contacts may cause the accidental selection of the communication channel by coil and activation of a shunt regulator, wherein while circulating an excessive current when it is put in parallel with the power contacts.
• This system is also unsuitable for selecting the starting and operating conditions of the processing circuit, the disappearance of the contact power supply causing a parasitic starting. Selection at start-up based on information from the comparison of the two power sources presents the difficulty of locking the selection at the right time under all power-up conditions.
• One of the aims of the present invention is to propose another way of detecting the communication mode to be used and to control various functions of the portable object accordingly.
• the portable object of the invention is of the general type disclosed by EP-A-0,424,726 cited above, namely having a plurality of electrical contacts for communication galvanically with a terminal of a first type having itself a plurality of homologous electrical contacts, as well as a coil for contactless communication with a terminal of a second type emitting a modulated electromagnetic field transmitting data.
• the data transmitted by the terminal being clocked by a clock signal, it comprises clock detector means for modifying the operation of the portable object as a function of the presence or of the absence of a clock signal in the received signal.
• these means clock detectors detect the clock signal in the signal picked up by the coil.
• the portable object in contactless communication mode, is remotely powered by the electromagnetic field received by the coil and the clock signal, and then includes rectifying and filtering means to obtain a DC supply voltage. for the object in contactless communication mode from the electromagnetic field picked up by the coil, and the detector means receive as input the signal present between the coil and the rectification and filtering means (where its amplitude is the greatest) .
• the clock signal can be extracted at the same place.
• the clock can be defined by the frequency of the carrier received, divided into the means for extracting the clock.
• the data itself is preferably extracted downstream from the rectification and filtering stage, so that the demodulation of the signal is more stable, in particular in the case of amplitude modulation.
• Means for demodulating the signal picked up by the coil, so as to extract communication data therefrom in particular amplitude demodulating means operating on the signal delivered in exit from the rectification and filtering stages;
• Means for transmitting data from the portable object to the terminal in contactless mode by modulating the load at the terminals of the coil advantageously, the modulation is then a modulation of a subcarrier produced by division of the fre- quency of the clock supplied by the detection means and / or the circuit is capable of two modes of operation in nominal consumption and low consumption , and means are provided for placing the circuit in low consumption mode before the data transmission means begin to operate said modulation;
• the clock detector means can control communication and / or signal processing and / or data processing protocols received.
• the signal presence / absence clock can be operated in several ways, for example by providing the signal in- HIBITION a regulator that stabilizes the DC voltage supply so that the controller operates that in contactless mode. The risk of inadvertent activation of this shunt regulator is eliminated. Also, this signal can be used in the development of the activation signal of the processing circuit and the selection of its clock signal. Finally, the communication and signal processing protocols can differ between the contact and contactless communication modes and the presence / absence of a clock can be used to control the protocols used.
• an analog switch can be also provided for interrupting the li-, aison communications mode by contacts, thus allowing to avoid interpreting as parasites of the data appearing on the input (coil or contacts) unused.
• a stabilizing stage comprising a shunt regulator element mounted in shunt between the supply terminals of the circuit to be supplied and associated with a resistive component connected in series in the circuit supply line, the shunt regulating element taking and deriving a variable fraction of the circuit supply current so that the resistive element and the shunt regulating element dissipate any additional energy not necessary for the operation of the circuit, so as to correlate, stabilize the supply voltage at the terminals of the circuit, limit the voltage excursion at the terminals of the element tuned upstream and prevent variations in the current consumed influence upstream on the amplitude of the signal to be demodulated.
• means may be provided to inhibit selective tively and temporarily the operation of the shunt regulator, in particular in response to the detection of a type of communication via contacts.
• the entire electronic circuit of the portable object with the exception of the winding of the tuned element, is very advantageously produced in integrated monolithic technology.
• FIG. 1 is a block diagram of a system according to the invention, in its most general aspect, comprising a terminal and a tative Por- object in the field of this terminal.
• FIG. 2 shows a particular embodiment of the portable object of FIG. 1.
• FIG. 3 details the regulator circuit of the diagram in Figure 2.
• FIG. 6 is a detailed example of an embodiment of the demodulator circuit of FIG. 5.
• Figure 7 details the clock extractor circuit of the diagram in Figure 2.
• Figure 8 is a series of timing diagrams explaining how the portable object is remotely powered and from which the clock signal is extracted.
• Figure 9 is a series of timing diagrams explaining the transmission of information from the terminal to the object.
• Figure 10 is a series of waveform diagrams explaining the transmission of information from the object to the terminal.
• FIG. 11 shows the different switches operated in a mixed card between the two contact / contactless modes of operation.
• the reference 100 designates a terminal, which can be coupled with a portable object 200 placed in its vicinity .
• the terminal includes a transmission coil 102 which, associated with a capacitor such as 104, forms a tuned circuit 106 intended to generate a modulated magnetic induction field.
• the tuning frequency of circuit 106 is for example 13.56 MHz, a value of course in no way limiting, this particular choice simply due to the fact that it corresponds to a value authorized by European standards for communication and remote power supply functions . In addition, this relatively high value makes it possible to design circuits with coils having few turns, therefore easy and inexpensive to produce.
• the tuned circuit 106 is supplied from a high-frequency continuous wave oscillator 108 and, for modulation, from a mixer stage 108 controlled by the signals to be transmitted TXD from a digital circuit 112.
• the operation of circuit 112 and in particular the sequencing of signals TXD, is clocked by a circuit 114 producing a clock signal CLK.
• the reception stages which extract the data received RXD from the signal taken from the terminals of the coil 102, comprise a high-frequency demodulator circuit 116 as well as a sub-carrier demodulator circuit 118 when one has chosen, as is will indicate below, to use a subcarrier modulation in the portable object ⁇ terminal direction (this technique is of course in no way limiting, the modulation can also be done in baseband).
• the portable object 200 includes a coil 202 co-operating with an electronic circuit 204 which advantageously is made of fully integrated monolithic technology so as to have an object of small dimensions, typically in the format "map credit ' '; the coil 202 is for example a printed coil and all of the circuits 204 are produced in the form of a specific integrated circuit (ASIC).
• ASIC specific integrated circuit
• the coil 202 forms with a capacitor 206 a resonant circuit 208 tuned to a given frequency (for example 13.56 MHz) allowing the bidirectional exchange of data with the terminal by the technique called "by induction" as well as the remote supply by the field magnetic picked up by the coil 202, that is to say the same coil as that used for the exchange of information.
• a given frequency for example 13.56 MHz
• the alternating voltage collected at the terminals of the tuned circuit 208 is applied to a single or full alternating rectifier stage 210, then to a filtering stage 212, to give a filtered rectified voltage b.
• the portable object also includes a digital processing stage 214, typically made from a microprocessor, memories RAM, ROM and EPROM and interface circuits.
• nant Downstream of the rectification 210 and filtering 212 stages are mounted in parallel a number of specific stages, including nant:
• This stabilizer stage 216 can be a conventional type voltage stabilizer or, as a variant (but not limited to), a specific circuit which will be described below with reference to FIGS. 2 and 3. - a demodulator stage 218 receiving as input signal b and outputting a demodulated signal e applied to the RXD data input of digital circuit 214.
• This demodulator can in particular be a demodulator with amplitude variation detection and / or with variable threshold, as will be explained in more detail below with reference to FIGS. 4, 5 and 6.
• an extractor stage clock 220 receiving as input the signal collected at the terminals of the tuned circuit 208 and outputting a ç applied to the clock input CLK of the digital circuit signal 214.
• the clock extractor stage of 220 can be placed either upstream of the rectification 210 and filtering stages 212, as illustrated, or downstream of these stages, that is to say operate on the signal b instead of the signal a; this latter variant is less advantageous, however, insofar as the clock extractor will then have to have greater sensitivity to compensate for the smoothing of the input signal by filtering.
• a modulator stage 222 which operates, in itself known, by "charge modulation", a technique consisting in varying in a controlled manner the current consumed by the tuned circuit 208 situated in the surrounding magnetic field generated by the terminal.
• This modulator circuit 222 comprises a resistive element 224 (added resistance or, in monolithic technology, MOS type component without grid acting as a resistance) in series with a switching element 226 (MOS transistor) controlled by the modulation signal f present on the TXD output of digital circuit 214.
• the modulator stage 222 instead of being placed downstream of the rectification 210 and filtering 212 circuits, can also be placed upstream of these circuits, as illustrated at 222 ′ in FIG. 1, it is ie directly across the resonant circuit 208.
• the general structure and proposed, wherein the demodulator stage 218 is located downstream of the recovery stages 210 and filter 212, has the advantage of being less sensitive to instantaneous variations in the signal. Indeed, in the case of a remotely powered portable object, the fact of operating the demodulation on a rectified and filtered signal to reduce the effects of the instantaneous power of the energy changes in a cycle of oscillation.
• FIG. 2 a particular embodiment of the structure of Figure 1, which is in particular characterized by a particular structure given to the floor controller 216 which, as will be explained in more detail later, a floor type "shunt regulator" with a shunt component 228 for deriving a controlled manner the supply current of the digital circuit 214, therefore mounted in parallel between the terminals VCC and GND, combined with a 230 series resistive element placed in the VCC supply line upstream of the regulator component 228.
• a floor type "shunt regulator” with a shunt component 228 for deriving a controlled manner the supply current of the digital circuit 214, therefore mounted in parallel between the terminals VCC and GND, combined with a 230 series resistive element placed in the VCC supply line upstream of the regulator component 228.
• the shunt 228 can advantageously be a Zener diode or, preferably, a component or integrated functionally equivalent to a Zener diode, for example a component of the LM185 / LM2S5 / LM385 series from National Semiconductor Corporation, which is a component forming reference reference. voltage (fixed or adjustable voltage as appropriate), with a bias current of only 20 ⁇ A, a very low dynamic impedance and a range of operating currents from 20 ⁇ A to 20 mA.
• Component 228 can also be a monolithic equivalent, integrated on the ASIC, of such a voltage reference component.
• Figure 3 depicts one particular embodiment of this circuit 216 with a component of the type described above in which the voltage reference input 234 is biased to a predetermined value by a voltage divider 236, 238 connected between VCC and ground.
• the resistive element 230 can be an added resistance or, advantageously, an integrated monolithic component, for example (as for the component 224) an MOS element acting as a resistance.
• a switching component such as a MOS transistor 240, which is maintained by passing normal func- tioning by applying a signal INH / to its gate.
• This transistor can be switched to the off state by applying a simple INH control signal (in particular a software command from the computing circuit 214) which has the effect of inhibiting the operation of the shunt regulator, the circuit behaving then as if it had been omitted.
• This possibility of inhibiting the shunt regulator can in particular be used when it is desired to supply the microprocessor with a high voltage without risk of destroying the regulator stage.
• the amplitude demodulator stage 218 will now be described in more detail, with reference to FIGS. 4 to 6.
• This demodulator amplitude is a circuit suitable for processing modulated signals with a low modulation depth.
• the expression “shallow modulation depth” or “weak modulation” will be understood to mean a modulation whose rate is typically less than or equal to 50%, preferably less than 20%, the “rate” being defined as being the ratio
• FIG. 4 illustrates a first possible variant embodiment, where the demodulator is an adaptive variable threshold demodulator.
• the circuit comprises, after an optional low-pass filtering stage 242, a comparator 244, preferably with hysteresis, whose positive input receives the signal b to be demodulated (if necessary filtered by stage 242) and whose negative input receives this same signal b, but after crossing an RC stage 246, 248 acting as an integrator.
• the comparison is thus made between, on the one hand, the instantaneous value of the signal and, on the other hand, an average value of this signal, constituting the variable comparison threshold.
• FIG. 5 illustrates a second possible variant embodiment of the demodulator 218, which in this case is a demodulator sensitive to amplitude variations.
• the signal b is applied to a stage CR 250, 252 acting as a differentiator.
• the output signal is applied to the positive terminal of comparator 244 (here again preferably with hysteresis) whose negative input is connected to a fixed potential, for example ground.
• the demodulator is sensitive to variations in the amplitude (due to the differentiating stage), independently of the average value of the signal; it is only the variations of this average value that the comparator detects.
• FIG. 6 gives a more detailed example of an embodiment of such a demodulator circuit with detection of amplitude variations.
• the low-pass filter 242 consisting of the resistor 252 and the capacitor 254
• the series capacitor 250 acting as a differentiator in combination with the resistors 256 to 264.
• the signal thus differentiated is applied to two symmetrical comparators 244, 266 of which the outputs act on two flip-flops 268, 270 mounted in a flip-flop so as to produce two symmetrical signals RXD and RXD / shaped appropriately.
• FIG. 7 illustrates an exemplary embodiment of the extractor and clock detector circuit 220.
• This circuit receives as input a signal taken from the terminals of the resonant circuit 208 and applied to the differential inputs of a hysteresis comparator 272 which supplies the clock signal CLK.
• the clock signal is also applied to two inputs of an EXCLUSIVE OR gate 274 directly on one of the inputs, and through an RC circuit 276, 278 on the other input.
• This RC circuit which introduces a delay in the transmission of the received signal, is chosen with a time constant of the order of l / 4f CLK (c K e ing the clock frequency generated by the circuit 114 of the terminal 100).
• the output signal from gate 274 is then averaged by an RC circuit 280, 282 whose time constant is much greater than l / 2.f CLK (preferably of the order of l / f L ⁇ ) and then applied to one of the inputs of a comparator 284 for comparison with a fixed threshold S.
• the clock signal CLK allows the appropriate timing of the digital processing circuit 214, while the output of the comparator 284 gives a signal PRSCLK indicative of the presence or not of a clock signal.
• the PRSCLK signal presence / absence of the clock signal is advantageously used to signal to the digital circuit that the object is in a "contactless” type environment and decide on corresponding actions such as selection of the appropriate communication protocol, activation of the shunt regulator, PRSCLK being used to produce INH / (see description above with reference to figure 3), etc.
• FIG. 11 presents in detail the various switches which are thus automatically operated between the "contactless” and “contactless” modes.
• Contacts 286 are the CLK (clock), GND (ground), I / O (data), VCC (power) and RST / (reset) contacts of ISO 7816-3, which will be referred to for more details.
• the various switches 288 to 296 are all represented in the "contact" position (referenced '0'), default position, their toggle- ment to the "contactless” position (referenced 1 ') being controlled by the signal PRSCLK delivered by the circuit 220, revealing the presence of a clock signal coming from the rectifying and filtering means.
• the extraction of a clock signal is also particularly advantageous when it is desired to achieve a modulation not in baseband but modulated subcarrier as the subcarrier can easily be generated by dividing the clock frequency.
• the digital circuit 214 then adds the subcarrier thus generated to the data to be transmitted to produce the signal TXD applied to the charge modulator circuit 222.
• the tuned circuit 208 captures part of the magnetic energy produced by the terminal.
• the corresponding alternating signal a illustrated in FIG. 8, is rectified by block 210 and filtered by capacitor 212, to give a filtered rectified voltage b illustrated in FIG. 8.
• a rectified and filtered voltage is thus obtained having a peak voltage of the order of 8.5 V.
• the amplitude of the voltage a, and therefore of the voltage sion b very much depends on the distance between object and terminal, the amplitude being all the more important as the object is near the terminal.
• the regulator stage 216 intervenes to compensate for these variations, by delivering to the digital circuit 214 a stable voltage, typically of the order of 3 V (timing diagram d of FIG. 8).
• the voltage in b when one is far enough from the terminal, almost at the range limit, the voltage in b will be fairly close to the required value of 3 V, the voltage drop between b and d will be low, the current passing through the shunt 228 will also be very weak and almost all of the current delivered by the supply circuit will be used to supply the digital circuit 214. It will be noted that, in this case, the current flowing through shunt 228 may be as low as a few microamps only (minimum bias current).
• the voltage in b will be high, the potential difference between b and d will also be significant (several volts), and the current passing through the shunt 228 will be high, the element resistive 230 and the shunt 228 dissipating the excess energy.
• the shunt regulator stage provides several advantages within the framework of the circuit that has been described.
• the capacitor 206 of the tuned circuit 208 is an element produced in integrated monolithic technology, since the risks of breakdown due to overvoltages are thus avoided. Indeed, given the geometric constraints of the integrated circuit, it is not possible to produce capacitors having high breakdown voltages. Or the digital circuit 214, which is built around a microprocessor, requires for its power supply a relatively large power, so a level field magnetically that high enough, which could create overvoltages in the tuned circuit if the indicated precautions were not taken.
• the shunt regulator has the effect of equalizing instantaneous variations in the supply current of the digital circuit (the consumption of such a circuit is indeed not constant) and to avoid their repercussions on the functioning of the other organs of the circuit, for communication both from the object to the terminal and from the terminal to the object; in fact, undesirable variations in current or voltage could introduce modulation or demodulation errors.
• the design of the circuit makes it possible to avoid any waste of energy, since the current in shunt 228 is practically zero. Thus, all the available energy captured by the tuned circuit can be used to operate the digital circuit.
• the clock extractor circuit 220 makes it possible to transform the alternating signal picked up at the terminals of the tuned circuit 208 into a series workshop of perfectly calibrated clock pulses.
• the terminal modulates the amplitude of the magnetic field it produces.
• the information sent is binary, this modulation amounts to decrease by a predetermined amount, for example 10%, the signal amplitude.
• a predetermined amount for example 10%
• the signal amplitude Such a reduction corresponds for example to the transmission of a logical '0', the maximum amplitude for a remaining the logic: see Figure 9 is the timing diagram of the signal picked up by the tuned circuit 208.
• the object to the terminal is performed by load variation, that is to say controlled variation of the current consumed by the tuned circuit 208.
• the resistive element 224 is selectively switched by the component 226, the resistance being for example switched when the object wants to send a logical '0', not switched for a logical '0'.
• the resistor When the resistor is switched, that is to say for a logic '0', the voltage a decreases due to the additional load.
• the resistance value is of course chosen so that this voltage drop nevertheless makes it possible to maintain a correct supply of the digital circuit.
• This can for example be achieved by the microprocessor program of the digital circuit which, before starting to send data to the terminal, will place the transmission routine in RAM (whose access consumes little energy) and disconnect the EPROM memory (access to which requires significantly higher energy).
• the digital circuit goes into "low consumption” mode to have a large reserve of current, which will be consumed in the modulation resistance for sending messages to the terminal.

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