EP0233903A1 - Element inductif commande electriquement - Google Patents

Element inductif commande electriquement

Info

Publication number
EP0233903A1
EP0233903A1 EP86904760A EP86904760A EP0233903A1 EP 0233903 A1 EP0233903 A1 EP 0233903A1 EP 86904760 A EP86904760 A EP 86904760A EP 86904760 A EP86904760 A EP 86904760A EP 0233903 A1 EP0233903 A1 EP 0233903A1
Authority
EP
European Patent Office
Prior art keywords
cores
control
winding
current
component
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP86904760A
Other languages
German (de)
English (en)
Inventor
André Kislovski
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Ascom Hasler AG
Original Assignee
Hasler AG
Ascom Hasler AG
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Hasler AG, Ascom Hasler AG filed Critical Hasler AG
Publication of EP0233903A1 publication Critical patent/EP0233903A1/fr
Withdrawn legal-status Critical Current

Links

Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01F—MAGNETS; INDUCTANCES; TRANSFORMERS; SELECTION OF MATERIALS FOR THEIR MAGNETIC PROPERTIES
    • H01F29/00—Variable transformers or inductances not covered by group H01F21/00
    • H01F29/14—Variable transformers or inductances not covered by group H01F21/00 with variable magnetic bias
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01F—MAGNETS; INDUCTANCES; TRANSFORMERS; SELECTION OF MATERIALS FOR THEIR MAGNETIC PROPERTIES
    • H01F29/00—Variable transformers or inductances not covered by group H01F21/00
    • H01F29/14—Variable transformers or inductances not covered by group H01F21/00 with variable magnetic bias
    • H01F2029/143—Variable transformers or inductances not covered by group H01F21/00 with variable magnetic bias with control winding for generating magnetic bias

Definitions

  • the invention relates to an inductive component according to the preamble of claims 1 and 2. Furthermore, it relates to a method for operating and using the component according to the preambles of the other independent claims.
  • Inductive components are generally known as choke coils, inductive resistors, signal transmitters, etc., as are their use in electrical / electronic circuits. Their counterparts as components of such circuits are resistors and capacitors.
  • the decisive size of an inductive component with regard to a useful signal is the relative permeability ⁇ r of its core material, which together with the square of the number of turns n of the winding is proportional to the inductance L of the element.
  • the inductance L is the practically important variable that the circuit technician is interested in.
  • the electrically controllable resistor examples include the electron tube, in particular the pentode, or the field effect transistor.
  • An example of the electrically changeable capacitor is the reverse-biased semiconductor diode.
  • the known electrically controllable inductive components such as variometers, magnetic amplifiers, regulating chokes etc. cannot be compared in their mode of operation with the above-mentioned examples of field effect transistors or semiconductor diodes. They work essentially using nonlinear magnetization curves, with the alternating currents to be controlled passing through a substantial part of the magnetization curve in each wave period and driving the magnetic core into saturation for a longer or shorter period. Here the waveform is changed drastically.
  • the above-mentioned inductive components can therefore be compared more with today's phase-cut controls, for example using a thyristor.
  • the object of the invention is therefore to provide, as a counterpart to the electrically controllable resistors and capacitors, an inductive component for universal use in any electrical / electronic circuit, the inductance L which is effective for any alternating signal is always constant and can nevertheless be varied within wide limits .
  • the inductive component specified by the solution to the problem and the uses found according to the invention open the way for a large number of very different new circuit arrangements, for which there has certainly been a considerable need for a long time, but which have hitherto been virtually impossible to implement.
  • the new inductive component and its uses according to the invention are thus suitable for giving the electrical / electronic circuit technology new possibilities and thus essential impulses.
  • FIG. 13 Schematic representation of an inventive use of the component according to the previous figures.
  • FIG. 1 shows, purely schematically and in general, an inductive component 10 which can be controlled electrically via a control input 16.
  • the component 10 comprises a ferromagnetic core 9 and an induction winding 15. against its two signal connections 14, the component 10 has an inductance L which is independent of the shape, amplitude and frequency of the useful signal S which is applied to the signal connections 14.
  • the inductance L is thus a real constant, the value of which is however via an electrical control signal which is applied to the signal input 16, i.e. can be varied within wide limits, in particular by means of a control current I.
  • the variability, adjustability or controllability of the inductive component 10 is indicated in FIG. 1 by an arrow which crosses the core 9 and the induction winding 15.
  • the inductive component 10 shown forms a real, electrically controllable component for the construction of any electrical and / or electronic circuits, the counterparts of which are electrically controllable resistors and electrically controllable capacitors.
  • the Inductance L of the device 10 is therefore analogous to understand how the resistance value R of a 'device' variable resistor 'and the capacitance C of a component "controllable capacitor". Like these sizes R and C, the size L of the component 10 is - it should be emphasized again - signal-independent.
  • FIG. 2 shows the dependence of the magnetic flux density B " on the magnetic field strength H for a core 9 made of a suitable ferromagnetic material, in particular a ferrite. This dependence is well known as a magnetization curve or hysteresis curve.
  • the curve of FIG. 2 is especially around the curve of a soft magnetic material in which the two arms of the hysteresis essentially coincide, that is to say are largely identical for increasing and decreasing field strength IT.
  • the total magnetic field strength T which is composed of a
  • Nonlinearity between b and h means and the mathematical expression for the stated inconsistency of the relative permeability ⁇ is ⁇ ⁇ .
  • the operating point A should be selected in a linear area of the magnetization curve.
  • a second linear region of the magnetization curve lies with large values of H, known as saturation.
  • the relative permeability ⁇ is very low, i.e. their value becomes approximately 1 and thus corresponds only to the value of non-magnetic or weakly magnetic substances.
  • the saturation range is therefore viewed as uninteresting from a conventional point of view and, apart from special cases, remains ignored. In special cases, the saturation range is used e.g. to trigger signals that indicate that saturation has been reached.
  • An example of this is the device according to US 3541 428 (F.C. Schwarz, Unsaturating saturable core transformer).
  • the core 9 is initially split into two identical cores 11 and 12, each with half the cross section of the core 9. Furthermore, each of these partial cores is provided with an induction winding, both of which have half the number of turns as the induction winding 15 of the component 10 described so far.
  • the cores 11 and 12 thus have identical properties, but are operated differently. This is shown in FIG. 3. Analogously to FIG. 2, the total field strength T of the core 11 and that of the core 12 is plotted on the abscissa and the total flux densities B ′′ accordingly on the ordinate.
  • the cores 11 and 12 have the same core material and the same core geometry, the same course of the two magnetization curves as the core 9 of FIG. 2.
  • the ordinate is placed through this working point A ⁇ , which means a shift of the abscissa by the amount HAI nacn ün s. This is permissible and has no physical consequence.
  • a second control current I also sets an operating point A in the second core 12, which, however, in contrast to the operating point Ai of core 11, does not lie in the 1st quadrant but in the 3rd quadrant of the illustration. Furthermore, the associated abscissa is shifted to the right by the amount HA of the assigned bias field strength, so that both operating points Ai and A lie on the same ordinate. Finally, it is ensured that the amount of HI is equal to H 2.
  • Fig. 2 bi a ⁇ «h + a2 * h 2 + a3 « h 3 + a4 « h 4 + ...
  • -b 2 a ⁇ (-h) + a2 (-h) 2 + a 3 (-h) 3 + a (-h) 4 + ...
  • the quasi-linear relationship between b and h at the total working point A is entered in FIG. 3 with the reference number 18.
  • Any desired signal S for example a square wave signal of 1.7 V ss , a pulse duty factor of 5 to 2 and a frequency of 37.6 kHz
  • the inductance L acting here is proportional to the respective one , given by b and h permeability ⁇ A, ie proportional to the slope 2a ⁇ of the relationship 18 of b and h.
  • the magnetization curves of the two cores 11, 12 shift in opposite directions along the abscissa H.
  • the operating points Ax and A2 on the ordinate either slide in opposite directions or from.
  • a changed slope 2a ⁇ arises in the overall operating point A, which represents a correspondingly changed inductance value L for the useful signal S mentioned.
  • the slope of the magnetization curve fluctuates considerably from zero to deep saturation.
  • the symmetrical working point setting Ax, A2 shown allows the inductance value L to be varied in any case in a ratio of at least 1: 100. With certain core materials, a ratio of 1: 1000 can easily be achieved.
  • the control takes place via the control currents I ⁇ and I and the associated premagnetization + H or -H of the cores 11, 12.
  • the size of the useful signals S must be adapted to this area. This means that the signal field strength h of the respective useful signal S is always small compared to the variation range in which the bias field strengths H and -H can be set. The amplitude of a useful signal S must therefore always be so small that it is far from sufficient to drive the cores 11, 12 into saturation. This should also be expressed by choosing the lowercase letters h for the signal field strength and b for the Signal flux density compared to the capital letters H and B of the corresponding pre-magnification values.
  • the magnetization curve of the core material to be used is subject to the condition that the entire area is curved as uniformly as possible and without a saturation kink.
  • the Taylor series b a ⁇ «h + a2 * h2 + ... this means that in each working point Ax or A2 the factor ax of the first link is as large as possible and the factors a2, 83, a 4 ... of the other Links should be comparatively small as possible.
  • the first derivative dB * / dl ⁇ f (), it means that the derivative should have as few distinct turning points as possible.
  • a well-suited material that is also suitable for high frequencies is, for example, the material "H” from Magnetics, which has an A ⁇ _ value of around 18000-10 "with a toroidal core 22.1 x 13.71 x 6.35" 9 H / w2.
  • each core can be composed of two or more partial cores, whereby the total cross-sections of all partial cores in the pair must be the same .
  • the sub-cores can be combined concentrically or axially.
  • two or more pairs of cores 11, 12 can be used which have different core material. This creates a superposition of different magnetization curves, which, however, is symmetrical overall for the control currents I ⁇ and I2 and the resulting operating points Aj and A2.
  • FIG. 5 shows schematically two possibilities for the very simple physical structure, which is well known in terms of illustration, but not functionally, for example from that already cited US 3 541428 or from US 2 802 186 (GH Dewitz, Saturable core apparatus).
  • the component 10 comprises two ferromagnetic cores 11 and 12, which are identical in terms of their geometry and the core material and are ring-shaped and are magnetically independent of one another. Furthermore, the component 10 comprises an induction winding 15, which consists of two partial windings 15.1 and 15.2 composed, which are connected in series, have the same number of turns and each wind around one of the cores 11, 12 individually in the same winding direction.
  • the component 10 finally includes a control winding 17, which also consists of two partial windings 17.1 and 17.2 composed, which are connected in series, which have the same number of turns and also each individually one of the cores 11, 12, but one part winding 17.1 in one and the other part winding 17.2 in the other direction. 5b, the component 10 comprises a single control winding 17, which winds around the two cores 11, 12 together.
  • the control currents I ⁇ and I2 for biasing the cores 11 and 12 are inevitably the same, so that the biasing field strengths H and -H are also the same in amount.
  • the direction of the bias fields is in opposite directions in the two cores 11, 12 (indicated by the arrows H and -H), which is an expression of the minus sign (-) of the field strength H in the core 12.
  • the by a useful signal S through the induction winding 15 Signal field strengths h which arise in the cores 11, 12 and overlap the bias fields H or -H are also the same in amount and have the same sense of rotation, which is indicated by the arrows h.
  • the ferromagnetic cores 11, 12 are two identical, coaxially arranged, cylindrical or better toroidal ring cores (in particular ferrite cores), each of which in the is essentially wound uniformly over its entire angular range with a partial winding 15.1 or 15.2 of the same number of turns. These partial windings have opposite winding senses.
  • the control winding 17 is also wound together in a second operation via the coaxially combined cores 11, 12 and their partial windings 15.1, 15.2 uniformly over the entire angular range, as a result of which it mechanically holds the cores 11 and 12.
  • the magnetic fields H and -H have the same direction of rotation, while the signal fields h have opposite directions of rotation in the two cores 11, 12. This is the case the symbols (__) and ⁇ indicated next to the cut surfaces of the cores 11, 12.
  • toroidal cores 11, 12 not only results in a very compact construction from parts available on the market, but also results in optimal electrical properties because the magnetic field H is evenly distributed in a torus and therefore only minimal magnetic scattering occurs.
  • the coupling of the windings 15 and 17 with the cores 11, 12 is also maximum, while the coupling between the cores 11, 12 with each other is again minimal.
  • Such a component 10, constructed from toroidal cores 11, 12, therefore has, in addition to the properties described with reference to FIG. which make it suitable for use at high frequencies up to at least 100 kHz. Above all, this means that there are hardly any harmful interactions between the windings 15 and 17 and / or harmful capacitances on the windings 15 and 17.
  • the windings 15 and 17 are mutually interchangeable with respect to their function. Because of the described
  • the winding 15 - as previously described - as a signal winding and the winding 17 as a control winding.
  • the size and shape of the cores 11, 12, the core material, the number of turns, the wire thickness and the winding area of the windings 15 and 17 can be selected purely according to practical needs which result from the type of use of the respective component 10. They are irrelevant to the basic behavior of the component 10. In particular, instead of being closed in a ring (in particular as a toroidal ferrite core), the cores 11, 12 can in principle also be slit or even rod-shaped. However, due to the then inevitable magnetic stray fluxes, all properties deteriorate so significantly that such a design of a component 10 can hardly be described as meaningful.
  • FIG. 7 shows the symbolic representation for an element 10 corresponding to FIG. 5b.
  • This element 10 has the two cores 11 and 12, both of which interact with the control winding 17, due to the type of winding according to FIG. 5 in opposite directions. This is indicated by the two inverted arrow heads in the cores 11, 12 next to the winding 17.
  • the partial windings 15.1 and 15.2 connected in series have the same winding direction, which is represented by dots next to the partial windings and by the same direction arrowheads in the cores 11, 12 next to the partial windings 15.1, 15.2.
  • FIG. 8 shows the symbolic representation of a component 10 which corresponds to the component of FIG. 6.
  • the partial windings 15.1 and 15.2 have different winding directions, while the winding direction of the control winding 17 is the same for both cores 11, 12.
  • FIG. 9 shows the symbolic representation of a component with two core pairs which are combined in pairs (for example coaxially or concentrically).
  • the control winding 17 wraps around all four cores 11a, 11b, 12a, 12b together with a uniform winding direction.
  • the partial windings 15.1 and 15.2 each wind around two cores 11a, 11b and 12a, 12b with an inverse winding direction.
  • This component corresponds to variant aa) shown. If the core material of the cores 11a, 11b is different from the material of the cores 12a, 12b, the component corresponds to the variant).
  • 10 shows the symbolic representation of a component 10 corresponding to variant bb).
  • This component 10 has two control windings 17a and 17b which, for example, have the same winding direction and different numbers of turns. Both control windings 17a, 17b act, galvanically isolated, on the cores 11 and 12. Such a component 10 thus allows two control currents I a , ⁇ _ to be conveniently superimposed, with complete potential isolation being automatically ensured.
  • FIG. 11 shows the symbolic representation of a component 10 in accordance with variant bc).
  • This element has two pairs of cores Ha, 12a and 11b, 12b of the same or different core material.
  • a control winding 17a or 17b is assigned to each of the pairs, possibly with a different winding direction as shown.
  • the control currents I a and I D allow the core pairs Ha, 12a and 11b, 12b to be magnetized independently, either in the same sense (as shown) or in opposite directions. In this way, interference effects on the control lines can be compensated for and / or a further improved linearization of the respective permeability ⁇ A effective for the useful signal S can be achieved.
  • FIG. 12 shows the symbolic representation of a component 10 corresponding to variant c) with two induction windings 15a and 15b, which can be used, for example, as the primary and secondary winding of a transformer or pulse transformer and can have the same or different number of turns.
  • the component can be used wherever an electrically controllable inductance makes sense in an electrical and / or electronic circuit.
  • Simple examples of a use according to the invention are e.g. a variable inductive resistor or a resonant circuit tunable via its inductance.
  • the component 10 according to FIG. 13 is always connected to a controlled circuit 25 with its induction winding 15 and to a control circuit 27 with its control winding 17 or forms a component of these circuits with these windings in such a way that the control circuit Circuit 27 for the controlled circuit 25 sets a linear inductance L of a value lying between wide limits.
  • induction windings 15a, 15b and / or several control windings 17a, 17b these windings can be connected to different ones Connect inputs of the same circuits 25 or 27 or to corresponding separate circuits.
  • the inductive component 10 Compared to the comparable components controllable resistance R and controllable capacitance C, the inductive component 10 has the essential advantage that its circuits are inherently galvanically isolated. Different potentials in the circuits, e.g. 25 and 27, therefore, do not matter.
  • the component 10 is controlled via any currents I which are not too high in frequency.
  • the direct current the sinusoidal current associated with an alternating voltage network and the pulsating, unsmoothed direct current obtained by rectifying a sinusoidal current.
  • the control can thus act statically or dynamically, but substantial inductive effects of the control winding 17 on the control current I should be avoided.
  • the useful signals S which are preferably high-frequency (frequency greater than approx. 1 kHz) and for which an inductive effect is just desired.
  • a component 10 can be produced using known methods from parts available on the market and is therefore inexpensive. It is insensitive to destructive influences of any kind. Finally, the embodiments according to the invention and practical measures make it adaptable to different types of application, for example to applications in High-frequency range, the conditions in energy converters, the tasks of digital and analog technology, problems with measurement and control technology, etc. In the latter case, the component (10) can serve very cheaply as an actuator for influencing the respective control variable, for example an AC voltage.
  • the signal conversion is in the foreground, e.g. by means of an inductive. Transformer or a transformer.
  • the respective useful signal S is subjected to a variable inductive influence in such a way that the useful signal S itself or a variable derived from it is amplified or weakened to a degree that corresponds to the respective inductive influence.
  • Examples include a potentiometric attenuator for an alternating signal consisting of a series connection of an inductive fixed resistor and a component 10. Or a transformer with a variable, controllable "turn ratio" between the primary and secondary windings, in which the useful signal is more or less attenuated Primary winding is supplied so that the derived variable, ie the voltage across the secondary winding, is correspondingly larger or smaller.
  • a transformer with a variable, controllable "turn ratio" between the primary and secondary windings in which the useful signal is more or less attenuated Primary winding is supplied so that the derived variable, ie the voltage across the secondary winding, is correspondingly larger or smaller.
  • the component 10 forms a fundamentally new component with excellent properties, the possible uses of which are so numerous that they can hardly be shown in detail.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Coils Or Transformers For Communication (AREA)

Abstract

l'élément inductif (10) d'usage universel dans tout circuit électrique ou électronique présente une inductance (L) constante, indépendante du signal, pouvant être commandée électriquement et fortement variable. L'élément (10) est composé de deux noyaux (11, 12) ferromagnétiques indentiques, indépendants magnétiquement l'un de l'autre, en forme d'anneaux fermés, qui portent chacun les parties d'enroulement (15.1, 15.2) d'un enroulement d'induction (15) et ensemble un enroulement de commande (17). Le sens d'enroulement des enroulements (15.1, 15.2, 17) est tel que les champs magnétiques engendrés par les courants circulant dans les enroulements s'affaiblissent mutuellement dans l'un des noyaux (12), mais augmentent dans l'autre noyau (12). L'élément (10) est connecté par son enroulement d'induction (15) à un circuit (25) commandé tandis que son enroulement de commande (17) est relié à un circuit de commande (27); il constitue avec ses enroulement (15, 17) une partie de ces circuits de commande (25, 27). En variant le courant (I) circulant dans l'enroulement de commande (17), le circuit de commande (27) modifie la valeur de l'inductance (L) pour le circuit commandé (25), l'étendue de la variation atteignant au moins le rapport 1:100.
EP86904760A 1985-09-02 1986-08-15 Element inductif commande electriquement Withdrawn EP0233903A1 (fr)

Applications Claiming Priority (4)

Application Number Priority Date Filing Date Title
CH377185 1985-09-02
CH3771/85 1985-09-02
CH486885 1985-11-13
CH4868/85 1985-11-13

Publications (1)

Publication Number Publication Date
EP0233903A1 true EP0233903A1 (fr) 1987-09-02

Family

ID=25693802

Family Applications (1)

Application Number Title Priority Date Filing Date
EP86904760A Withdrawn EP0233903A1 (fr) 1985-09-02 1986-08-15 Element inductif commande electriquement

Country Status (5)

Country Link
US (1) US4853611A (fr)
EP (1) EP0233903A1 (fr)
AU (1) AU6194486A (fr)
CA (1) CA1287099C (fr)
WO (1) WO1987001505A1 (fr)

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Publication number Priority date Publication date Assignee Title
CH670926A5 (fr) * 1986-09-05 1989-07-14 Hasler Ag Ascom
EP0261663B1 (fr) * 1986-09-26 1992-06-17 Hitachi, Ltd. Dispositif à laser avec générateur d'impulsion haute-tension, générateur d'impulsion haute-tension et méthode de génération d'impulsion
JPH0377360A (ja) * 1989-08-18 1991-04-02 Mitsubishi Electric Corp 半導体装置
US6755254B2 (en) 2001-05-25 2004-06-29 Dril-Quip, Inc. Horizontal spool tree assembly
US7161458B2 (en) * 2005-02-22 2007-01-09 Delta Electronics, Inc. Electromagnetic device having independent inductive components
US8178998B2 (en) * 2009-06-30 2012-05-15 Verde Power Supply Magnetically integrated current reactor
US8120457B2 (en) 2010-04-09 2012-02-21 Delta Electronics, Inc. Current-controlled variable inductor
US9343996B2 (en) 2014-02-04 2016-05-17 Pavel Dourbal Method and system for transmitting voltage and current between a source and a load
CN106233403B (zh) * 2014-04-17 2019-12-03 镁思锑技术有限公司 场调节器

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BE639429A (fr) *
DE953713C (de) * 1941-09-04 1956-12-06 Siemens Ag Einrichtung zur Gewinnung einer Wechselspannung aus einer Gleichspannung und einer Grundwechselspannung
US2586657A (en) * 1948-08-24 1952-02-19 Varo Mfg Co Inc Saturable transformer
US2802186A (en) * 1952-04-19 1957-08-06 Cgs Lab Inc Saturable core apparatus
BE527536A (fr) * 1954-03-23 1956-11-09 H Howe Perfectionnements aux appareils de commande electromagnetiques
US2773134A (en) * 1954-05-25 1956-12-04 Westinghouse Electric Corp Magnetic amplifiers
US2782269A (en) * 1955-06-28 1957-02-19 Bell Telephone Labor Inc Magnetic amplifier circuits
DE1069278B (fr) * 1958-09-06 1959-11-19
GB966247A (en) * 1962-01-01 1964-08-06 Westinghouse Electric Corp Electrical inductive apparatus

Non-Patent Citations (1)

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Title
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Also Published As

Publication number Publication date
AU6194486A (en) 1987-03-24
WO1987001505A1 (fr) 1987-03-12
US4853611A (en) 1989-08-01
CA1287099C (fr) 1991-07-30

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