EP0056642A1 - Méthode et circuit pour chauffer, allumer ainsi que pour commander ou régler le courant électrique de lampes de décharge à gaz à basse pression - Google Patents

Méthode et circuit pour chauffer, allumer ainsi que pour commander ou régler le courant électrique de lampes de décharge à gaz à basse pression Download PDF

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Publication number
EP0056642A1
EP0056642A1 EP82100310A EP82100310A EP0056642A1 EP 0056642 A1 EP0056642 A1 EP 0056642A1 EP 82100310 A EP82100310 A EP 82100310A EP 82100310 A EP82100310 A EP 82100310A EP 0056642 A1 EP0056642 A1 EP 0056642A1
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EP
European Patent Office
Prior art keywords
voltage
frequency
low
gas discharge
pressure gas
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Granted
Application number
EP82100310A
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German (de)
English (en)
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EP0056642B1 (fr
Inventor
Gerhard Prof. Dipl.-Phys. Wollank
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Individual
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Individual
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Priority to AT82100310T priority Critical patent/ATE31236T1/de
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    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
    • H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
    • H05B41/295—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices and specially adapted for lamps with preheating electrodes, e.g. for fluorescent lamps
    • H05B41/298—Arrangements for protecting lamps or circuits against abnormal operating conditions
    • H05B41/2981—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y10—TECHNICAL SUBJECTS COVERED BY FORMER USPC
    • Y10S—TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y10S315/00—Electric lamp and discharge devices: systems
    • Y10S315/02—High frequency starting operation for fluorescent lamp

Definitions

  • the invention relates to a method and a circuit arrangement for heating and igniting as well as for controlling or regulating the luminous flux of low-pressure gas discharge lamps, in particular fluorescent lamps, by means of a ballast in which an inverter is generated from a direct voltage that is generated by means of a rectifier from an alternating current supply network generated higher frequency than mains frequency; wherein an LC circuit consisting of a capacitor and a first choke is connected between the inverter output and the low-pressure gas discharge lamp, a second choke is connected in parallel with the low-pressure gas discharge lamp, and the inverter constantly recharges the capacitor at a controllable frequency.
  • Such a circuit arrangement is known for example from US-PS 42 07 497.
  • the known circuit consists of an inverter gas-fed with DC voltage, which is connected by two thyristors connected in series is formed with an anti-parallel diode. From the connection point of the two thyristors, an LC circuit tuned to the inverter frequency leads to the primary winding of an output transformer, to its secondary winding. Up to 40 pieces of fluorescent lamps can be connected via a separate ballast.
  • Each formwork unit consists of an LC circuit in series and a choke or a capacitor parallel to the fluorescent tube. The brightness of the fluorescent lamps is achieved by suitable control of the inverter thyristors and the resulting control of the amplitude of the alternating voltage feeding the fluorescent lamps.
  • a major disadvantage of the known circuit lies in the use of the single LC circuit in the supply line for the primary winding of the transformer.
  • This LC circuit must be dimensioned such that it transmits the electrical power required to supply all connected fluorescent lamps at the specified inverter frequency. In the event of failure of one or more fluorescent lamps, this LC circuit is misaligned so that impermissibly high voltages can arise which destroy the inverter thyrists, breakdown of the insulation of the cables and can endanger the operating and maintenance personnel.
  • iron chokes tuned to the mains frequency are also used as ballasts, which are compensated for with the aid of capacitors.
  • Phase cutters are used to control or regulate the luminous flux.
  • Special fluorescent lamps or fluorescent lamps with ignition aids and additional heating transformers are required for proper operation. Because of the required use of heating transformers, special sockets are also required that contact the fluorescent lamp with screw connections, which makes it very difficult to replace the fluorescent lamps.
  • Such lighting systems generate considerable. loss losses, namely through the upstream iron choke, the heating transformers and the generation of reactive power in the leading edge controller.
  • leading edge controller itself generates radio interference, which must be prevented from spreading on the installation lines with the help of interference suppressors and shields.
  • Fluorescent lamps that are specially designed for operation with variable brightness are almost twice as expensive as normal fluorescent lamps.
  • the present invention is based on the object of specifying a method for heating and igniting and for controlling or regulating the luminous flux of low-pressure gas discharge lamps, in particular fluorescent lamps, with which the power losses can be reduced considerably, the luminous efficiency of the fluorescent lamps increased and a variation in the luminous flux or the illuminance is possible without flickering between about 10% and 100% of the nominal luminous flux, which when switched off change a defective lamp no impermissibly high voltages arise and that can be realized using commercial components.
  • Another advantage results from the control of the luminous flux via the frequency, whereby the preheating of the heating coils and low luminous flux or illuminance at low frequency values, the maximum luminous flux or illumination value at high frequency values are achieved.
  • the fact known per se is exploited here that low-pressure gas discharge lamps emit higher luminous fluxes when fed with alternating voltages of increased frequency with the same power consumption, or that the same luminous fluxes are achieved with reduced electrical power consumption.
  • Another advantage of frequency control is. in the fact that with a suitable adjustment of the chokes and capacitors connected to the low-pressure gas discharge lamp and with increasing brightness of the lamps, the current for preheating the heating coils can also be reduced continuously without the need for mechanical or electronic switching elements.
  • ballast LC element for each low-pressure gas discharge lamp, which is also not tuned to the resonant frequency of the AC voltage supply.
  • the frequency is kept constant at its low value for a certain period of time after the low-pressure gas discharge lamp is switched on until the heating filaments reach their prescribed temperature and then continuously to the luminous flux corresponding to the desired luminous flux Value increased.
  • the ignition voltage required for igniting the gas discharge is only reached after the heating coils have reached their prescribed emission temperature. This significantly increases the life of the fluorescent lamps and eliminates the annoying flickering of the low-pressure gas discharge lamps when they are switched on.
  • Such a circuit arrangement has the advantage that it can be constructed with conventional components and in small dimensions, so that each lamp is on own ballast with an inverter and several chokes and capacitors according to the number of low-pressure gas discharge lamps installed in the lamp.
  • the DC voltage for a large number of such ballasts can be generated centrally and distributed to the individual lights in a simple manner via installation lines.
  • the control voltage that controls the inverters and that determines the luminous flux of the low-pressure gas discharge lamps is generated centrally and is supplied to each ballast as a low-power ignition pulse alternating voltage via a separate line that can run parallel to the direct current supply lines.
  • This circuit arrangement has the advantages that the ignition pulse generator without the ignition pulse alternating voltage With the help of further supply voltages directly converted into firing pulses of suitable shape and power in order to ignite the main thyristors of the inverter, and that the use of thyristors enables very simple, reliable, robust inverters which can operate at a sufficiently high frequency.
  • reverse-conducting thyristors can be switched at frequencies that lie above the hearing range of the human ear, so that the ballasts cannot emit any disturbing sound signals.
  • the. Ignition transformer s a second secondary winding, which delivers a blocking pulse to the control electrode of the other thyristor via a parallel RC element. Ignition of the blocked thyristor due to exceeding the permissible voltage steepness is avoided in this way.
  • This simple measure means that thyristors can also be used in the inverter that are not specially designed for a high permissible voltage steepness.
  • the first inductor in the ballast LC element of each low-pressure gas discharge lamp can be formed with two windings, one winding being arranged in front of and the other winding behind the low-pressure gas discharge lamp.
  • the ballast choke can simultaneously act as a radio interference suppression choke against the radio interference generated in the low-pressure gas discharge lamp itself.
  • the second inductor can advantageously be divided, one inductor in parallel with one each Low pressure gas discharge lamp is arranged.
  • Another possibility in the case of series connection of low-pressure gas discharge lamps is that the second inductor is designed with a plurality of windings, one winding being arranged in parallel with one low-pressure gas discharge lamp.
  • this circuit is useful since the number of components required can be reduced further.
  • a potentiometer is provided for setting the luminous flux setpoint of the low-pressure gas discharge lamp, while an integrating controller is provided for controlling the frequency generator with a defined ramp-up curve.
  • the defined ramp-up curve ensures that - as already mentioned - before the ignition of the low-pressure gas discharge lamp at low frequency, the prescribed heating current flows through the heating filaments, after the ignition of the low-pressure gas discharge lamp the heating current only increases with increasing frequency until about 40% of the nominal luminous flux is reached insignificant and continuously reduced to less than 25% of its initial value when the frequency continues to increase until the nominal luminous flux is reached.
  • the frequency is adjusted in accordance with the optimum characteristic for the low-pressure gas discharge lamps and the lamps themselves achieve their maximum service life in this way.
  • the frequency generator is preferably designed as a voltage-controlled pulse generator for voltage blocks of alternating polarity with the frequency of the pulse width being inversely proportional.
  • the duty cycle of the voltage blocks therefore becomes shorter with increasing frequency.
  • the inverter thyristors get less than 20% of the luminous flux is about 20 usec. long ignition pulses, which at 100% luminous flux to about 4 usec. be reduced. In this way, safe and low-loss switching of the thyristors of the inverter is guaranteed under all operating conditions.
  • a light-sensitive component for example a photodiode, a phototransistor or a photoresistor
  • the circuit can work as an illuminance controller, whereby it can be implemented with only one inexpensive quadruple operational amplifier and practically any number of ballasts can be controlled.
  • the illuminance control sets the luminous flux to lower values or can even switch off the lamps including the heater.
  • a rectifier which converts the mains voltage into such a DC voltage, advantageously consists of a mains input filter, an uncontrolled diode bridge, a DC smoothing element, a current measuring element for measuring the actual value of the direct current, a DC voltage measuring element for measuring the actual value of the DC voltage and a DC switch for blocking the Direct current in case of undervoltage, overcurrent or short circuit.
  • the uncontrolled Rectifying the mains voltage enables a slight phase shift between the mains current and the mains voltage.
  • the measuring elements allow the frequency transmitter to be switched off when the voltage drops below the level required for the lamps to operate properly and the DC voltage to be switched off in the event of an overcurrent or short circuit, such as can occur when a defective lamp is replaced.
  • the DC switch is preferably designed as a thyristor that can be switched on and off via the control electrode.
  • the use of such a thyristor considerably simplifies the implementation of the circuit arrangement.
  • a device in the form of a timing element which prevents the DC switch from being switched on again for a specific period of time after the DC switch has been switched off.
  • a further device in the form of a counter or timer is provided which, after a certain number of unsuccessful attempts to switch the DC switch back on, prevents further start attempts.
  • This device acts as an electronic fuse, which must either be reset to its normal state either by a special restart button or by briefly pressing the power switch.
  • a feedforward control of the actual value of the direct voltage to the frequency generator is provided. such that the frequency increases when the DC voltage drops, and the frequency decreases when the DC voltage increases.
  • the feedforward control is more economical and cheaper than keeping the DC voltage constant by means of high-current control devices.
  • the inverter is formed from two series-connected reverse-conducting thyristors Th1, Th2 between the connection poles of a supplying direct voltage U.
  • Each thyristor Th1, Th2 is assigned its own ignition pulse generator, which generates ignition pulses for mutually switching on the thyristors Th1, Th2 from an ignition pulse alternating voltage U1 applied to a terminal 31.
  • Each pulse generator has a decoupling diode D1, D2 and a uni-function transistor T1, T2, in the main circuit of which the primary winding 1.1 of an ignition transformer 1 is located.
  • the ignition pulses for the main thyristor Th1 which are coupled into a first secondary winding 1.2 of the ignition transformer 1, are formed.
  • a second secondary winding 1.3 and a parallel RC element R2, C2 short blocking pulses are connected to the control electrode of the other main thyristor Th2.
  • ballast LC element consisting of a capacitor 3 and a first inductor 4, the free ends of the heating filaments 5, 7 being connected via a second inductor are.
  • the second inductor 6 has two windings 6a, 6b, which are each connected in parallel to a fluorescent lamp 2a, 2b.
  • FIG. 3 shows a further arrangement with a fluorescent lamp 2 and a second choke 6, with a single capacitor 3 and two first chokes 4a, 4b, one choke 4a being connected upstream and the other choke 4b being connected behind the fluorescent lamp 2.
  • a public supply network 9 which can be an AC or three-phase network
  • the electrical energy passes through a network input filter 10, a network switch 11 to an uncontrolled rectifier bridge 12, where it is converted into DC voltage.
  • the DC voltage is smoothed in a smoothing element 13 and measured in a voltage measuring element 14.
  • the level of the flowing direct current is measured in a current measuring element 15.
  • the DC voltage U is available for distribution to the ballasts assigned to the individual lights.
  • the actual value of the DC voltage measured in the voltage measuring element 14 is processed in a DC voltage evaluation circuit 18 in the form of a function generator.
  • the characteristic curve of the circuit 18 is selected such that a negative blocking signal is emitted below a certain minimum voltage, for example 400 V, which switches off the undervoltage and short-circuit protection switch 16 via a timing element 19.
  • the timer 19 ensures that the switch 16 remains locked for a certain period of time, for example 3 seconds.
  • the timing element 19 is activated not only by undervoltage, but also by overcurrent, which is measured by the current measuring element 15.
  • the switch 16 switches within 1 to 2 msec. the current. Due to the action of the choke in the smoothing element 13, the current only increases to a value slightly above the nominal current within the switch-off time. After the delay time of approximately 3 seconds has elapsed, the timer 19 switches the switch 16 on again.
  • a monitoring and safety circuit 20 is provided which, after a certain number of e.g. 3 or 5 unsuccessful attempts to switch the switch 16 off permanently.
  • the power switch 11 In order to be able to put the system back into operation after eliminating the short circuit, the power switch 11 must be pressed briefly. However, it is also possible to provide a restart button in the monitoring and safety circuit 20 itself.
  • the electronic part for generating the ignition pulse alternating voltage U1 consists of the functional units 21 to 30.
  • the setpoint for the luminous flux or for the illuminance set on a luminous flux setpoint transmitter 21 reaches a frequency ramp generator with a characteristic curve which has an essentially integrating character.
  • the characteristic curve is modified in the lower area so that the output signal of the frequency ramp generator 22 remains constant for a certain period of time. This time range serves to preheat the heating filaments in the fluorescent lamps so that a flicker-free start of the gas discharge is possible.
  • the output signal of the frequency ramp generator 22 is converted in a voltage-frequency converter 23 into an alternating voltage, the frequency of which is proportional to the applied voltage.
  • the positive part of the AC voltage reaches a pulse generator 24 for positive ignition pulses.
  • the output voltage of the frequency ramp generator 22 is also present at the pulse generator 24.
  • the width of the individual pulses is inversely proportional to the frequency. With 100% luminous flux, the width of the ignition pulses is approximately 4 / usec., With less than 20% luminous flux, approximately 20 / usec.
  • the ignition impulses pass through an ignition pulse amplifier 25 to the ignition pulse line 31, via which they are passed to the individual ballasts.
  • the negative part of the AC voltage at the output of the voltage-frequency converter 23 reaches an ignition pulse generator 29 for negative ignition pulses.
  • the output voltage of the frequency ramp generator 22, which is inverted via an inverter 28, is at the second input of the ignition pulse generator 29.
  • the width of the negative ignition pulses, which are modulated in width, also reach the ignition pulse line 31 via an ignition pulse amplifier 30.
  • the sum of positive and negative ignition pulses forms the ignition pulse alternating voltage U1.
  • the ramp generator 22 can be switched on and off directly without the mains switch 11 having to be operated.
  • the actual value of the luminous flux emitted by the fluorescent lamps can be measured and regulated to a constant value.
  • a voltage supply 17 generates the supply voltages ⁇ U V for the electronic part.
  • FIG. 5 shows a circuit diagram for the part of the electronics which generates the ignition pulse alternating voltage U1.
  • a setpoint potentiometer R51 can be seen, on which the desired luminous flux is set.
  • the maximum and minimum brightness value can be predetermined using resistors R53 and R54.
  • An operational amplifier 50 together with a capacitor C13, forms an integrating element in accordance with the characteristic of the frequency ramp generator 22 in FIG. 4.
  • the output voltage of the operational amplifier 50 cannot exceed the value set on the wiper of the setpoint potentiometer R51 due to the clamping diode D6.
  • the output voltage of the operational amplifier 50 reaches the control input of a voltage-controlled oscillator module 51 via a zener diode ZD, the fundamental frequency of which is set by a capacitor C15.
  • the output voltage of the operational amplifier 50 In order for the output voltage of the operational amplifier 50 to have an effect at the input of the voltage-controlled oscillator 51, it must have risen above the lock voltage of the Zener diode ZD. With the aid of the Zener diode ZD, the modification of the lower region of the characteristic curve of the frequency ramp generator 22 in FIG. 4 is achieved .
  • the positive half-wave passes via a diode D9 to an operational amplifier 52 connected as a comparator, at the second input of which the output voltage of the operational amplifier 50 is present. Rectangular pulses, the width of which is anti-proportional to the frequency, are generated in the operational amplifier 52.
  • the pulses are coupled via a coupling capacitor C16 to an amplifier transistor T30, amplified there and passed to the ignition pulse line 31.
  • the negative part of the output voltage of the voltage-controlled oscillator module 51 reaches via a diode D10 an operational amplifier 54, also connected as a comparator, at whose second input the output voltage of the operational amplifier 50, which is inverted in an operational amplifier 53 connected as an inverter, is present.
  • the mode of operation of the comparator 54 corresponds exactly to that of the comparator 52, the negative pulses reach the ignition pulse line 31 via the coupling capacitor C17 and the amplification transistor T2.
  • a control voltage U ( U ) dependent on the direct voltage U is applied via a coupling diode D7 to the output voltage of the operational amplifier 50 operating as a ramp generator.
  • the DC-dependent measurement voltage U (U) is also applied to the voltage-controlled oscillator module 5 via a further coupling diode D8, where it changes the output frequency inversely proportional to the measurement value.
  • Switch 26 is provided for switching on the frequency ramp generator. Via a switch 33, a photodiode FD can be connected to the ramp generator, so that the luminous flux of the fluorescent lamps can then be regulated to a constant value.
  • Fig. 6 shows the circuit diagram of an embodiment of the rectifier circuit.
  • the electrical power comes from a four-wire three-phase network with the connection terminals R, S, T, Mp via a fuse Si and the network.
  • gangsfilter with the capacitors C11 and the chokes L11 and the power switch 11 on the uncontrolled rectifier bridge with the diodes D13.
  • the use of an uncontrolled rectifier bridge in connection with the mains input filter enables a phase shift poor or free current draw from the three-phase network 10.
  • At the output of the rectifier bridge D13 there is an RC suppressor R4, C4 and a smoothing element with the choke L14 and the capacitor C14.
  • the DC supply voltage U arises at the capacitor C14.
  • the direct current I formed in the rectifier bridge D13 flows through a thyristor Th4 with a suppression element C5, R5 connected in parallel and via a current measuring resistor R15, at which the measuring voltage U (I) drops.
  • the level of the DC voltage U is detected via a resistor R14, at the output of which is the measuring voltage U ( U ).
  • the thyristor Th4 which acts as an undervoltage and short-circuit protection switch, is a thyristor that can be switched on and off via its control electrode.
  • the control electrode current I G required for switching on and off is formed in a circuit with a PNP transistor T3 and a thyristor Th3.
  • the inrush current is supplied from the positive pole of the supply voltage U V via the transistor T3, which is turned on via a resistor R7.
  • a current and voltage-dependent control voltage U * which is formed from a combination of the current-dependent measurement voltage U ( I ) and the voltage-dependent measurement voltage U ( U ) and is coupled to the base of the transistor T3 via a diode D5.
  • the current and voltage-dependent control voltage U * which blocks the transistor T3 is also conducted via a coupling RC element R6, C6 to the control electrode of the thyristor Th3, whereupon the thyristor Th3 becomes conductive.
  • the blocking pulse capacitor C10 which is charged via a resistor R10, drives a negative control electrode current I G via the control path of the Thyristors Th4, whereupon this switches off.
  • the thyristor Th3 blocks again and the capacitor C10 charges again via the resistor R10.
  • the current and voltage-dependent control voltage U * disappears again, whereupon the transistor T3 and thus the thyristor Th4 are switched on again.
  • Fig. 7 shows the external view of a ballast for connecting 4 fluorescent lamps, two of which are connected in series.
  • a housing 40 can be seen, on one end of which a clamping strip 41 is fastened.
  • U the DC voltage
  • U1 the ignition pulse alternating voltage
  • the other end of the housing there is a second terminal strip 42, to which the connection contacts of the four fluorescent lamps 2a, 2b, 2c, 2d are guided.
  • the thyristors of the inverter which make do with small cooling plates due to the low power loss, the ignition transformers with the associated electronics, and the ballast capacitors and the chokes for the fluorescent lamps.
  • FIG. 8 shows the external view of a ballast for two fluorescent lamps.
  • the structure is identical to that of FIG. 7.
  • the outer dimensions of the housing 40 are matched to the dimensions of the luminaire.
  • one ballast can be used to operate all fluorescent lamps between 20 and 65W power consumption without change, since the lamp power can be set by selecting the largest frequency of the ignition pulse alternating voltage U1. This reduces the different number of types and thus the costs.
  • the clear terminal strips allow a clear assignment of the Lamp holders.
  • FIGS. 9 to 13 each show, depending on the luminous flux L, which is given as a percentage of the nominal value, various measured values which result when different fluorescent lamps are operated on a ballast constructed in accordance with the invention.
  • the values of heating current I H and total current I H + I L are the same.
  • the lamp current I L increases as the heating current I H initially remains substantially constant.
  • the total current I L + I H flows via the first heating coil and the gas discharge path of the fluorescent lamp to the second heating coil.
  • the arithmetic mean of the lamp current I L which corresponds to the current through the gas discharge path, increases linearly with the luminous flux L. The phase shift between total current and heating current increases with increasing luminous flux.
  • Fig. 10 shows for a 65W fluorescent lamp the power consumption N in watts, the flowing direct current I in milliamps, the lamp voltage U L in volts and the frequency f in kilohertz as a function of the luminous flux L.
  • the lamp voltage U L is the Peak voltage between the middle of the heating coils. Before the lamp is ignited, the lamp voltage peak value is 400V.
  • the re-ignition voltage of the lamp remains constant at 420V up to 40% of the luminous flux and drops to 220V at 100% luminous flux. From 20% to 100% luminous flux, the direct current I and the total power N increase almost linearly.
  • the power consumption for heating the heating coils before igniting the lamp is 8W.
  • Fig. 12 shows the corresponding measured values for a 58W fluorescent lamp.

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  • Circuit Arrangements For Discharge Lamps (AREA)
  • Discharge-Lamp Control Circuits And Pulse- Feed Circuits (AREA)
  • Medicines Containing Antibodies Or Antigens For Use As Internal Diagnostic Agents (AREA)
  • Steroid Compounds (AREA)
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EP82100310A 1981-01-20 1982-01-18 Méthode et circuit pour chauffer, allumer ainsi que pour commander ou régler le courant électrique de lampes de décharge à gaz à basse pression Expired EP0056642B1 (fr)

Priority Applications (1)

Application Number Priority Date Filing Date Title
AT82100310T ATE31236T1 (de) 1981-01-20 1982-01-18 Verfahren und schaltungsanordnung zum heizen und zuenden sowie zum steuern oder regeln des lichtstroms von niederdruckgasentladungslampen.

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE3101568 1981-01-20
DE3101568A DE3101568C2 (de) 1981-01-20 1981-01-20 Schaltungsanordnung zum Betrieb von Niederdruckentladungslampen mit einstellbarem Lichtstrom

Publications (2)

Publication Number Publication Date
EP0056642A1 true EP0056642A1 (fr) 1982-07-28
EP0056642B1 EP0056642B1 (fr) 1987-12-02

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Application Number Title Priority Date Filing Date
EP82100310A Expired EP0056642B1 (fr) 1981-01-20 1982-01-18 Méthode et circuit pour chauffer, allumer ainsi que pour commander ou régler le courant électrique de lampes de décharge à gaz à basse pression

Country Status (6)

Country Link
US (1) US4398128A (fr)
EP (1) EP0056642B1 (fr)
JP (1) JPS57151199A (fr)
AT (1) ATE31236T1 (fr)
DE (2) DE3101568C2 (fr)
FI (1) FI73114C (fr)

Cited By (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0092654A2 (fr) * 1981-04-14 1983-11-02 Siemens Aktiengesellschaft Appareil ballast
EP0126556A1 (fr) * 1983-05-05 1984-11-28 Dubank Electronics (Pty) Limited Procédé pour mettre en oeuvre et démarrer une lampe à décharge, alimentation de puissance et ballast électronique y afférent
GB2147162A (en) * 1983-09-22 1985-05-01 Isco Inc Gas discharge lamp control circuits for absorbance monitors
WO1985004769A1 (fr) * 1984-04-09 1985-10-24 Nigg Juerg Procede de raccordement liberable d'appareils d'eclairage electriques, adaptateur respectivement ballast et circuit avec un generateur haute frequence
WO1987000719A1 (fr) * 1985-07-23 1987-01-29 Wolf, Karl Circuit pour l'amorcage et le fonctionnement d'au moins une lampe a decharge de faible ou de haute pression avec oscillations a frequence elevee
EP0279073A2 (fr) * 1985-02-07 1988-08-24 Nigg, Jürg Disposition de circuit pour le fonctionnement haute fréquence de lampes fluorescentes à filaments de préchauffage
WO2000002423A2 (fr) * 1998-07-01 2000-01-13 Everbrite, Inc. Alimentation pour lampe a decharge gazeuse

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Publication number Priority date Publication date Assignee Title
AT380373B (de) * 1983-05-17 1986-05-12 Zumtobel Ag Umschwingwechselrichter zur speisung von leuchtstofflampen
EP0176563A4 (fr) * 1984-03-28 1986-05-12 Electronic Transformer Corp Unite de charge et de commande pour une lampe a decharge electrique.
US5010279A (en) * 1985-08-26 1991-04-23 Lathom Michael S Switched capacitive ballasts for discharge lamps
DE3611611A1 (de) * 1986-04-07 1987-10-08 Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh Schaltungsanordnung zum hochfrequenten betrieb einer niederdruckentladungslampe
DE3711814C2 (de) * 1986-05-09 1998-04-09 Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh Elektronisches Vorschaltgerät zum Betrieb von Leuchtstofflampen
FR2599208A1 (fr) * 1986-05-23 1987-11-27 Harel Jean Systeme electronique d'alimentation pour tubes fluorescents a electrodes
DK161274C (da) * 1986-10-31 1991-12-02 Jorck & Larsen Vekselstroemsgenerator til forsyning og regulering af f.eks. lysstofroer, anvendelse af vekselstroemsgenerator og fremgansgsmaade til regulering af vekselstroem
US4885507A (en) * 1987-07-21 1989-12-05 Ham Byung I Electronic starter combined with the L-C ballast of a fluorescent lamp
US5053913A (en) * 1989-02-17 1991-10-01 Unison Industries Limited Partnership Capacitive discharge ignition exciter using scr discharge switches
DE3938677A1 (de) * 1989-11-22 1991-05-23 Trilux Lenze Gmbh & Co Kg Leuchtstofflampen-vorschaltgeraet
GB2245436A (en) * 1990-05-30 1992-01-02 Solar Wide Ind Ltd Solar-powered fluorescent lamp-drive circuit
US5642016A (en) * 1990-05-30 1997-06-24 Shalvi; Ram Drive circuit for a solar lamp with automatic electrical control of the lamp operating conditions
US5309066A (en) * 1992-05-29 1994-05-03 Jorck & Larsen A/S Solid state ballast for fluorescent lamps
US5473502A (en) * 1992-09-22 1995-12-05 Simmonds Precision Engine Systems Exciter with an output current multiplier
FR2779288B1 (fr) * 1998-06-02 2000-08-18 Valeo Electronique Module d'alimentation d'une lampe a decharge, notamment de projecteur de vehicule automobile
SE518667C2 (sv) * 2001-03-29 2002-11-05 Apra Light Ab Energibesparande system för tändning, drift och släckning av anslutna gasurladdningslampor.
DE10125510A1 (de) * 2001-05-23 2002-12-05 Innolux Gmbh Leuchtstofflampenschaltung
TWI326564B (en) * 2005-05-03 2010-06-21 Darfon Electronics Corp Power supply circuit for lamp and transformer therefor
TWI432096B (zh) 2011-12-27 2014-03-21 Ind Tech Res Inst 燈管控制系統、燈管節能系統及其節能方法

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US4207498A (en) * 1978-12-05 1980-06-10 Lutron Electronics Co., Inc. System for energizing and dimming gas discharge lamps
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Cited By (11)

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EP0092654A2 (fr) * 1981-04-14 1983-11-02 Siemens Aktiengesellschaft Appareil ballast
EP0092654A3 (fr) * 1981-04-14 1984-04-18 Siemens Aktiengesellschaft Appareil ballast
EP0126556A1 (fr) * 1983-05-05 1984-11-28 Dubank Electronics (Pty) Limited Procédé pour mettre en oeuvre et démarrer une lampe à décharge, alimentation de puissance et ballast électronique y afférent
GB2147162A (en) * 1983-09-22 1985-05-01 Isco Inc Gas discharge lamp control circuits for absorbance monitors
GB2163015A (en) * 1983-09-22 1986-02-12 Isco Inc Method of operating an absorbance monitor
WO1985004769A1 (fr) * 1984-04-09 1985-10-24 Nigg Juerg Procede de raccordement liberable d'appareils d'eclairage electriques, adaptateur respectivement ballast et circuit avec un generateur haute frequence
EP0279073A2 (fr) * 1985-02-07 1988-08-24 Nigg, Jürg Disposition de circuit pour le fonctionnement haute fréquence de lampes fluorescentes à filaments de préchauffage
EP0279073A3 (fr) * 1985-02-07 1990-06-27 Nigg, Jürg Disposition de circuit pour le fonctionnement haute fréquence de lampes fluorescentes à filaments de préchauffage
WO1987000719A1 (fr) * 1985-07-23 1987-01-29 Wolf, Karl Circuit pour l'amorcage et le fonctionnement d'au moins une lampe a decharge de faible ou de haute pression avec oscillations a frequence elevee
WO2000002423A2 (fr) * 1998-07-01 2000-01-13 Everbrite, Inc. Alimentation pour lampe a decharge gazeuse
WO2000002423A3 (fr) * 1998-07-01 2000-04-06 Everbrite Inc Alimentation pour lampe a decharge gazeuse

Also Published As

Publication number Publication date
FI73114C (fi) 1987-08-10
DE3101568A1 (de) 1982-08-05
DE3277796D1 (en) 1988-01-14
FI820146L (fi) 1982-07-21
FI73114B (fi) 1987-04-30
DE3101568C2 (de) 1986-01-09
JPS57151199A (en) 1982-09-18
EP0056642B1 (fr) 1987-12-02
ATE31236T1 (de) 1987-12-15
US4398128A (en) 1983-08-09

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