EP0012055A1 - In Streifenleitertechnik ausgeführter Monopulsprimärstrahler und Antenne mit einem solchen Strahler - Google Patents

In Streifenleitertechnik ausgeführter Monopulsprimärstrahler und Antenne mit einem solchen Strahler Download PDF

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Publication number
EP0012055A1
EP0012055A1 EP79400867A EP79400867A EP0012055A1 EP 0012055 A1 EP0012055 A1 EP 0012055A1 EP 79400867 A EP79400867 A EP 79400867A EP 79400867 A EP79400867 A EP 79400867A EP 0012055 A1 EP0012055 A1 EP 0012055A1
Authority
EP
European Patent Office
Prior art keywords
radiating
zones
primary source
substrate
face
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Granted
Application number
EP79400867A
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English (en)
French (fr)
Other versions
EP0012055B1 (de
Inventor
Robert Pierrot
François Gautier
Pierre Crochet
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Thales SA
Original Assignee
Thomson CSF SA
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Thomson CSF SA filed Critical Thomson CSF SA
Publication of EP0012055A1 publication Critical patent/EP0012055A1/de
Application granted granted Critical
Publication of EP0012055B1 publication Critical patent/EP0012055B1/de
Expired legal-status Critical Current

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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
    • H01Q9/04—Resonant antennas
    • H01Q9/0407—Substantially flat resonant element parallel to ground plane, e.g. patch antenna
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q25/00—Antennas or antenna systems providing at least two radiating patterns
    • H01Q25/02—Antennas or antenna systems providing at least two radiating patterns providing sum and difference patterns

Definitions

  • the present invention relates to a printed monopulse primary source, in particular for an airborne radar antenna, and to the antenna comprising such a source.
  • a monopulse primary source comprises radiating elements supplied with electromagnetic energy to develop a summing path and one or two difference paths oriented, for example, in elevation and in bearing, ⁇ S, ⁇ G channels.
  • An object of the present invention is the implementation of a printed monopulse primary source which does not have the aforementioned drawbacks and limitations.
  • Another object of the present invention is the implementation of a printed monopulse primary source comprising independent sum and difference channels.
  • Another object of the present invention is the implementation of a printed monopulse antenna having, due to its great simplicity of production, a low production cost.
  • the printed monopulse primary source comprises on a substrate of dielectric material a series of radiating zones forming at least one sum path and a difference path.
  • the radiating zones are arranged on a first face of the substrate of dielectric material.
  • the sum and difference channels constituted by distinct radiating zones are independent.
  • a reception supply circuit for the radiating zones, and connection means ensure the electrical connection of the radiating zones to the reception supply circuit in the thickness of the dielectric material substrate, the reception supply circuit and the radiating zones being separated. .
  • Such a printed monopulse source can be used in any airborne radar, in particular in active missile or self-steering radars.
  • the printed monopulse source object of the invention comprises, on a first face of a substrate of dielectric material 1, a series of radiating zones 20, 21, 22, 23, 24 constituting the radiating element of the primary source.
  • the first face of the substrate of dielectric material comprises five radiating zones constituting sum channels, site difference path ⁇ S, and field difference difference ⁇ G channel formed by distinct radiating zones. Any embodiment comprising a different number of radiating zones aimed at forming at least one sum channel ⁇ and one difference channel ⁇ does not depart from the scope of the present invention.
  • the primary source also comprises, disposed on a second face of the substrate opposite to the first face, a reception supply circuit 2 of the radiating zones 20, 21, 22, 23 24.
  • Connection means 3 provide the electrical connection of the zones radiating to the receiving supply circuit 2 in the thickness of the substrate of dielectric material.
  • the sum and difference channels comprise, on the first face of the substrate of dielectric material, a central radiating zone 20 forming the sum channel Z and four lateral radiating zones 21, 22, 23, 24 arranged symmetrically with respect to the central radiating zone 20.
  • the four lateral radiating zones 21, 22, 23, 24 are arranged symmetrically with respect to the central radiating zone 20 and respectively form two by two, radiating zones 21, 22 and 23, 24, the site difference tracks ⁇ S and deposit difference ⁇ G.
  • the three channels ⁇ , ⁇ S, ⁇ G are thus independent, the radiation patterns of these three channels being adjusted experimentally taking into account the couplings between the radiation zones.
  • the substrate of dielectric material 1 is constituted by a first and a second wafer of dielectric material 11, 12 each comprising on a first face a conductive sole 110, 120 or ground plane of reference.
  • the two conductive soles are for example produced by metallization and the two plates 11, 12 are placed back to back by their conductive sole 110, 120.
  • the two conductive soles 110 and 120 are joined to one another by means of a metal frame 4 ensuring, on the one hand, the electrical contact between the two conductive soles 111 and 120, and on the other hand , good rigidity and good sealing of the assembly.
  • the reception supply circuit 2 is directly connected to output terminals 5, 6 fixed to the chassis 4 and the central radiating area 20 is directly connected to an electromagnetic energy supply terminal 7 by a coaxial cable for example.
  • the connection means 3 are advantageously constituted by coaxial lines for example.
  • the reception supply circuit for the radiating zones comprises for each difference channel ⁇ S, ⁇ G, a transmission line in T 13, 14.
  • the branches 131, 132 and 141, 142 of each Tees have respectively equal lengths L and their ends are respectively connected to a lateral radiating zone forming a difference path by the connection means 3.
  • the lengths L of the Tees are determined experimentally in order to optimize the radiation patterns.
  • the Tee lines 13, 14 are, for example, ribbon lines each comprising an impedance transformer 133, 143.
  • connection means of the central radiating zone are directly connected to the supply terminal 7.
  • the terminals 5, 6, 7 are for example coaxial terminals fixed to the chassis.
  • a primary source prototype was produced for S-band operation, the operating wavelength being close to 10 cm.
  • the assembly taking into account the metal chassis 4. has the appearance of a reduced cylindrical volume of 13 cm in diameter and 6 cm in height.
  • the radiating zones are printed on a dielectric plate of 5 mm thick glass epoxy copper laminate dielectric constant of two faces 4, 5.
  • the reception feed circuit is formed on a dielectric material wafer known as trade name of metallized "Rexolite" two faces, thickness 1.7 mm and dielectric constant 2.5.
  • FIG. 4 relates to an embodiment of the invention allowing operation of the source in the frequency bands such as the Ku band for wavelengths of the order of a centimeter, the implementation in microelectronics being facilitated by the simplification of the source structure.
  • the substrate of dielectric material 1 is constituted by a wafer of single dielectric material comprising, on the one hand, a first face constituting the first face of the substrate 1.
  • This first face comprises the distinct radiating zones constituting the channels sum ⁇ and difference ⁇ S, to G.
  • the second face of the wafer of dielectric material opposite the first face, constitutes the second face of the substrate and comprises a conductive sole 150.
  • the second face of the wafer of dielectric material comprises two T-shaped transmission lines 16, 17 constituting with the metal sole 150 coplanar transmission lines.
  • the branches of Tees of identical length are respectively connected to a lateral radiating zone forming a difference path Z. S or ⁇ G by the connection means 3.
  • the transmission lines 16 and 17 are connected to the coaxial terminals 5, 6 not shown in the figure 4 and the metal chassis 4 can be reduced to a simple metal cylinder welded to the conductive sole 150 if this chassis is necessary for the mechanical maintenance of the primary source.
  • the coaxial supply terminal 7 can be welded directly to the metal soleplate 150.
  • the lateral radiating zones 21, 22, 23, 24 are excited two by two for each site difference path and deposit in phase opposition, the lateral radiating zones constituting the difference channels by the choice of their excitation point .
  • the connection means 3 ensuring the electrical connection of the radiating zones to the reception supply circuit are connected to these radiating zones at a particular point determining the excitation point 204, 211, 221, 231 of each of the zones .
  • the excitation point of each radiating zone has, with respect to the zero-field radio center of each zone, a determined eccentricity e.
  • the radiating zones consist of circular metallized pellets of the same diameter printed on the substrate of dielectric material.
  • the radio center in this case corresponds to the center of each patch.
  • the arithmetic value of the eccentricity is characteristic of the impedance of each radiating zone.
  • the excitation point of two lateral radiating zones forming a difference channel has an opposite eccentricity, the eccentricity being measured in magnitude and in sign with respect to the eccentricity of the central radiating zone defining the direction of polarization of the radioelectric signal .
  • the direction of polarization of the signals is represented, at the level of each radiating zone, by a vector P whose origin is located at the radioelectric center of the radiating zone and the end at the point of excitation of The area.
  • the lateral zones constituting a difference site or deli deposit route come to the reception of the signals in phase opposition due to the equality of the branches of each tee up to the level of their respective junction.
  • the phase opposition of the signals in each difference channel is thus carried out in principle and is independent of the frequency.
  • the operating band of the primary source is only limited by the radiating zones themselves and by the Tees whose standing wave rate is only suitable for a determined frequency band.
  • the choice of identical electrical lengths for the transmission lines 16, 17 up to the level of the terminals 5, 6 makes it possible to obtain the phasing of the signals by construction.
  • All of the embodiments of the invention shown in FIGS. 2 to 5 include radiating zones of circular shape. Any embodiment comprising radiating zones of different shape does not depart from the scope of the present invention.
  • the radiating zones are square metallized pellets 30, 31, 32, 33, 34 of the same dimensions.
  • the direction of polarization of the electric field is also given by a polarization vector P whose origin corresponds to the radio-electric center of the radiating zone and the end with the excitation point 301, 311, 321, 331, 341.
  • the eccentricity e of the excitation points of the lateral radiating zones is preferably defined in a direction parallel to the eccentricity of the central radiating zone.
  • the power supply circuit for receiving the radiating zones consists of at least one hybrid circuit 70 comprising two asymmetrical inputs phase-shifted by n 701 and 702 decoupled.
  • the hybrid circuit is arranged on a substrate of dielectric material 100 independent of the dielectric substrate 1 comprising the radiating zones constituting the radiant element.
  • the dielectric substrate 100 is, for example, mounted on a metal frame 200 ensuring the mechanical strength of the reception supply circuit.
  • Each of the phase-shifted inputs of n 701, 702 is connected respectively by terminals 201, 202, of the coaxial terminal type fixed to the chassis 200, to one of the lateral radiating zones 21, 22 by means of connection means 3 of equal electrical length. . ''
  • the connection means 3 preferably consist of a coaxial cable whose central core is connected to a phase-shifted input of ⁇ 701, 702 of the hybrid circuit 70 and at the point of excitation of each radiating zone defining with the radio center of each radiating area the direction of polarization P of the electric field of the emission signal.
  • the external conductor of the coaxial cables constituting the connection means 3 are connected to the conductive sole 110 of the substrate 1 and to the chassis 200 of the substrate 100 by means of terminals 201, 202 and coaxial terminals directly soldered to the conductive sole 110 of the substrate 1 and not shown in FIG. 7.
  • the excitation points of each zone have an identical eccentricity e, the phase shift of n making it possible to form the corresponding difference channel being brought to the level of the hybrid circuit 70.
  • the power supply circuit for receiving the radiating zones is constituted by at least one hybrid circuit 71 disposed on a substrate of independent dielectric material comprising two symmetrical inputs in phase 711 and 712 connected by the terminals 201, 202 respectively to the lateral radiating zones 21 and 22 forming at least one difference channel.
  • the difference signal is obtained on a channel 713 connected to a terminal 203, the connection means 3 ensuring the electrical connection of the radiating zones with the receiving supply circuit are connected at a particular point of each radiating zone determining the point of excitation. of each radiating zone.
  • the excitation point of the two lateral radiating zones forming the difference channel have, according to FIG. 8, an opposite eccentricity, the eccentricity e being measured in magnitude and in sign with respect to the eccentricity of the central radiating zone defining the direction polarization of the radio signal emitted by the primary source.
  • the two lateral zones 21 and 22 directly delivering signals in phase opposition to the hybrid ring 71 form a difference path therewith.
  • FIGS. 7 and 8 allow, by the complete separation of the reception supply circuit of the radiating element from the source, complete decoupling of the transmission-supply-reception functions and an improvement system performance from the point of view of channel decoupling.
  • the antenna according to the invention shown in Figure 9, it comprises a parabolic reflector 90.
  • the radiating element of the primary source 1 is disposed at the focus of the reflector 90 and held in position by a part frustoconical 91 solidiaire of the reflector.
  • the frusto-conical part 91 covers the opening of the reflector and is, for example, fitted therein and fixed to the latter by any suitable means.
  • the frustoconical part 91 has at its top a housing 92 intended to receive the radiating element 1 from the primary source, the radiating zones forming the independent sum and difference channels being oriented towards the reflector.
  • the frustoconical part 91 is constituted by a dielectric material with a dielectric constant of less than 1.1, such as a polyurethane foam for example.
  • the reception supply circuit 2 constituting with the radiating element 1 the primary source is for example arranged on the back of the reflector.
  • the connection means 3 constituted by coaxial cables connect the reception supply circuit to the radiating element 1 as described and shown in FIGS. 7 or 8 for example, the semi-rigid coaxial cables allowing the mechanical maintenance of the whole part radiating 1 frustoconical part 91 and the reflector 90.
  • the caxial cables are preferably arranged along a generator of the frustoconical part orthogonally to the vector P representing the vector polarization of the electric field of the signal emitted by the primary source. Any embodiment in which the primary source or the radiating part of the primary source is offset in off-set with respect to the focus of the reflector of the radar antenna does not depart from the scope of the present invention.
  • the simplicity of the reception supply circuit makes it possible to obtain low radioelectric losses, the integration of the reception supply circuit and of the radiating zones on the opposite faces of the dielectric substrate or on wafers. separate dielectric and separation of sum and difference channels to minimize these losses.
  • the circuits of the monopulse primary source which is the subject of the invention can be produced by the photoengraving technique, this makes it possible to obtain radiating and supply circuits of high precision and of low cost for a minimum bulk compared to the sources. classics.
EP79400867A 1978-11-24 1979-11-14 In Streifenleitertechnik ausgeführter Monopulsprimärstrahler und Antenne mit einem solchen Strahler Expired EP0012055B1 (de)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
FR7833292 1978-11-24
FR7833292A FR2442519A1 (fr) 1978-11-24 1978-11-24 Source primaire monopulse imprimee pour antenne de radar aeroporte et antenne comportant une telle source

Publications (2)

Publication Number Publication Date
EP0012055A1 true EP0012055A1 (de) 1980-06-11
EP0012055B1 EP0012055B1 (de) 1983-11-16

Family

ID=9215328

Family Applications (1)

Application Number Title Priority Date Filing Date
EP79400867A Expired EP0012055B1 (de) 1978-11-24 1979-11-14 In Streifenleitertechnik ausgeführter Monopulsprimärstrahler und Antenne mit einem solchen Strahler

Country Status (5)

Country Link
US (1) US4318107A (de)
EP (1) EP0012055B1 (de)
JP (1) JPS5577208A (de)
DE (1) DE2966414D1 (de)
FR (1) FR2442519A1 (de)

Cited By (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0200819A2 (de) * 1985-04-25 1986-11-12 Robert Bosch Gmbh Array-Antenne
EP0237110A1 (de) * 1986-03-05 1987-09-16 THORN EMI Electronics Limited Peilantennensystem
US5165109A (en) * 1989-01-19 1992-11-17 Trimble Navigation Microwave communication antenna
WO2000017960A1 (en) * 1998-09-18 2000-03-30 Tantivy Communications, Inc. Antenna array structure stacked over printed wiring board with beamforming components

Families Citing this family (22)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPS56134804A (en) * 1980-03-25 1981-10-21 Mitsubishi Electric Corp Tracking antenna
US4414550A (en) * 1981-08-04 1983-11-08 The Bendix Corporation Low profile circular array antenna and microstrip elements therefor
GB2108327B (en) * 1981-09-07 1985-04-24 Nippon Telegraph & Telephone Directivity diversity communication system
JPS59178002A (ja) * 1983-03-29 1984-10-09 Radio Res Lab 円偏波アンテナ
JPS59157311U (ja) * 1983-04-06 1984-10-22 三菱電機株式会社 電子走査アンテナ
JPS59157312U (ja) * 1983-04-06 1984-10-22 三菱電機株式会社 電子走査アンテナ
DE3514880A1 (de) * 1984-05-22 1985-11-28 Robert Bosch Gmbh, 7000 Stuttgart Array-antenne
US6195035B1 (en) * 1984-10-12 2001-02-27 Textron Systems Corporation Cylindrical monopulse
US4962383A (en) * 1984-11-08 1990-10-09 Allied-Signal Inc. Low profile array antenna system with independent multibeam control
US4835540A (en) * 1985-09-18 1989-05-30 Mitsubishi Denki Kabushiki Kaisha Microstrip antenna
JPH01166597A (ja) * 1987-12-23 1989-06-30 Fujitsu Ltd リフロー半田接合方法
AU4411289A (en) * 1988-10-19 1990-05-14 Toyo Communication Equipment Co., Ltd. Array antenna and a feeder device therefor
JPH02126413U (de) * 1989-03-28 1990-10-18
US5400041A (en) * 1991-07-26 1995-03-21 Strickland; Peter C. Radiating element incorporating impedance transformation capabilities
JPH0738332A (ja) * 1993-07-23 1995-02-07 Nec Corp 簡易モノパルス追尾アンテナ
US5512911A (en) * 1994-05-09 1996-04-30 Disys Corporation Microwave integrated tuned detector
US5493303A (en) * 1994-07-12 1996-02-20 M/A-Com, Inc. Monopulse transceiver
DE19615497A1 (de) * 1996-03-16 1997-09-18 Pates Tech Patentverwertung Planarer Strahler
US6052889A (en) * 1996-11-21 2000-04-25 Raytheon Company Radio frequency antenna and its fabrication
FR2818017B1 (fr) * 2000-12-13 2003-01-24 Sagem Reseau d'elements d'antenne patch
US9350086B2 (en) 2012-11-09 2016-05-24 Src, Inc. Shaped lens antenna for direction finding at the Ka-band
FR3007215B1 (fr) * 2013-06-17 2015-06-05 Zodiac Data Systems Source pour antenne parabolique

Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
FR2180114A1 (de) * 1972-04-14 1973-11-23 Hughes Aircraft Co
US4042935A (en) * 1974-08-01 1977-08-16 Hughes Aircraft Company Wideband multiplexing antenna feed employing cavity backed wing dipoles
US4083046A (en) * 1976-11-10 1978-04-04 The United States Of America As Represented By The Secretary Of The Navy Electric monomicrostrip dipole antennas

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US3943523A (en) * 1972-03-07 1976-03-09 Raytheon Company Airborne multi-mode radiating and receiving system
US3953857A (en) * 1972-03-07 1976-04-27 Jenks Frederic A Airborne multi-mode radiating and receiving system
FR2219533B1 (de) * 1973-02-23 1977-09-02 Thomson Csf
US3965475A (en) * 1975-05-30 1976-06-22 The United States Of America As Represented By The United States Administrator Of The National Aeronautics And Space Administration Switchable beamwidth monopulse method and system
US4089003A (en) * 1977-02-07 1978-05-09 Motorola, Inc. Multifrequency microstrip antenna
US4142190A (en) * 1977-09-29 1979-02-27 The United States Of America As Represented By The Secretary Of The Army Microstrip feed with reduced aperture blockage

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
FR2180114A1 (de) * 1972-04-14 1973-11-23 Hughes Aircraft Co
US4042935A (en) * 1974-08-01 1977-08-16 Hughes Aircraft Company Wideband multiplexing antenna feed employing cavity backed wing dipoles
US4083046A (en) * 1976-11-10 1978-04-04 The United States Of America As Represented By The Secretary Of The Navy Electric monomicrostrip dipole antennas

Cited By (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0200819A2 (de) * 1985-04-25 1986-11-12 Robert Bosch Gmbh Array-Antenne
EP0200819A3 (de) * 1985-04-25 1987-12-09 Robert Bosch Gmbh Array-Antenne
EP0237110A1 (de) * 1986-03-05 1987-09-16 THORN EMI Electronics Limited Peilantennensystem
US5165109A (en) * 1989-01-19 1992-11-17 Trimble Navigation Microwave communication antenna
WO2000017960A1 (en) * 1998-09-18 2000-03-30 Tantivy Communications, Inc. Antenna array structure stacked over printed wiring board with beamforming components
US6362790B1 (en) 1998-09-18 2002-03-26 Tantivy Communications, Inc. Antenna array structure stacked over printed wiring board with beamforming components

Also Published As

Publication number Publication date
US4318107A (en) 1982-03-02
DE2966414D1 (en) 1983-12-22
JPS5577208A (en) 1980-06-10
FR2442519B1 (de) 1982-04-16
EP0012055B1 (de) 1983-11-16
FR2442519A1 (fr) 1980-06-20

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