WO2023100321A1 - 電力変換装置、モータ駆動装置及び冷凍サイクル適用機器 - Google Patents

電力変換装置、モータ駆動装置及び冷凍サイクル適用機器 Download PDF

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Publication number
WO2023100321A1
WO2023100321A1 PCT/JP2021/044279 JP2021044279W WO2023100321A1 WO 2023100321 A1 WO2023100321 A1 WO 2023100321A1 JP 2021044279 W JP2021044279 W JP 2021044279W WO 2023100321 A1 WO2023100321 A1 WO 2023100321A1
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WIPO (PCT)
Prior art keywords
capacitor
control
current
value
voltage
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Ceased
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PCT/JP2021/044279
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English (en)
French (fr)
Japanese (ja)
Inventor
知宏 沓木
基 豊田
浩一 有澤
貴昭 ▲高▼原
遥 松尾
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Mitsubishi Electric Corp
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Mitsubishi Electric Corp
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Priority to CN202180104479.1A priority Critical patent/CN118318384A/zh
Priority to JP2023564368A priority patent/JPWO2023100321A1/ja
Priority to US18/696,598 priority patent/US20240380350A1/en
Priority to PCT/JP2021/044279 priority patent/WO2023100321A1/ja
Publication of WO2023100321A1 publication Critical patent/WO2023100321A1/ja
Anticipated expiration legal-status Critical
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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/36—Arrangements for braking or slowing; Four quadrant control
    • F—MECHANICAL ENGINEERING; LIGHTING; HEATING; WEAPONS; BLASTING
    • F25—REFRIGERATION OR COOLING; COMBINED HEATING AND REFRIGERATION SYSTEMS; HEAT PUMP SYSTEMS; MANUFACTURE OR STORAGE OF ICE; LIQUEFACTION SOLIDIFICATION OF GASES
    • F25B—REFRIGERATION MACHINES, PLANTS OR SYSTEMS; COMBINED HEATING AND REFRIGERATION SYSTEMS; HEAT PUMP SYSTEMS
    • F25B49/00—Arrangement or mounting of control or safety devices
    • F25B49/02—Arrangement or mounting of control or safety devices for compression type machines, plants or systems
    • F25B49/025—Motor control arrangements
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/42—Conversion of DC power input into AC power output without possibility of reversal
    • H02M7/44—Conversion of DC power input into AC power output without possibility of reversal by static converters
    • H02M7/48—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using DC to AC converters or inverters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using DC to AC converters or inverters
    • H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using DC to AC converters or inverters with pulse width modulation
    • F—MECHANICAL ENGINEERING; LIGHTING; HEATING; WEAPONS; BLASTING
    • F25—REFRIGERATION OR COOLING; COMBINED HEATING AND REFRIGERATION SYSTEMS; HEAT PUMP SYSTEMS; MANUFACTURE OR STORAGE OF ICE; LIQUEFACTION SOLIDIFICATION OF GASES
    • F25B—REFRIGERATION MACHINES, PLANTS OR SYSTEMS; COMBINED HEATING AND REFRIGERATION SYSTEMS; HEAT PUMP SYSTEMS
    • F25B2600/00—Control issues
    • F25B2600/02—Compressor control
    • F25B2600/021—Inverters therefor

Definitions

  • the present disclosure relates to a power conversion device, a motor drive device, and a refrigeration cycle application device that convert AC power into desired power.
  • a power conversion device that converts AC power supplied from an AC power supply into desired AC power and supplies it to a load such as an air conditioner.
  • a power converter which is a control device for an air conditioner, rectifies AC power supplied from an AC power supply with a diode stack, which is a rectifier, and smoothes the power with a smoothing capacitor
  • a technology is disclosed in which an inverter comprising a plurality of switching elements converts the AC power into desired AC power and outputs the AC power to a compressor motor as a load.
  • the operation of the inverter is controlled so that the pulsation corresponding to the detected value of the capacitor voltage is superimposed on the drive pattern of the motor. Since the pulsation of the capacitor voltage depends on the power supply frequency, this control is called "power supply pulsation compensation control".
  • the power supply frequency is the frequency of the power supply voltage applied from the AC power supply.
  • the power supply ripple compensation control is operating as expected, aging deterioration of the smoothing capacitor is suppressed.
  • the power supply pulsation compensation control does not operate as expected, the increase in the pulsating current increases the electrical stress that the smoothing capacitor receives, which accelerates aging deterioration of the smoothing capacitor. Therefore, it is important to check whether the power supply ripple compensation control is operating as expected and to take appropriate measures.
  • the present disclosure has been made in view of the above, and an object thereof is to obtain a power conversion device that can appropriately cope with the case where the power supply ripple compensation control does not operate as expected.
  • the power converter according to the present disclosure includes a rectifier, a capacitor connected to the output terminal of the rectifier, an inverter connected to both ends of the capacitor, and a controller. and
  • the rectifier rectifies a power supply voltage applied from an AC power supply.
  • the inverter converts the DC power output from the capacitor into AC power, and outputs the AC power to the device on which the motor is mounted.
  • the control unit controls the inverter to perform a first control that suppresses pulsation of capacitor current, which is charge/discharge current of the capacitor.
  • the control unit determines whether or not the compensating operation by the first control is normal, and if it is determined that the compensating operation is not normal, the control unit reduces the driving rotation speed of the motor or stops driving the motor. 2 control is performed.
  • FIG. 1 is a diagram showing a configuration example of a power converter according to Embodiment 1;
  • FIG. FIG. 2 is a block diagram showing a configuration example of a control unit included in the power converter according to Embodiment 1;
  • FIG. 4 is a diagram showing a configuration example of a q-axis current pulsation calculation section included in the control section according to Embodiment 1;
  • FIG. 4 is a diagram for explaining a threshold setting method according to the first embodiment;
  • Flowchart for explaining the operation of the control unit according to the first embodiment 1 is a block diagram showing an example of a hardware configuration realizing functions of a control unit according to Embodiment 1;
  • FIG. 4 is a block diagram showing another example of a hardware configuration that implements the functions of the control unit according to Embodiment 1;
  • FIG. 10 is a diagram for explaining a threshold setting method according to the second embodiment;
  • Flowchart for explaining the operation of the control unit according to the second embodiment Flowchart for explaining the operation of the control unit according to the third embodiment
  • Flowchart for explaining the operation of the control unit according to the fourth embodiment A diagram showing a configuration example of a refrigeration cycle application device according to Embodiment 5
  • FIG. 1 is a diagram showing a configuration example of a power conversion device 1 according to Embodiment 1.
  • the power converter 1 is connected to a commercial power source 110 and a compressor 315 .
  • the commercial power supply 110 is an example of an AC power supply
  • the compressor 315 is an example of the equipment referred to in the first embodiment.
  • a motor 314 is mounted on the compressor 315 .
  • a motor drive device 2 is configured by the power conversion device 1 and the motor 314 included in the compressor 315 .
  • the power converter 1 includes a reactor 120, a rectifying section 130, current detecting sections 501 and 502, a voltage detecting section 503, a smoothing section 200, an inverter 310, current detecting sections 313a and 313b, and a control section 400. , provided.
  • the reactor 120 is connected between the commercial power supply 110 and the rectifying section 130 .
  • the rectifying section 130 has a bridge circuit composed of rectifying elements 131-134.
  • the rectifying unit 130 rectifies the power supply voltage applied from the commercial power supply 110 and outputs the rectified power supply voltage.
  • the rectifier 130 performs full-wave rectification.
  • the smoothing section 200 is connected to the output terminal of the rectifying section 130 .
  • Smoothing section 200 has capacitor 210 as a smoothing element, and smoothes the rectified voltage output from rectifying section 130 .
  • the capacitor 210 is, for example, an electrolytic capacitor, a film capacitor, or the like.
  • Capacitor 210 is connected to the output terminal of rectifying section 130 .
  • Capacitor 210 has a capacity corresponding to the degree of smoothing the rectified voltage. Due to this smoothing, the voltage generated in the capacitor 210 does not have a full-wave rectified waveform of the rectified voltage, but has a waveform in which a voltage ripple corresponding to the frequency of the commercial power supply 110 is superimposed on the DC component, and does not pulsate greatly.
  • the main component of the voltage ripple frequency is twice the frequency of the power supply voltage. If the power input from commercial power supply 110 and the power output from inverter 310 do not change, the amplitude of this voltage ripple is determined by the capacitance of capacitor 210 . However, in the power conversion device 1 according to the present disclosure, an increase in capacitance is avoided in order to suppress an increase in cost of the capacitor 210 . As a result, a certain amount of voltage ripple is generated in the capacitor 210 .
  • the voltage across capacitor 210 is a pulsating voltage in a range such that the maximum value of the voltage ripple is less than twice the minimum value.
  • Current detector 501 detects rectified current I ⁇ b>1 flowing out from rectifier 130 and outputs the detected value of rectified current I ⁇ b>1 to controller 400 .
  • Current detection unit 502 detects inverter input current I ⁇ b>2 that flows into inverter 310 and outputs a detected value of inverter input current I ⁇ b>2 to control unit 400 .
  • Voltage detection unit 503 detects capacitor voltage Vdc , which is the voltage of capacitor 210 , and outputs the detected value of the detected capacitor voltage Vdc to control unit 400 .
  • Voltage detection unit 503 can be used as a detection unit that detects the power state of capacitor 210 .
  • the inverter 310 is connected to both ends of the smoothing section 200 , that is, the capacitor 210 .
  • the inverter 310 has switching elements 311a-311f and freewheeling diodes 312a-312f.
  • the inverter 310 turns on and off the switching elements 311a to 311f under the control of the control unit 400, converts the power output from the rectifying unit 130 and the smoothing unit 200 into AC power having a desired amplitude and phase, and the motor 314 is mounted. It outputs to the compressor 315, which is a device that has been processed.
  • the current detection units 313 a and 313 b each detect the current value of one phase out of the three-phase motor currents output from the inverter 310 to the motor 314 .
  • Each detection value of the current detection units 313 a and 313 b is input to the control unit 400 .
  • the control unit 400 calculates the current of the remaining one phase based on the detected value of the current of any two phases detected by the current detection units 313a and 313b.
  • a motor 314 mounted on the compressor 315 rotates according to the amplitude and phase of the AC power supplied from the inverter 310 to perform compression operation.
  • the compressor 315 is a hermetic compressor used in an air conditioner or the like, the load torque of the compressor 315 can often be regarded as a constant torque load.
  • FIG. 1 shows a case where the motor windings in the motor 314 are Y-connected
  • the present invention is not limited to this example.
  • the motor windings of the motor 314 may be delta-connection, or may be switchable between Y-connection and delta-connection.
  • reactor 120 may be arranged after rectifying section 130 .
  • the power conversion device 1 may include a booster section, or the rectifier section 130 may have the function of the booster section.
  • the current detection units 501 and 502, the voltage detection unit 503 and the current detection units 313a and 313b may be simply referred to as "detection units”.
  • the current values detected by the current detection units 501 and 502, the voltage value detected by the voltage detection unit 503, and the current values detected by the current detection units 313a and 313b may be simply referred to as "detected values". be.
  • the control unit 400 detects the value of the rectified current I1 detected by the current detection unit 501, the value of the inverter input current I2 detected by the current detection unit 502, and the capacitor voltage Vdc detected by the voltage detection unit 503. Get the detected value.
  • the control unit 400 also acquires the detected values of the motor currents detected by the current detection units 313a and 313b.
  • Control unit 400 controls the operation of inverter 310, specifically, the on/off of switching elements 311a to 311f included in inverter 310, using the detection values detected by the respective detection units.
  • control unit 400 controls the operation of the inverter 310 so that AC power including pulsation corresponding to the pulsation of the power flowing from the rectifying unit 130 into the capacitor 210 of the smoothing unit 200 is output from the inverter 310 to the compressor 315. do.
  • the pulsation according to the pulsation of the power flowing into the capacitor 210 of the smoothing section 200 is, for example, the pulsation that varies depending on the frequency of the pulsation of the power flowing into the capacitor 210 of the smoothing section 200 .
  • control unit 400 suppresses capacitor current I3, which is the charge/discharge current of capacitor 210 .
  • the control unit 400 performs control so that any one of the speed, voltage, and current of the motor 314 is in a desired state. Note that the control unit 400 does not have to use all the detection values acquired from each detection unit, and can perform control using some of the detection values.
  • the control unit 400 controls the motor 314 without a position sensor.
  • position sensorless control methods for the motor 314 There are two types of position sensorless control methods for the motor 314: primary magnetic flux constant control and sensorless vector control. Embodiment 1 will be described based on sensorless vector control as an example. It should be noted that the control method described below can be applied to the primary magnetic flux constant control with minor modifications.
  • the rectified current I1 flowing out of the rectifier 130 is affected by the power phase of the commercial power supply 110, the characteristics of elements installed before and after the rectifier 130, and the like.
  • the rectified current I1 has characteristics including the power supply frequency and harmonic components of the power supply frequency (frequency components of integer multiples of 2 or more).
  • the capacitor current I3 when the capacitor current I3 is large, aging deterioration of the capacitor 210 is accelerated. In particular, when an electrolytic capacitor is used as the capacitor 210, the degree of aging deterioration is accelerated.
  • control unit 400 controls the inverter 310 so that the inverter input current I2 becomes equal to the rectified current I1, and controls the capacitor current I3 to approach zero. This suppresses deterioration of the capacitor 210 .
  • a ripple component caused by PWM Pulse Width Modulation
  • control unit 400 needs to control inverter 310 with the ripple component taken into consideration.
  • Control unit 400 controls inverter 310 so that a value obtained by removing PWM ripple from inverter input current I2 from capacitor 210 to inverter 310 matches rectified current I1, and adds pulsation to the power output to motor 314 .
  • the control unit 400 appropriately pulsates the inverter input current I2 to perform control for reducing the capacitor current I3, that is, power supply pulsation compensation control.
  • control unit 400 performs power supply ripple compensation control on capacitor 210 .
  • the power supply ripple compensation control is compensation control performed to suppress the power supply ripple component contained in the capacitor current I3.
  • the power supply pulsation component is a pulsation component of the capacitor current I3 that can occur in the capacitor current I3 due to the power supply frequency and harmonic components of the power supply frequency (frequency components of integer multiples of 2 or more).
  • the power supply ripple compensation control is performed based on the detected value of at least one of the rectified current I1, the inverter input current I2, the capacitor current I3, and the capacitor voltage Vdc , which is information for grasping the power state of the capacitor 210. be able to.
  • FIG. 2 is a block diagram showing a configuration example of the control unit 400 included in the power converter 1 according to Embodiment 1.
  • the control unit 400 includes a rotor position estimation unit 401, a speed control unit 402, a flux-weakening control unit 403, a current control unit 404, coordinate conversion units 405 and 406, a PWM signal generation unit 407, a q-axis current A pulsation calculator 408 and an adder 409 are provided.
  • the rotor position estimation unit 401 calculates the dq-axis Estimate an estimated phase angle ⁇ est , which is the direction at , and an estimated speed ⁇ est , which is the rotor speed.
  • the speed control unit 402 automatically adjusts the q-axis current command i q1 * so that the speed command ⁇ * and the estimated speed ⁇ est match.
  • the speed command ⁇ * is, for example, a temperature detected by a temperature sensor (not shown) or a setting indicated by a remote control that is an operation unit (not shown). It is based on information indicating temperature, operation mode selection information, operation start and operation end instruction information, and the like.
  • the operation modes are, for example, heating, cooling, and dehumidification.
  • the flux-weakening control unit 403 automatically adjusts the d-axis current command i d * so that the absolute value of the dq-axis voltage command vector V dq * falls within the limits of the voltage limit value V lim * . Further, in Embodiment 1, the flux-weakening control unit 403 performs flux-weakening control in consideration of the q-axis current ripple command i qrip * calculated by the q-axis current ripple calculation unit 408 .
  • the flux-weakening control can be broadly divided into a method of calculating the d-axis current command id * from the equation of the voltage limit ellipse, and a method in which the absolute value deviation between the voltage limit value Vlim * and the dq-axis voltage command vector Vdq * is zero. There are two methods of calculating the d-axis current command i d * so that
  • the current control unit 404 automatically adjusts the dq-axis voltage command vector V dq * so that the dq-axis current vector i dq follows the d-axis current command id * and the q-axis current command i q * .
  • the coordinate conversion unit 405 coordinates-converts the dq-axis voltage command vector V dq * from the dq coordinates into the voltage command V uvw * of the AC quantity according to the estimated phase angle ⁇ est .
  • a coordinate transformation unit 406 coordinates-transforms the current I uvw flowing through the motor 314 from an alternating current quantity to a dq-axis current vector i dq of dq coordinates in accordance with the estimated phase angle ⁇ est .
  • the control unit 400 controls the two-phase current values detected by the current detection units 313a and 313b among the three-phase current values output from the inverter 310 for the current Iuvw flowing through the motor 314, It can be obtained by calculating the current value of the remaining one phase using the current values of the two phases.
  • PWM signal generation unit 407 generates a PWM signal based on voltage command V uvw * coordinate-transformed by coordinate transformation unit 405 .
  • Control unit 400 applies a voltage to motor 314 by outputting the PWM signal generated by PWM signal generation unit 407 to switching elements 311 a to 311 f of inverter 310 .
  • a q-axis current ripple calculation unit 408 calculates a q-axis current ripple command i qrip * based on the detected value of the capacitor voltage V dc detected by the voltage detection unit 503 and the estimated speed ⁇ est .
  • An addition unit 409 adds the q-axis current command i q1 * output from the speed control unit 402 and the q-axis current ripple command i qrip * calculated by the q-axis current ripple calculation unit 408, and the calculated value is A certain q-axis current command i q * is output as a torque current command to the current control unit 404 .
  • FIG. 3 is a diagram showing a configuration example of the q-axis current ripple calculator 408 included in the controller 400 according to the first embodiment.
  • the q-axis current pulsation calculator 408 is configured as a feedback controller with a command value of zero. Generally, feedback controllers have a lower control response than feedforward controllers and are unsuitable for suppressing high-frequency pulsations, but various high-frequency pulsation suppression means have been proposed in the past. Famous methods include a method using Fourier coefficient calculation and a PID (Proportional Integral Differential) controller.
  • the q-axis current pulsation calculator 408 includes a subtractor 383 , Fourier coefficient calculators 384 to 387 , PID controllers 388 to 391 , and an AC restorer 392 .
  • the subtractor 383 calculates the deviation between the zero command value and the capacitor voltage Vdc .
  • Fourier coefficient calculators 384 to 387 assume that the power supply frequency is the 1f component, and calculate the amplitudes of the sin2f component, cos2f component, sin4f component, and cos4f component included in the deviation.
  • the detection signals multiplied by the Fourier coefficient calculators 384 to 387 are sin2 ⁇ in t, cos2 ⁇ in t, sin4 ⁇ in t, and cos4 ⁇ in t, respectively.
  • the detected signal has amplitudes of sin2f component, cos2f component, sin4f component, and cos4f component whose deviation includes twice the average value of the product of the input signal and the detected signal. That is, the Fourier coefficient calculators 384 to 387 calculate the amplitude of the component corresponding to the power supply frequency of the commercial power supply 110 included in the deviation between the detected value and the command value. If the capacitor current I3 has a periodic waveform, the output signals of the Fourier coefficient calculators 384 to 387 are substantially constant.
  • the PID control units 388 to 391 perform proportional-integral-derivative control, that is, PID control, so that specific frequency components of these deviations are zero.
  • the proportional gain and the derivative gain can be zero, but the value of the integral gain must be non-zero in order to converge the deviation to zero. Therefore, in the PID controllers 388 to 391, integral action is the main function. Since the output of the integral control normally changes gently, the outputs of the PID control units 388 to 391 can also be regarded as substantially constant.
  • the capacitor voltage Vdc is obtained by dividing the electric charge accumulated in the capacitor current I3, that is, the integrated value of the capacitor current I3, by the capacitance of the capacitor 210.
  • the detection signals multiplied by the Fourier coefficient calculators 384 to 387 are sin2 ⁇ in t, cos2 ⁇ in t, sin4 ⁇ in t, and cos4 ⁇ in t, respectively, as described above.
  • the AC restoration unit 392 shifts the restoration signal by the phase difference ⁇ offset to restore the outputs of the PID control units 388 to 391 to AC components. It is multiplied by sin4( ⁇ int + ⁇ offset ) and cos4( ⁇ int + ⁇ offset ) and then summed to determine the q-axis current ripple command i qrip * . In this manner, the AC restoring unit 392 generates the q-axis current pulsation command i qrip * , which is a pulsation command for suppressing the capacitor current I3.
  • the sensorless vector control system is exemplified, but it can also be applied to constant primary magnetic flux control by adding pulsation to the speed command, voltage command, etc. by adding some modifications.
  • the q-axis current pulsation command i qrip * may be generated based on the capacitor current I3.
  • Capacitor current I3 can be calculated from the detected value of rectified current I1 detected by current detector 501 and the detected value of inverter input current I2 detected by current detector 502 . Alternatively, it may be calculated based on the capacitor voltage Vdc and the capacitance of the capacitor 210, as in a third embodiment to be described later. Alternatively, the capacitor current I3 may be directly detected as in a fourth embodiment to be described later.
  • FIG. 4 is a diagram for explaining a threshold setting method according to the first embodiment.
  • the left side of FIG. 4 shows the time-varying waveform of the capacitor voltage Vdc when the power supply ripple compensation control is not performed.
  • the case where the power supply ripple compensation control is not performed means that the power supply ripple compensation control function is not activated.
  • the right side of FIG. 4 shows the time-varying waveform of the capacitor voltage Vdc when the power supply ripple compensation control is being performed.
  • the power supply ripple compensation control means that the power supply ripple compensation control function is activated.
  • the threshold value a which is the first threshold value
  • the threshold value b which is the second threshold value
  • the thresholds a and b are desirably set individually for each product or model.
  • the set thresholds a and b can be stored in a memory or processing circuit, which will be described later.
  • the positive and negative peak values of the capacitor voltage Vdc are surely smaller than when the power supply ripple compensation control is not performed. Also, when the power supply ripple compensation control function works effectively, the positive peak value of the capacitor voltage Vdc becomes smaller than the threshold value a, and the negative peak value of the capacitor voltage Vdc becomes larger than the threshold value b. Therefore, if the positive and negative peak values of the capacitor voltage Vdc are threshold-determined based on the threshold values a and b set in this manner, it can be appropriately determined whether or not the compensation operation by the power supply ripple compensation control is normal. can judge.
  • FIG. 5 is a flow chart for explaining the operation of the control unit 400 according to the first embodiment.
  • the control unit 400 reads the thresholds a and b from the memory or processing circuit (step S21).
  • the control unit 400 acquires the detected value of the capacitor voltage Vdc from the voltage detection unit 503 (step S22).
  • the control unit 400 calculates positive and negative peak values of the capacitor voltage Vdc based on the acquired detection values (step S23).
  • the control unit 400 compares the positive peak value of the capacitor voltage Vdc with the threshold value a, and compares the negative peak value of the capacitor voltage Vdc with the threshold value b (step S24).
  • step S25 When the positive peak value of the capacitor voltage Vdc is smaller than the threshold value a and the negative peak value of the capacitor voltage Vdc is larger than the threshold value b (step S25, Yes), the control unit 400 performs the power supply ripple compensation control function. is normal (step S26). Henceforth, it returns to step S22 and the process from step S22 is repeated.
  • step S25, No when the positive peak value of the capacitor voltage Vdc is equal to or greater than the threshold value a, or the negative peak value of the capacitor voltage Vdc is equal to or less than the threshold value b (step S25, No), the control unit 400 performs power supply ripple compensation. It is determined that the control function is not normal (step S27). In this case, the control unit 400 performs control to reduce the driving rotation speed of the motor 314 (step S28). Henceforth, it returns to step S22 and the process from step S22 is repeated.
  • step S28 If control is performed in step S28 to reduce the driving rotation speed of the motor 314, it may be determined in the processing of steps S25 and S26 that the power supply pulsation compensation control function is normal. In this case, the drive rotation speed of the motor 314 is returned to the instructed rotation speed, and the process of FIG. 5 is performed again. In addition, when it is determined that the power supply pulsation compensation control function is not normal, the operation of the power converter 1 is stopped and the driving of the motor 314 is stopped. In addition, in this paper, the control for reducing the driving rotation speed of the motor 314 or the control for stopping the driving of the motor 314 may be referred to as "second control".
  • step S25 it is determined as "No" when the positive peak value of the capacitor voltage Vdc and the threshold value a are equal, or when the negative peak value of the capacitor voltage Vdc and the threshold value b are equal. It may be judged as "Yes”. That is, when the positive peak value of the capacitor voltage Vdc is larger than the threshold value a or the negative peak value of the capacitor voltage Vdc is smaller than the threshold value b, it is determined that the power supply ripple compensation control function is not normal. good too.
  • FIG. 6 is a block diagram showing an example of a hardware configuration that implements the functions of the control unit 400 according to the first embodiment.
  • FIG. 7 is a block diagram showing another example of the hardware configuration that implements the functions of the control unit 400 according to the first embodiment.
  • the configuration may include an interface 424 .
  • the processor 420 is an example of computing means.
  • the processor 420 may be a computing means called a microprocessor, microcomputer, CPU (Central Processing Unit), or DSP (Digital Signal Processor).
  • the memory 422 includes nonvolatile or volatile semiconductor memories such as RAM (Random Access Memory), ROM (Read Only Memory), flash memory, EPROM (Erasable Programmable ROM), EEPROM (registered trademark) (Electrically EPROM), Magnetic discs, flexible discs, optical discs, compact discs, mini discs, and DVDs (Digital Versatile Discs) can be exemplified.
  • the memory 422 stores a program for executing the functions of the control unit 400 and the set values of the threshold values a and b described above.
  • Processor 420 exchanges necessary information via interface 424, processor 420 executes programs stored in memory 422, and processor 420 refers to data including threshold values a and b stored in memory 422. , the above-described processing can be executed. Results of operations by processor 420 may be stored in memory 422 .
  • the processor 420 and memory 422 shown in FIG. 6 may be replaced with a processing circuit 423 as shown in FIG.
  • the processing circuit 423 corresponds to a single circuit, a composite circuit, an ASIC (Application Specific Integrated Circuit), an FPGA (Field-Programmable Gate Array), or a combination thereof.
  • Information to be input to the processing circuit 423 and information to be output from the processing circuit 423 can be obtained via the interface 424 .
  • part of the processing in the control unit 400 may be performed by the processing circuit 423 and the processing not performed by the processing circuit 423 may be performed by the processor 420 and the memory 422 .
  • the control unit performs the first control of controlling the inverter to suppress the pulsation of the capacitor current, which is the charging/discharging current of the capacitor.
  • the control unit determines whether or not the compensating operation by the first control is normal, and if it is determined that the compensating operation is not normal, reduces the driving rotation speed of the motor or stops driving the motor. 2nd control to carry out.
  • the first control which is the power supply ripple compensation control, does not operate as expected, it is possible to take appropriate measures.
  • the determination processing according to the first embodiment it is possible to determine whether or not the power supply ripple compensation control function is operating effectively, so it becomes easy to identify the faulty part in the power converter. Further, if only the power supply ripple compensation control function fails, it is possible to operate with limited functions, which is useful information for users and maintenance workers.
  • the first and second threshold values for determining whether or not the compensation operation by the first control, which is the power supply ripple compensation control, is normal are each the maximum capacitor voltage when the first control is not performed. It can be set based on a value and a minimum value. By using the first and second thresholds set in this manner, it is possible to appropriately determine whether the power supply ripple compensation control function is operating effectively. In addition, such a setting method is useful in the field of refrigeration cycle equipment where there are a wide variety of products with different current ratings.
  • Embodiment 2 a threshold setting method different from that in the first embodiment will be described.
  • the operation of the second embodiment can be performed by a configuration unit that is the same as or equivalent to the power conversion device 1 shown in FIG. 1 and the control unit 400 shown in FIG.
  • FIG. 8 is a diagram for explaining a threshold setting method according to the second embodiment.
  • the left side of FIG. 8 shows the temporal change waveform of the capacitor voltage Vdc when the power supply ripple compensation control is not performed.
  • the right side of FIG. 8 shows the time-varying waveform of the capacitor voltage Vdc when the power supply ripple compensation control is being performed.
  • the third threshold c is determined based on the pulsation width of the capacitor voltage Vdc when power supply pulsation compensation control is not performed.
  • the pulsation width referred to here is the absolute value of the difference between the instantaneous value of the capacitor voltage Vdc and the average value of the capacitor voltage Vdc . It is desirable to set the threshold value c individually for each product or model.
  • the set threshold value c can be stored in memory 422 or processing circuit 423 .
  • the ripple width of the capacitor voltage Vdc when the power supply ripple compensation control is performed is more reliable than the ripple width of the capacitor voltage Vdc when the power supply ripple compensation control is not performed. becomes smaller. Therefore, the instantaneous value of the capacitor voltage Vdc when the power supply ripple compensation control is performed is based on the threshold c set based on the ripple width of the capacitor voltage Vdc when the power supply ripple compensation control is not performed. is determined as a threshold value, it can be appropriately determined whether or not the compensation operation by the power supply ripple compensation control is normal.
  • FIG. 9 is a flowchart for explaining the operation of the control unit 400 according to the second embodiment.
  • the control unit 400 reads the threshold c from the memory 422 or the processing circuit 423 (step S31).
  • the control unit 400 acquires the detected value of the capacitor voltage Vdc from the voltage detection unit 503 (step S32).
  • the control unit 400 calculates the peak value and average value of the capacitor voltage Vdc based on the acquired detection values (step S33).
  • Control unit 400 calculates the pulsation width from the peak value and average value of capacitor voltage Vdc (step S34).
  • the control unit 400 compares the pulsation width calculated in step S34 with the threshold value c (step S35).
  • step S34 determines that the power supply pulsation compensation control function is normal (step S37). Henceforth, it returns to step S32 and the process from step S32 is repeated.
  • step S34 determines that the power supply pulsation compensation control function is not normal (step S38). In this case, the control unit 400 performs control to decrease the driving rotation speed of the motor 314 (step S39). Henceforth, it returns to step S32 and the process from step S32 is repeated.
  • step S39 If control is performed in step S39 to reduce the driving rotation speed of the motor 314, it may be determined in the processing of steps S36 and S37 that the power supply ripple compensation control function is normal. In this case, the driving rotation speed of the motor 314 is returned to the instructed rotation speed, and the process of FIG. 9 is executed again. In addition, when it is determined that the power supply pulsation compensation control function is not normal, the operation of the power converter 1 is stopped and the driving of the motor 314 is stopped.
  • step S36 "No” is determined when the pulsation width and the threshold c are equal, but “Yes” may be determined. That is, when the pulsation width is larger than the threshold value c, it may be determined that the power supply pulsation compensation control function is not normal.
  • the pulsation width is calculated as the absolute value of the difference between the instantaneous value of the capacitor voltage Vdc and the average value of the capacitor voltage Vdc , but it is not limited to this example.
  • the pulsation width may be obtained by calculating the effective value obtained by averaging the square of the difference between the instantaneous value of the capacitor voltage and the average value of the capacitor voltage, as shown in the following equation (1).
  • the pulsation width is "the absolute value of the difference between the instantaneous value of the capacitor voltage Vdc and the average value of the capacitor voltage Vdc ", for example, if the instantaneous value increases even once due to noise, there is a concern that the pulsation width will increase.
  • the effective value calculation is performed by integrating and averaging over an arbitrary time, as in the above formula (1), the calculated value will increase when the situation where the instantaneous value is large continues, so that accidental noise will not occur. You can limit the impact. Therefore, if the pulsation width is calculated using the above equation (1), a more accurate threshold value can be obtained, so that it is possible to improve the accuracy of determining whether or not the power supply pulsation compensation control function is normal. It becomes possible.
  • the third threshold for determining whether or not the compensation operation by the first control which is the power supply ripple compensation control, is normal can be determined based on the absolute value of the difference between the instantaneous value of the capacitor voltage when the first control is not performed and the average value of the capacitor voltage when the first control is not performed.
  • the third threshold value set in this manner it is possible to appropriately determine whether or not the power supply ripple compensation control function is operating effectively.
  • such a setting method is useful in the field of refrigeration cycle equipment where there are a wide variety of products with different current ratings.
  • the third threshold may be set based on the effective value obtained by averaging the square of the difference between the instantaneous value of the capacitor voltage and the average value of the capacitor voltage over an arbitrary period of time.
  • Embodiment 3 describes a determination method using a threshold different from those in Embodiments 1 and 2.
  • FIG. The operation of the third embodiment can be performed by a configuration unit that is the same as or equivalent to the power conversion device 1 shown in FIG. 1 and the control unit 400 shown in FIG.
  • FIG. 10 is a flowchart for explaining the operation of the control unit 400 according to the third embodiment.
  • the control unit 400 reads the threshold value d, which is the fourth threshold value, from the memory 422 or the processing circuit 423 (step S41).
  • the threshold d is a threshold set based on the capacitor current I3 when the power supply ripple compensation control is not performed.
  • the control unit 400 acquires the detected value of the capacitor voltage Vdc from the voltage detection unit 503 (step S42).
  • the control unit 400 calculates the capacitor current I3 based on the acquired detection value and the capacitance C of the capacitor 210 (step S43). Specifically, the capacitor current I3 can be calculated based on the capacitor voltage Vdc and the capacitance C of the capacitor 210 using the following equation (2).
  • the control unit 400 compares the capacitor current I3 calculated in step S43 with the threshold value d (step S44). If the capacitor current I3 calculated in step S43 is smaller than the threshold value d (step S45, Yes), the control unit 400 determines that the power supply ripple compensation control function is normal (step S46). Henceforth, it returns to step S42 and the process from step S42 is repeated.
  • step S45, No determines that the power supply ripple compensation control function is not normal (step S47). In this case, the control unit 400 performs control to reduce the driving rotation speed of the motor 314 (step S48). Henceforth, it returns to step S42 and the process from step S42 is repeated.
  • step S48 If control is performed in step S48 to reduce the drive rotation speed of the motor 314, it may be determined in the processing of steps S45 and S46 that the power supply ripple compensation control function is normal. In this case, the driving rotation speed of the motor 314 is returned to the instructed rotation speed, and the process of FIG. 10 is executed again. In addition, when it is determined that the power supply pulsation compensation control function is not normal, the operation of the power converter 1 is stopped and the driving of the motor 314 is stopped.
  • step S45 "No” is determined when the capacitor current I3 and the threshold value d are equal, but “Yes” may be determined. That is, when the capacitor current I3 is larger than the threshold value d, it may be determined that the power supply ripple compensation control function is not normal.
  • the fourth threshold for determining whether or not the compensation operation by the first control, which is the power supply ripple compensation control, is normal can be set based on the instantaneous value of the capacitor voltage when the second control is not performed and the capacitor current when the first control is not performed. Also, this capacitor current can be calculated based on the detected value of the capacitor voltage and the capacitance of the capacitor.
  • FIG. 11 is a diagram showing a configuration example of a power converter 1A according to the fourth embodiment.
  • a current detector 504 that detects the capacitor current I3 is added.
  • 2 A of motor drive apparatuses are comprised by 1 A of power converters, and the motor 314 with which the compressor 315 is provided.
  • Other configurations are the same as or equivalent to those of the power conversion device 1 shown in FIG. 1, and the same or equivalent components are denoted by the same reference numerals, and overlapping descriptions are omitted.
  • the current detection unit 504 may be simply referred to as a "detection unit".
  • FIG. 12 is a flowchart for explaining the operation of the control unit 400 according to the fourth embodiment.
  • the control unit 400 reads the threshold value d, which is the fourth threshold value, from the memory 422 or the processing circuit 423 (step S51).
  • Threshold d is a threshold set based on capacitor current I3 when power supply ripple compensation control is not performed, as in the third embodiment.
  • the control unit 400 acquires the detected value of the capacitor current I3 from the current detection unit 504 (step S52).
  • the control unit 400 compares the detected value of the capacitor current I3 acquired in step S52 with the threshold value d (step S53). If the capacitor current I3 is smaller than the threshold value d (step S54, Yes), the control unit 400 determines that the power supply ripple compensation control function is normal (step S55). Henceforth, it returns to step S52 and the process from step S52 is repeated.
  • step S54 determines that the power supply ripple compensation control function is not normal (step S56). In this case, the control unit 400 performs control to reduce the driving rotation speed of the motor 314 (step S57). Henceforth, it returns to step S52 and the process from step S52 is repeated.
  • step S57 If control is performed in step S57 to reduce the driving rotation speed of the motor 314, it may be determined in the processing of steps S54 and S55 that the power supply ripple compensation control function is normal. In this case, the driving rotation speed of the motor 314 is returned to the instructed rotation speed, and the process of FIG. 12 is executed again. In addition, when it is determined that the power supply ripple compensation control function is not normal, the operation of the power conversion device 1A is stopped and the driving of the motor 314 is stopped.
  • step S54 "No” is determined when the detected value of the capacitor current I3 and the threshold value d are equal, but “Yes” may be determined. That is, when the detected value of the capacitor current I3 is larger than the threshold value d, it may be determined that the power supply ripple compensation control function is not normal.
  • the fourth threshold for determining whether or not the compensation operation by the first control, which is the power supply ripple compensation control, is normal can be set based on the detected value of the capacitor current when the control of is not performed.
  • the fourth threshold value set in this way it becomes possible to appropriately determine whether or not the power supply ripple compensation control function is operating effectively.
  • such a setting method is useful in the field of refrigeration cycle equipment where there are a wide variety of products with different current ratings.
  • FIG. 13 is a diagram showing a configuration example of a refrigeration cycle equipment 900 according to Embodiment 5.
  • a refrigerating cycle-applied equipment 900 according to the fifth embodiment includes the power converter 1 described in the first to third embodiments.
  • the refrigerating cycle applied equipment 900 according to Embodiment 1 can be applied to products equipped with a refrigerating cycle, such as air conditioners, refrigerators, freezers, and heat pump water heaters.
  • constituent elements having functions similar to those of the first to third embodiments are assigned the same reference numerals as those of the first to third embodiments.
  • Refrigerating cycle applied equipment 900 includes compressor 315 incorporating motor 314 according to Embodiment 1, four-way valve 902, indoor heat exchanger 906, expansion valve 908, and outdoor heat exchanger 910 with refrigerant pipe 912. attached through
  • a compression mechanism 904 that compresses the refrigerant and a motor 314 that operates the compression mechanism 904 are provided inside the compressor 315 .
  • the refrigeration cycle applied equipment 900 can perform heating operation or cooling operation by switching operation of the four-way valve 902 .
  • the compression mechanism 904 is driven by a variable speed controlled motor 314 .
  • the refrigerant is pressurized by the compression mechanism 904 and sent out through the four-way valve 902, the indoor heat exchanger 906, the expansion valve 908, the outdoor heat exchanger 910, and the four-way valve 902. Return to compression mechanism 904 .
  • the refrigerant is pressurized by the compression mechanism 904 and sent through the four-way valve 902, the outdoor heat exchanger 910, the expansion valve 908, the indoor heat exchanger 906, and the four-way valve 902. Return to compression mechanism 904 .
  • the indoor heat exchanger 906 acts as a condenser to release heat, and the outdoor heat exchanger 910 acts as an evaporator to absorb heat.
  • the outdoor heat exchanger 910 acts as a condenser to release heat, and the indoor heat exchanger 906 acts as an evaporator to absorb heat.
  • the expansion valve 908 reduces the pressure of the refrigerant to expand it.
  • Embodiment 5 has been described as including the power converter 1 described in Embodiments 1 to 3, it is not limited to this.
  • a power converter 1A shown in FIG. 11 may be provided.
  • a power converter other than the power converters 1 and 1A may be used as long as the control methods of the first to fourth embodiments can be applied.
  • 1, 1A power conversion device, 2, 2A motor drive device, 110 commercial power supply, 120 reactor, 130 rectification section, 131 to 134 rectification element, 200 smoothing section, 210 capacitor, 310 inverter, 311a to 311f switching element, 312a to 312f Freewheeling diode, 313a, 313b, 501, 502, 504 current detection unit, 314 motor, 315 compressor, 383 subtraction unit, 384 to 387 Fourier coefficient calculation unit, 388 to 391 PID control unit, 392 AC restoration unit, 400 control unit , 401 rotor position estimation unit, 402 speed control unit, 403 flux-weakening control unit, 404 current control unit, 405, 406 coordinate conversion unit, 407 PWM signal generation unit, 408 q-axis current pulsation calculation unit, 409 addition unit, 420 Processor, 422 memory, 423 processing circuit, 424 interface, 503 voltage detection unit, 900 refrigeration cycle application equipment, 902 four-way valve, 904 compression mechanism, 90

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PCT/JP2021/044279 2021-12-02 2021-12-02 電力変換装置、モータ駆動装置及び冷凍サイクル適用機器 Ceased WO2023100321A1 (ja)

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US18/696,598 US20240380350A1 (en) 2021-12-02 2021-12-02 Power converter, motor drive apparatus, and refrigeration cycle applied apparatus
PCT/JP2021/044279 WO2023100321A1 (ja) 2021-12-02 2021-12-02 電力変換装置、モータ駆動装置及び冷凍サイクル適用機器

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JP2003250300A (ja) * 1997-10-31 2003-09-05 Hitachi Ltd 電気車の駆動装置及び電気車駆動用インバータの制御方法
JP2015061336A (ja) * 2013-09-17 2015-03-30 富士電機株式会社 永久磁石形同期電動機の制御装置
JP2016021785A (ja) * 2014-07-11 2016-02-04 シャープ株式会社 モータ制御装置及び冷凍・空調装置
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JPH11178388A (ja) * 1997-12-09 1999-07-02 Fujitsu General Ltd ブラシレスモータの制御方法
JP2015061336A (ja) * 2013-09-17 2015-03-30 富士電機株式会社 永久磁石形同期電動機の制御装置
JP2016021785A (ja) * 2014-07-11 2016-02-04 シャープ株式会社 モータ制御装置及び冷凍・空調装置
JP2017153236A (ja) * 2016-02-24 2017-08-31 株式会社Ｓｏｋｅｎ 電力変換器
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