WO2022183537A1 - 五相永磁容错电机矢量与直接转矩控制驱动系统的开路统一容错控制方法 - Google Patents
五相永磁容错电机矢量与直接转矩控制驱动系统的开路统一容错控制方法 Download PDFInfo
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
- H02P21/22—Current control, e.g. using a current control loop
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
- H02P21/06—Rotor flux based control involving the use of rotor position or rotor speed sensors
- H02P21/10—Direct field-oriented control; Rotor flux feed-back control
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
- H02P21/0003—Control strategies in general, e.g. linear type, e.g. P, PI, PID, using robust control
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
- H02P21/0003—Control strategies in general, e.g. linear type, e.g. P, PI, PID, using robust control
- H02P21/0017—Model reference adaptation, e.g. MRAS or MRAC, useful for control or parameter estimation
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
- H02P21/05—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation specially adapted for damping motor oscillations, e.g. for reducing hunting
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
- H02P21/24—Vector control not involving the use of rotor position or rotor speed sensors
- H02P21/28—Stator flux based control
- H02P21/30—Direct torque control [DTC] or field acceleration method [FAM]
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P25/00—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details
- H02P25/16—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details characterised by the circuit arrangement or by the kind of wiring
- H02P25/22—Multiple windings; Windings for more than three phases
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P29/00—Arrangements for regulating or controlling electric motors, appropriate for both AC and DC motors
- H02P29/02—Providing protection against overload without automatic interruption of supply
- H02P29/024—Detecting a fault condition, e.g. short circuit, locked rotor, open circuit or loss of load
- H02P29/028—Detecting a fault condition, e.g. short circuit, locked rotor, open circuit or loss of load the motor continuing operation despite the fault condition, e.g. eliminating, compensating for or remedying the fault
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
- Y02T10/00—Road transport of goods or passengers
- Y02T10/60—Other road transportation technologies with climate change mitigation effect
- Y02T10/72—Electric energy management in electromobility
Definitions
- the invention belongs to the technical field of multi-phase motor fault-tolerant control, and in particular relates to an open-circuit unified fault-tolerant control method for a five-phase permanent magnet fault-tolerant motor vector and direct torque control drive system.
- Multi-phase permanent magnet motors have the advantages of high efficiency, high power density, wide speed regulation range, low torque ripple and strong fault tolerance, and have been widely concerned and applied in electric vehicles, hybrid vehicles and other electric drive fields.
- Vector control (VC) and direct torque control (DTC) have attracted much attention due to their high driving performance.
- VC Vector control
- DTC direct torque control
- the failure of the motor drive system will affect the normal operation of the entire application system, and even cause a safety accident. Therefore, it is of great practical significance to study the fault-tolerant control of the multi-phase permanent magnet motor drive system and improve the reliability of the motor drive system.
- the document "Fault-tolerant direct torque control of five-phase FTFSCW-IPM motor based on analogous three-phase SVPWM for electric vehicle applications” (IEEE Transaction on Vehicular Technology, 2017) aims at five One-phase open-circuit fault of phase permanent magnet motor, the corresponding SVPWM fault-tolerant control method is proposed, which overcomes the shortcomings of the fault-tolerant control system based on hysteresis control.
- this type of fault-tolerant control strategy is based on the voltage vector reconstruction after the fault, and the algorithm is relatively complex , is not conducive to engineering.
- the present invention proposes an open-circuit unified fault-tolerant control method based on a CPWM-based five-phase permanent magnet fault-tolerant motor vector and direct torque control drive system, starting from essentially revealing the fault-tolerant mechanism. Improve the stable operation ability of the motor drive system, so that the control system not only has good open-circuit fault fault-tolerant operation performance, but also has good dynamic and static performance, anti-interference ability and robustness, and can be applied to various new control algorithms. Minimize reconfiguration of the control system and save controller CPU memory resources under different faults.
- the technical solution adopted in the present invention is: an open-circuit unified fault-tolerant control method for a five-phase permanent magnet fault-tolerant motor vector and direct torque control drive system, comprising the following steps:
- Step 1) establishing the current mathematical model of the five-phase permanent magnet fault-tolerant motor during normal operation
- the five-phase permanent magnet fault-tolerant motor runs under normal operating conditions, and the expressions of its currents i A , i B , i C , i D and i E are as follows:
- ⁇ 72°
- ⁇ is the rotor position electrical angle
- i d1 * , i q1 * are the direct-axis and quadrature-axis components of the fundamental current given value
- id3 * , i q3 * are the third harmonic current given values Direct axis and quadrature axis components
- Step 2) Obtain the fault-tolerant current of one-phase open circuit, non-adjacent two-phase open circuit and adjacent two-phase open circuit, and analyze the fault-tolerant mechanism;
- Step 3 Use the difference between the given speed and the detected actual speed to construct a high-quality torque controller to obtain a high-quality torque given T e * , so as to suppress the motor torque ripple after the fault, and at the same time, the load disturbance, the system Parameter changes and electromagnetic torque ripple factors caused by faults are taken into account;
- Step 4) Detect the five-phase currents i A , i B , i C , i D and i E of the five-phase permanent magnet fault-tolerant motor, and obtain the current components i d1 , i q1 , i q1 , i d3 , i q3 ;
- the current component in the two-phase rotating coordinate system of the five-phase permanent magnet fault-tolerant motor is expressed as:
- Step 5 Utilize the current components i d1 , i q1 and the high-quality torque given T e * under the two-phase rotating coordinate system to calculate the quadrature-axis fundamental wave voltage of the vector control VC drive system and the direct torque control DTC drive system ;
- Step 6 Based on the third harmonic current zero control strategy, use the current components i d3 and i q3 under the two-phase rotating coordinate system to obtain the third harmonic voltage of the AC-direction axis;
- Step 7) Calculate the phase voltage of the winding under the fault mode based on the fault-tolerant mechanism and the AC-DC axis voltage;
- Step 8) According to the back EMF of the motor and the winding phase voltage in the fault mode, obtain the given phase voltage of the five-phase winding in the fault-tolerant operation mode;
- Step 9) The five-phase winding is given a five-phase voltage command through the voltage source inverter, and the pulse width modulation CPWM mode is adopted to realize the disturbance-free operation of the five-phase permanent magnet fault-tolerant motor VC and the DTC drive system under any open-circuit fault condition.
- the present invention proposes a unified fault-tolerant control strategy for open-circuit faults suitable for VC and DTC drive systems for the first time, which essentially reveals the fault-tolerant mechanism.
- the fault-tolerant operation of the system in different open-circuit fault states is realized, thereby solving the problem that the fault-tolerant control schemes corresponding to various new basic control algorithms will also change and become complicated.
- the invention is based on the design of high-quality torque controller, so that the control system still has high-quality output torque even under open-circuit fault, and at the same time has good dynamic and static performance, anti-interference ability and robustness under normal and fault operation.
- the performance of the motor drive system is comprehensively improved.
- the present invention realizes the disturbance-free operation in the case of open-circuit fault based on the pulse width modulation CPWM method, which can effectively solve the problems of high current harmonic content, large torque ripple and low switching frequency caused by the traditional fault-tolerant control method based on hysteresis comparator.
- the traditional fault-tolerant control is generally based on the technical restraint of ensuring that the magnetomotive force before and after the fault is equal to the fundamental wave component of the AC-DC axis current, and the action mechanism of the third-harmonic AC-DC axis current before and after the fault is considered to ensure that the stator flux linkage track is a circle At the same time, the current quality under fault-tolerant operation is further improved.
- the current component is zero, which solves the problem of large loss of the motor under sudden load or fault operating conditions, and effectively improves the efficiency of the motor drive system.
- the proposed method has a small amount of calculation, is simple and easy to implement, and is beneficial to the engineering and practical application of the new theory.
- FIG. 1 is a schematic structural diagram of a five-phase permanent magnet fault-tolerant motor of the present invention
- FIG. 2 is a schematic block diagram of a unified fault-tolerant control strategy for open-circuit faults according to the present invention
- Figure 3 shows the current vector diagrams in normal and fault-tolerant operation;
- (a) is the current vector diagram in normal operation;
- (b) is the current vector diagram in the case of an open-circuit fault of phase A;
- (c) is the non-adjacent phase A , the current vector diagram of C two-phase open-circuit fault;
- (d) is the current vector diagram of the adjacent phase A, B two-phase open-circuit fault;
- Fig. 4 is the structural block diagram of the fault-tolerant control drive system of five-phase permanent magnet fault-tolerant motor based on CPWM of the present invention; (a) fault-tolerant VC drive system; (b) fault-tolerant DTC drive system;
- Fig. 5 is the simulation waveform of the DTC drive system when the load and system parameters are changed under normal working conditions of the present invention; (a) current waveform; (b) torque waveform; (c) rotational speed waveform; (d) stator flux linkage amplitude value waveform; (e) AC and direct axis current waveform;
- Fig. 6 is the simulation waveform of the VC drive system of the present invention under normal operation, A, C two-phase open-circuit fault without fault-tolerant operation and fault-tolerant operation; (a) current waveform; (b) torque waveform; (c) rotational speed waveform ;
- Fig. 7 is the simulation waveform of the DTC drive system of the present invention under normal operation, A and C two-phase open-circuit fault without fault-tolerant operation and fault-tolerant operation; (a) current waveform; (b) torque waveform; (c) rotational speed waveform ; (d) Amplitude waveform of stator flux linkage;
- FIG. 8 is a simulation waveform of the DTC drive system of the present invention under normal operation, non-fault-tolerant operation under A-phase open-circuit fault, and fault-tolerant operation.
- Fig. 9 is the simulation waveform of the DTC drive system of the present invention under normal operation, A and B two-phase open-circuit fault without fault-tolerant operation and fault-tolerant operation; (a) current waveform; (b) torque waveform; (c) rotational speed waveform .
- the control object of the present invention is a schematic structural diagram of a five-phase permanent magnet fault-tolerant motor, including a stator, a rotor, a permanent magnet, an armature tooth, a fault-tolerant tooth, and an armature winding;
- the circumferential intervals of the rings are evenly distributed, and the tooth width of the armature teeth and the tooth width of the fault-tolerant teeth are not equal;
- the armature teeth are wound with armature winding coils, which are single-layer concentrated windings, and between two adjacent single-layer concentrated windings It is isolated by fault-tolerant teeth;
- the permanent magnets are embedded in the rotor, which is distributed in a "V" shape; the total number of teeth of the armature teeth and fault-tolerant teeth is 20, and the number of poles of the permanent magnet is 18; because the stator adopts a single-layer concentrated winding, it is greatly reduced.
- the magnetic resistance of the motor's direct-axis magnetic circuit reduces the salient pole rate of the motor, making the inductance of the motor's direct-axis nearly equal; the stator part is provided with fault-tolerant teeth, which can effectively realize the electrical, magnetic and thermal isolation between the windings of each phase, and has a strong Fault tolerance performance.
- the principle block diagram of the unified fault-tolerant control strategy for open-circuit faults of the present invention includes obtaining high-quality torque reference, obtaining AC and DC axis reference voltage, analyzing the fault-tolerant mechanism to obtain fault-tolerant current, and obtaining fault winding voltage based on the fault-tolerant mechanism. Based on the back EMF to obtain the fault tolerance voltage.
- the specific implementation steps of the open-circuit fault unified fault-tolerant control strategy principle of the present invention include:
- Step 1) Establish a current mathematical model of the five-phase permanent magnet fault-tolerant motor during normal operation.
- the five-phase permanent magnet fault-tolerant motor runs under normal operating conditions, and its current expression is as follows:
- ⁇ 72°
- ⁇ is the rotor position electrical angle
- i d1 * , i q1 * are the direct-axis and quadrature-axis components of the fundamental current given value
- id3 * , i q3 * are the third harmonic current given values Direct and quadrature axis components.
- Step 2 Obtain fault-tolerant currents in different fault modes (one-phase open circuit, non-adjacent two-phase open circuit, and adjacent two-phase open circuits), and analyze the fault-tolerant mechanism.
- the magnetomotive force expression of the five-phase permanent magnet fault-tolerant motor under normal operating conditions is:
- MMF 1 Ni A + ⁇ Ni B + ⁇ 2 Ni C + ⁇ 3 Ni D + ⁇ 4 Ni E (2)
- ⁇ cos ⁇ +jsin ⁇ ; N is the number of winding turns; i A , i B , i C , i D , i E are the A, B, C, D, and E phase currents of the motor during normal operation.
- MMF 2 ⁇ Ni B1 + ⁇ 2 Ni C1 + ⁇ 3 Ni D1 + ⁇ 4 Ni E1 (3)
- i B1 , i C1 , i D1 , i E1 are the B, C, D, and E phase currents when the A phase fails.
- the fault-tolerant current under the open-circuit fault of the adjacent two-phase and non-adjacent two-phase can be calculated separately. It is worth noting that when a two-phase open-circuit fault occurs, there will be no third harmonic current in the five-phase permanent magnet fault-tolerant motor, so it can be ignored.
- the fault-tolerant current after non-adjacent (A, C) two-phase open-circuit fault is:
- i B2 , i D2 , i E2 are the B, D, and E phase currents when the A and C phases are faulty.
- the fault-tolerant current after the adjacent (A, B) two-phase open-circuit fault is:
- i C3 , i D3 , i E3 are the C, D, and E phase currents when the A and B phases are faulty.
- the current vector diagrams in normal and fault-tolerant operation are obtained accordingly, as shown in Figure 3, it can be found that in the fault-tolerant mode, the fault current vector is zero, the phase of the non-fault phase current vector is shifted and the magnitude increases responsively. Therefore, when the five-phase permanent magnet fault-tolerant motor fails, the corresponding fault-tolerant control strategy is used to ensure that the winding current satisfies the relationship in Figure 3, and the motor can run without disturbance under different faults, that is, the five-phase permanent magnet fault-tolerant motor drive system fault. fault tolerance mechanism.
- Step 3 Use the difference between the given speed and the detected actual speed to construct a high-quality torque controller to obtain a high-quality torque given T e * , so as to suppress the motor torque ripple after the fault, and at the same time, the load disturbance, the system Factors such as parameter changes and electromagnetic torque ripple caused by faults are taken into account.
- ⁇ is the mechanical angular velocity
- B is the friction coefficient
- J is the moment of inertia
- T L is the load torque
- T b represents the non-pulsating component of the electromagnetic torque
- ⁇ T e represents the pulsating component of the electromagnetic torque caused by the fault. Therefore, T b is designed to guarantee the system performance of the five-phase motor, and ⁇ T e is considered as the uncertainty factor of the system.
- the high-quality torque control strategy can eliminate the disturbance ⁇ T e , so the torque ripple of the five-phase permanent magnet fault-tolerant motor can be suppressed after the fault.
- equation (7) can be rewritten as:
- the high-quality torque controller is designed as:
- T m is the maximum value of TL and is greater than zero; ⁇ is a constant greater than zero.
- the constructed high-quality torque controller comprehensively considers factors such as load disturbance (T L ), system parameter changes (J and B), and electromagnetic torque ripple ( ⁇ T e ) caused by faults.
- the torque controller can not only suppress the electromagnetic torque ripple caused by faults, but also has good anti-interference performance against uncertain factors such as load disturbance and system parameter changes.
- Step 4) Detect the five-phase currents i A , i B , i C , i D and i E of the five-phase permanent magnet fault-tolerant motor, and obtain the current components i d1 , i q1 , i q1 , i d3 , i q3 .
- the current component in the two-phase rotating coordinate system of the five-phase permanent magnet fault-tolerant motor is expressed as:
- Step 5 Using the current components i d1 , i q1 and the high-quality torque given T e * in the two-phase rotating coordinate system to calculate the quadrature-axis fundamental wave voltage of the VC drive system and the DTC drive system.
- the given voltage of quadrature fundamental wave of VC drive system is acquired.
- Figure 4(a) shows the fault-tolerant VC drive system.
- the specific implementation steps for obtaining the quadrature fundamental wave given voltage of the VC drive system include:
- the given direct-axis voltage u d1 * is obtained after the difference between the given direct-axis current zero and the direct-axis current id1 through the PI regulator;
- the quadrature axis current i q1 * can be obtained by the following formula:
- pr is the number of pole pairs of the motor
- ⁇ f is the amplitude of the permanent magnet flux linkage
- the given voltage of quadrature fundamental wave of DTC drive system is acquired.
- Figure 4(b) shows the fault-tolerant DTC drive system.
- the specific implementation steps of obtaining the quadrature fundamental wave given voltage of the DTC drive system include:
- L s is the stator inductance
- the magnitude and phase of the stator flux linkage can be obtained as:
- the essence of the electromagnetic torque of the five-phase permanent magnet motor is the result of the interaction between the rotor magnetic field and the stator magnetic field, namely:
- ⁇ is the angle between the stator flux linkage and the rotor flux linkage, that is, the phase angle of the stator flux linkage.
- the present invention compares the direct-axis current i d1 with zero, and then uses the PI regulator as the stator flux linkage. Therefore, the given stator flux linkage can be adaptively adjusted according to the load conditions to ensure The direct-axis current component of the motor running under different working conditions is zero.
- Step 6 Based on the third harmonic current zero control strategy, the current components i d3 and i q3 in the two-phase rotating coordinate system are used to obtain the third harmonic voltage of the AC-direction axis.
- the current components i d3 and i q3 in the two-phase rotating coordinate system are compared with zero, respectively, and then the corresponding third harmonic voltage of the AC and DC axes is obtained after passing through the PI regulator.
- Step 7) Calculate the winding phase voltage in the fault mode based on the fault tolerance mechanism and the AC-DC axis voltage.
- phase voltage expression of the five-phase permanent magnet fault-tolerant motor is:
- i x is the phase current
- e x is the opposite potential.
- the winding phase voltage expression under A-phase winding fault is:
- u Ae3 , u Be3 , u Ce3 , u De3 , and u Ee3 are the phase voltages of the five-phase windings without considering the back EMF when the A and B two-phase windings fail.
- Step 8) According to the back EMF of the motor and the winding phase voltage in the fault mode, obtain the given phase voltage of the five-phase winding in the fault-tolerant operation mode.
- the back EMF under the open-circuit fault of the five-phase permanent magnet fault-tolerant motor is consistent with the back EMF during normal operation. Due to the small change in the amplitude of the permanent magnet flux linkage of the five-phase permanent magnet fault-tolerant motor and the small harmonic content of the back EMF, its reverse The electric potential can be expressed as:
- ⁇ f is the amplitude of the permanent magnetic flux linkage
- ⁇ e is the electrical angular velocity
- the given fault-tolerant phase voltage expression under the two-phase winding fault of A and C is:
- the given fault-tolerant phase voltage expression under the two-phase winding fault of A and B is:
- Step 9) The five-phase winding is given a five-phase voltage command through the voltage source inverter, and the pulse width modulation CPWM method is used to realize the disturbance-free operation of the five-phase permanent magnet fault-tolerant motor VC and the DTC drive system under any open-circuit fault condition.
- Figure 5 shows the simulation results of the operation when the load and system parameters are changed under normal conditions.
- the operating conditions of the motor are as follows: the speed is 800r/min, the initial load is 2N ⁇ m, the sudden change to 8N ⁇ m in 0.3s, and the moment of inertia becomes twice the original. It can be found from the simulation results that the current of the drive system of the present invention is relatively sinusoidal; the sudden load and moment of inertia have little effect on the operation of the system, indicating that the present invention has better resistance to load disturbance and system parameter changes; in addition, during the entire operation process, The stator flux linkage can be adaptively changed to ensure that the direct axis current is zero and improve the motor efficiency.
- Figures 6 and 7 show the simulation results of the VC and DTC drive systems in the case of non-adjacent two-phase (A, C) open-circuit faults, respectively.
- the operating conditions of the motor are as follows: the speed is 500 r/min, the load is 5 N m, the motor failure time is 0.2 s, and the fault-tolerant control strategy is adopted at 0.3 s. It can be seen that after the fault occurs in 0.2s, the fault phase current becomes zero, the electromagnetic torque pulsation and flux linkage pulsation increase significantly, and the rotational speed begins to oscillate.
- FIGS. 8 to 9 show the simulation results of the DTC drive system in the case of one-phase (A) open-circuit fault and two adjacent two-phase (A, B) open-circuit faults, respectively. It can be seen that the effectiveness of the unified fault-tolerant control strategy is adopted after the fault.
- the present invention provides an open-circuit unified fault-tolerant control method for a five-phase permanent magnet fault-tolerant motor vector and direct torque control drive system.
- the invention essentially reveals the fault-tolerant mechanism, and based on the pulse width modulation CPWM mode, proposes a unified fault-tolerant control strategy for open-circuit faults suitable for vector control and direct torque control drive systems, and effectively solves the fault-tolerant control corresponding to various new basic control algorithms.
- the solution will also change and complicate the problem; at the same time, a high-quality torque controller is designed, so that the control system still has high-quality output torque even under open-circuit faults, and has good dynamic performance under normal and faulty operation.
- the static performance, anti-interference ability and robustness comprehensively improve the operation performance of the motor drive system; the present invention does not need to change the coordinate transformation and additional compensation voltage, that is, does not need to change the structure of the control system, only needs to change the control strategy of one of the modules , which can realize fault-tolerant operation under different faults, simplify the controller algorithm, minimize the reconstruction of the control system and save the controller CPU memory resources under different faults in the true sense; breaking through the traditional fault-tolerant control is generally based on the AC-DC-axis current base
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- 一种五相永磁容错电机矢量与直接转矩控制驱动系统的开路统一容错控制方法,其特征在于,包括如下步骤:步骤1)建立五相永磁容错电机正常运行时的电流数学模型;五相永磁容错电机运行于正常运行工况下,其电流i A、i B、i C、i D和i E表达式如下式所示:其中,γ=72°,θ为转子位置电角度,i d1 *、i q1 *为基波电流给定值直轴和交轴分量,i d3 *、i q3 *为三次谐波电流给定值直轴和交轴分量;步骤2)获取一相开路、非相邻两相开路和相邻两相开路的容错电流,分析容错机理;步骤3)利用给定转速与检测到的实际转速之差,构建高品质转矩控制器获取高品质转矩给定T e *,以抑制故障后的电机转矩脉动,同时将负载扰动、系统参数变化以及由故障引起的电磁转矩脉动因素均考虑进去;步骤4)检测五相永磁容错电机的五相电流i A、i B、i C、i D和i E,经Clark和Park变换得到两相旋转坐标系下的电流分量i d1、i q1、i d3、i q3;五相永磁容错电机的两相旋转坐标系下的电流分量表示为:步骤5)利用两相旋转坐标系下的电流分量i d1、i q1以及高品质转矩给定T e *,以计算矢量控制VC驱动系统和直接转矩控制DTC驱动系统的交直轴基波电压;步骤6)基于三次谐波电流为零控制策略,利用两相旋转坐标系下的电流分量i d3、i q3以获取交直轴三次谐波电压;步骤7)基于容错机理以及交直轴电压,计算故障模式下的绕组相电压;步骤8)根据电机反电势和故障模式下的绕组相电压,获取容错运行模式下的五相绕组给定相电压;步骤9)将五相绕组给定五相电压指令经电压源逆变器,采用脉宽调制CPWM方式实现五相永磁容错电机VC与DTC驱动系统任意开路故障情况下的无扰运行。
- 根据权利要求1所述的一种五相永磁容错电机矢量与直接转矩控制驱动系统的开路统一容错控制方法,其特征在于,所述步骤2)具体实现包括:五相永磁容错电机正常运行工况下磁动势表达式为:MMF 1=Ni A+ηNi B+η 2Ni C+η 3Ni D+η 4Ni E其中,η=cosγ+jsinγ;N为绕组匝数;i A、i B、i C、i D、i E为电机正常运行时的A、B、C、D、E相电流;当五相永磁容错电机发生单相开路故障时,假如为A相,故障相A相的电流为零,此时磁动势表达式为:MMF 2=ηNi B1+η 2Ni C1+η 3Ni D1+η 4Ni E1其中,i B1、i C1、i D1、i E1为A相故障时的B、C、D、E相电流;根据故障前后磁动势相等和故障容错电流幅值相等原则,同时考虑到三次谐波电流,可得A相发生开路后其余非故障相的电流分配情况,如下式所示:同理,利用故障前后磁动势相等原则,可分别计算得到相邻两相和非相邻两相开路故障下的容错电流,发生两相开路故障时,五相永磁容错电机将不存在三次谐波电流,故可将其忽略;非相邻(A、C)两相开路故障后的容错电流为:其中,i B2、i D2、i E2为A、C两相故障时的B、D、E相电流;相邻(A、B)两相开路故障后的容错电流为:其中,i C3、i D3、i E3为A、B两相故障时的C、D、E相电流;当五相永磁容错电机发生故障时,通过相应的容错控制策略保证绕组电流满足上述容错电流,可保证电机在不同故障下无扰运行,即为五相永磁容错电机驱动系统故障时的容错机理。
- 根据权利要求1所述的一种五相永磁容错电机矢量与直接转矩控制驱动系统的开路统一容错控制方法,其特征在于,所述步骤3)利用给定转速与检测到的实际转速之差,构建高品质转矩控制器获取高品质转矩给定T e *的具体过程包括:五相永磁容错电机转矩与转速之间关系为:其中,ω为机械角速度,B为摩擦系数,J为转动惯量,T L为负载转矩;对于五相永磁容错电机系统处于故障模式下,其电磁转矩的表达式为T e=T b+ΔT e其中,T b代表电磁转矩无脉动分量,ΔT e代表电磁转矩由故障引起的脉动分量,所以,设计T b以保证五相电机的系统性能,而将ΔT e被认为是系统的不确定性因素,采用高品质转矩控制策略可消除扰动ΔT e,故而可抑制五相永磁容错电机在故障后转矩脉动;假设ΔT e=α 1T b,其中,α 1未知,但是有界限,其最大值为α 1m,故α 1满足|α 1|≤α 1m<1,五相永磁容错电机转矩与转速之间的关系式可改写为:其中,B m和J m分别为B的最大值和J的最小值,并且大于零,可以根据电机系统极端环境得到相应的数值;α 2=1-(J m/J),α 2的取值范围为:0≤α 2<1,令e=ω-ω *,ω *为转子给定角速度,则:ω=e+ω *即而可得:根据强鲁棒控制规律,设计高品质转矩控制器为:
- 根据权利要求1所述的一种五相永磁容错电机矢量与直接转矩控制驱动系统的开路统一容错控制方法,其特征在于,所述步骤5)利用两相旋转坐标系下的电流分量i d1、i q1以及高品质转矩给定T e *,以计算VC驱动系统和DTC驱动系统的交直轴基波电压的具体实现包括:第一部分,VC驱动系统的交轴基波给定电压获取;(1.1)采用i d=0控制,给定直轴电流零与直轴电流i d1之差经PI调节器后得到直轴电压给定u d1 *;(1.2)获取交轴电流i q1 *,将i q1 *与直轴电流i q1之差经PI调节器后得到直轴电压给定u q1 *,交轴电流i q1 *可由下式得到:其中,p r为电机的极对数,ψ f为永磁磁链幅值;第二部分,DTC驱动系统的交轴基波给定电压获取;(2.1)利用上述两相旋转坐标系下的电流分量i d1、i q1来计算定子磁链大小、相位以及估算转矩;定子磁链的交直轴分量的表达式为:其中,L s为定子电感;由上式可得定子磁链幅值大小和相位,为:由于五相永磁容错电机的交直轴电感接近相等,其估算转矩可由下式得到:(2.2)将给定转矩T e *与计算转矩之差经转速PI调节器后得到转矩角增量Δδ,并通过磁链自适应给定控制策略得到定子磁链的给定值ψ s *;五相永磁电机的电磁转矩本质是转子磁场与定子磁场相互作用的结果,即有:对上式两边求导,得:故转矩偏差ΔT e与转矩角增量Δδ之间具有非线性关系,因此,转矩角Δδ可由ΔT e通过PI调节器后得到;另外,定子磁链给定若为定值,当电机空载或突加重载运行时,需要额外的直轴电流分量来维持定子磁链不变;发明将直轴电流i d1与零作差比较后经PI调节器作为定子磁链给定,因此,给定的定子磁链可根据负载情况进行自适应地调节,以确保电机运行于不同工况下的直轴电流分量为零;(2.3)将定子磁链大小和相位、转矩角增量Δδ以及定子磁链的给定值ψ s *通过预期电压计算,得到两相旋转坐标系上的交直轴基波电压参考值u d1 *和u q1 *;根据五相永磁容错电机交直轴电压方程,R s为定子电阻,得到交直轴基波电压参考值的表达式为
- 根据权利要求1所述的一种五相永磁容错电机矢量与直接转矩控制驱动系统的开路统一容错控制方法,其特征在于,所述步骤6)的具体实现方式是将两相旋转坐标系下的电流分量i d3、i q3分别与零作差比较后经PI调节器后得到相应的交直轴三次谐波电压。
- 根据权利要求1所述的一种五相永磁容错电机矢量与直接转矩控制驱动系统的开路统一容错控制方法,其特征在于,所述步骤7)的具体实现包括:五相永磁容错电机的相电压表达式为:其中,x=A,B,C,D,E,R s为定子电阻,i x为相电流,e x为相反电势;则上式可改写为:当五相容错电机发生故障,上式可用交直轴电压的形式表示,则可得不同故障下的绕组相电压表达式,A相绕组故障下的绕组相电压表达式为:并且,u A1=0,其中,u Ae1、u Be1、u Ce1、u De1、u Ee1为A相绕组故障时未考虑反电势情况下的五相绕组相电压;u ed1 *=u d1 *-e d1 *,u eq1 *=u q1 *-e q1 *;u ed3 *=u d3 *-e d3 *,u eq1 *=u q3 *-e q3 *;e d1 *、e q1 *、e d3 *、e q3 *分别为五相反电势交直轴分量,可通过相反电势经过五相静止坐标系到两相旋转坐标系的坐标变换矩阵得到;A、C两相绕组故障下的绕组相电压表达式为:其中,u Ae2、u Be2、u Ce2、u De2、u Ee2为A、C两相绕组故障时未考虑反电势情况下的五相绕组相电压;A、B两相绕组故障下的绕组相电压表达式为:其中,u Ae3、u Be3、u Ce3、u De3、u Ee3为A、B两相绕组故障时未考虑反电势情况下的五相绕组相电压。
- 根据权利要求6所述的一种五相永磁容错电机矢量与直接转矩控制驱动系统的开路统一容错控制方法,其特征在于,所述步骤8)的具体实现包括:五相永磁容错电机开路故障下的反电势与正常运行时的反电势一致,由于五相永磁容错电机的永磁磁链幅值变化很小以及反电势的谐波含量很小,其五相反电势可表示为:其中,ψ f为永磁磁链幅值,ω为电角速度;将反电势代入五相永磁容错电机的相电压表达式,可得到不同故障模式下相应的容错电压给定值,A相绕组故障下的给定容错相电压表达式为:并且,u A *=e A;A、C两相绕组故障下的给定容错相电压表达式为:A、B两相绕组故障下的给定容错相电压表达式为:因此,只需已知五相永磁容错电机驱动系统的直轴电压u d *和交轴电压u q *,基于给定容错相电压表达式,即可实现该系统在电机绕组开路故障状态的容错运行。
- 根据权利要求1所述的一种五相永磁容错电机矢量与直接转矩控制驱动系统的开路统一容错控制方法,其特征在于,所述开路故障统一容错控制策略还适用于其他基于采用脉宽调制CPWM方式的驱动控制系统的开路故障容错运行。
- 根据权利要求1所述的一种五相永磁容错电机矢量与直接转矩控制驱动系统的开路统一容错控制方法,其特征在于,矢量与直接转矩控制驱动系统的开路统一容错控制方法还适用于五相永磁直线电机控制系统。
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---|---|---|---|---|
CN116633088A (zh) * | 2023-05-24 | 2023-08-22 | 南京航空航天大学 | 一种双凸极电机电流传感器零偏故障诊断和容错控制方法 |
CN117184219A (zh) * | 2023-08-31 | 2023-12-08 | 北京理工大学 | 一种用于线控转向系统的执行机构容错控制方法和装置 |
Families Citing this family (6)
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Citations (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US20160028343A1 (en) * | 2014-07-11 | 2016-01-28 | Seungdeog Choi | Fault tolerant control system for multi-phase permanent magnet assisted synchronous reluctance motors |
CN107276492A (zh) * | 2017-07-28 | 2017-10-20 | 江苏大学 | 基于容错矢量控制的五相永磁电机三次谐波电流注入方法 |
CN107565868A (zh) * | 2017-10-10 | 2018-01-09 | 东南大学盐城新能源汽车研究院 | 一种五相永磁同步电机开路故障下的容错控制系统及方法 |
CN108768223A (zh) * | 2018-05-29 | 2018-11-06 | 哈尔滨理工大学 | 基于定子铜耗最小的十二相永磁同步电机容错控制方法 |
CN110518859A (zh) * | 2019-08-14 | 2019-11-29 | 江苏大学 | 一种基于扰动观测器的五相永磁电机短路容错直接转矩控制方法 |
Family Cites Families (9)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
CN106208871B (zh) * | 2016-07-26 | 2018-12-14 | 江苏大学 | 五相永磁体内嵌式容错直线电机不相邻两相短路容错矢量控制方法 |
CN107222138B (zh) * | 2017-05-24 | 2019-05-31 | 江苏大学 | 一种考虑磁阻转矩的转矩脉动最小容错控制方法 |
CN108306571B (zh) | 2018-01-11 | 2019-12-31 | 江苏大学 | 一种五相永磁直线电机一相开路容错直接推力控制方法 |
CN110504889B (zh) | 2019-07-24 | 2021-06-22 | 江苏大学 | 一种五相永磁同步电机容错直接转矩控制方法 |
CN110829926B (zh) * | 2019-10-24 | 2021-03-23 | 江苏大学 | 一种用于五相永磁容错电机的svpwm容错控制方法及装置 |
CN111541409B (zh) * | 2020-04-09 | 2022-04-12 | 天津大学 | 基于调制函数的五相永磁同步电机单相开路故障svpwm控制方法 |
GB2599586B (en) * | 2020-10-27 | 2023-02-01 | Univ Jiangsu | Short-circuit fault-tolerant control method based on deadbeat current tracking for five-phase permanent magnet motor with sinusoidal back-electromotive |
CN112290859B (zh) * | 2020-10-27 | 2022-05-20 | 江苏大学 | 采用无差拍电流跟踪的五相永磁电机短路容错控制方法 |
CN113271048B (zh) * | 2021-03-02 | 2022-05-20 | 江苏大学 | 五相永磁容错电机控制驱动系统的开路统一容错控制方法 |
-
2021
- 2021-03-02 CN CN202110229844.3A patent/CN113271048B/zh active Active
- 2021-03-22 US US18/013,568 patent/US11888419B2/en active Active
- 2021-03-22 WO PCT/CN2021/082038 patent/WO2022183537A1/zh active Application Filing
- 2021-03-22 GB GB2200428.7A patent/GB2606611B/en active Active
Patent Citations (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US20160028343A1 (en) * | 2014-07-11 | 2016-01-28 | Seungdeog Choi | Fault tolerant control system for multi-phase permanent magnet assisted synchronous reluctance motors |
CN107276492A (zh) * | 2017-07-28 | 2017-10-20 | 江苏大学 | 基于容错矢量控制的五相永磁电机三次谐波电流注入方法 |
CN107565868A (zh) * | 2017-10-10 | 2018-01-09 | 东南大学盐城新能源汽车研究院 | 一种五相永磁同步电机开路故障下的容错控制系统及方法 |
CN108768223A (zh) * | 2018-05-29 | 2018-11-06 | 哈尔滨理工大学 | 基于定子铜耗最小的十二相永磁同步电机容错控制方法 |
CN110518859A (zh) * | 2019-08-14 | 2019-11-29 | 江苏大学 | 一种基于扰动观测器的五相永磁电机短路容错直接转矩控制方法 |
Cited By (4)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
CN116633088A (zh) * | 2023-05-24 | 2023-08-22 | 南京航空航天大学 | 一种双凸极电机电流传感器零偏故障诊断和容错控制方法 |
CN116633088B (zh) * | 2023-05-24 | 2024-03-08 | 南京航空航天大学 | 一种双凸极电机电流传感器零偏故障诊断和容错控制方法 |
CN117184219A (zh) * | 2023-08-31 | 2023-12-08 | 北京理工大学 | 一种用于线控转向系统的执行机构容错控制方法和装置 |
CN117184219B (zh) * | 2023-08-31 | 2024-03-26 | 北京理工大学 | 一种用于线控转向系统的执行机构容错控制方法和装置 |
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