WO2021038665A1 - Dispositif d'entraînement de moteur, ventilateur électrique, aspirateur électrique et sèche-mains - Google Patents

Dispositif d'entraînement de moteur, ventilateur électrique, aspirateur électrique et sèche-mains Download PDF

Info

Publication number
WO2021038665A1
WO2021038665A1 PCT/JP2019/033171 JP2019033171W WO2021038665A1 WO 2021038665 A1 WO2021038665 A1 WO 2021038665A1 JP 2019033171 W JP2019033171 W JP 2019033171W WO 2021038665 A1 WO2021038665 A1 WO 2021038665A1
Authority
WO
WIPO (PCT)
Prior art keywords
switching element
motor
voltage
conductive
controls
Prior art date
Application number
PCT/JP2019/033171
Other languages
English (en)
Japanese (ja)
Inventor
遥 松尾
裕次 ▲高▼山
和徳 畠山
Original Assignee
三菱電機株式会社
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by 三菱電機株式会社 filed Critical 三菱電機株式会社
Priority to JP2020521389A priority Critical patent/JP6739691B1/ja
Priority to PCT/JP2019/033171 priority patent/WO2021038665A1/fr
Publication of WO2021038665A1 publication Critical patent/WO2021038665A1/fr

Links

Images

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P25/00—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details
    • H02P25/02—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details characterised by the kind of motor
    • H02P25/04—Single phase motors, e.g. capacitor motors
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters

Definitions

  • the present invention relates to a motor drive device for driving a single-phase motor, an electric blower, an electric vacuum cleaner, and a hand dryer.
  • the single-phase PM motor has a brushless structure that does not use a brush, which is a mechanical structure, as compared with a DC motor with a brush, so that brush wear does not occur. Due to this feature, the single-phase PM motor can ensure a long life and high reliability. Further, the single-phase PM motor is a highly efficient motor because a secondary current does not flow through the rotor as compared with an induction motor.
  • the single-phase PM motor has the following advantages as compared with the three-phase PM motor having different numbers of phases.
  • (1) In the case of a three-phase PM motor, a three-phase inverter is required, whereas in a single-phase PM motor, a single-phase inverter may be used.
  • (2) When a full-bridge inverter generally used as a three-phase inverter is used, six switching elements are required, whereas in the case of a single-phase PM motor, four switching elements are required even if a full-bridge inverter is used. Can be configured with.
  • (3) Due to the features of (1) and (2), the single-phase PM motor can be miniaturized as compared with the three-phase PM motor.
  • Patent Document 1 discloses a technique relating to a drive system for a single-phase PM motor.
  • Patent Document 1 when the motor current flowing through the motor winding exceeds the threshold value, the voltage application to the motor winding is stopped. This operation of stopping the voltage application is defined as "freewheel" in Patent Document 1. During this freewheel period, one of the four switching elements connected to both ends of the motor winding is controlled to be conductive, forming a circuit through which current flows with the diode in the corresponding switching element. The wheel. During this time, the motor current circulates between the motor winding and the two switching elements.
  • Patent Document 1 a switching element is used to control the motor current. While the motor current is circulated, the value of the motor current does not increase, but all the energy of the motor current is consumed as heat by the resistance component of the winding. Therefore, in the technique of Patent Document 1, the motor current cannot be used efficiently, so that the power consumption increases. In particular, in the case of a configuration in which a storage battery such as a battery is used as a power source, there is a problem that the usable time is shortened due to a large amount of power consumption.
  • the present invention has been made in view of the above, and an object of the present invention is to obtain a motor drive device capable of efficiently using a motor current and reducing power consumption.
  • the motor drive device includes an inverter, a current detector, and a control unit.
  • the inverter has first and second legs, converts a DC voltage output from a power source into an AC voltage, and applies an AC voltage to the single-phase motor.
  • the first leg is a leg in which the first switching element of the upper arm and the second switching element of the lower arm are connected in series.
  • the second leg is a leg in which a third switching element of the upper arm and a fourth switching element of the lower arm are connected in series.
  • the second leg is connected in parallel to the first leg.
  • the current detector detects the motor current flowing through the single-phase motor.
  • the control unit controls the continuity of the first, second, third, and fourth switching elements based on the detection value of the current detector.
  • the single-phase motor is connected between the first connection point and the second connection point.
  • the first connection point is a connection point between the first switching element and the second switching element.
  • the second connection point is a connection point between the third switching element and the fourth switching element.
  • the control unit performs a first control for controlling the second and third switching elements to be conductive after controlling the first and fourth switching elements to be non-conducting.
  • the first period is a period in which the application of the AC voltage to the single-phase motor is stopped and the motor current is flowing in the first direction from the first connection point to the second connection point.
  • the motor drive device According to the motor drive device according to the present invention, there is an effect that the motor current can be efficiently used to reduce the power consumption.
  • Configuration diagram of a motor drive system including the motor drive device according to the first embodiment Circuit configuration diagram of the inverter shown in FIG.
  • a block diagram showing an example of the PWM signal generation unit shown in FIG. A time chart showing a waveform example of a main part in the PWM signal generation unit shown in FIG.
  • a block diagram showing another example of the PWM signal generation unit shown in FIG. A time chart showing a waveform example of a main part in the PWM signal generation unit shown in FIG.
  • the figure which shows the structure of the power conversion circuit which is a circuit including an inverter and a single-phase motor shown in FIG.
  • the figure which shows the switching pattern defined by the combination of the drive signal which controls continuity or non-conduction of each switching element of the power conversion circuit shown in FIG. The figure used for explaining the characteristic circuit operation in the power conversion circuit shown in FIG.
  • the figure which shows the path of the current which flows in a power conversion circuit when controlled by the pattern 1 defined in FIG. The figure which shows the path of the current which flows in a power conversion circuit when controlled by the pattern 3 defined in FIG.
  • FIG. 8 The figure which shows the equivalent circuit of the switching element of the power conversion circuit shown in FIG.
  • a time chart showing an example of a waveform of a PWM signal generated by the PWM signal generation unit shown in FIG. A flowchart showing an operation flow when a PWM signal is generated by the PWM signal generation unit shown in FIG.
  • a flowchart showing an operation flow when a PWM signal is generated by the PWM signal generation unit shown in FIG. A block diagram showing an example of a hardware configuration that realizes the function of the control unit according to the first embodiment.
  • Configuration diagram of the electric blower according to the second embodiment Configuration diagram of a vacuum cleaner provided with an electric blower according to the second embodiment
  • Configuration diagram of a hand dryer provided with an electric blower according to the second embodiment.
  • connection The motor drive device, electric blower, vacuum cleaner, and hand dryer according to the embodiment of the present invention will be described in detail with reference to the accompanying drawings below.
  • the present invention is not limited to the following embodiments. Further, in the following description, the electrical connection and the physical connection are not distinguished, and are simply referred to as "connection”.
  • FIG. 1 is a configuration diagram of a motor drive system 1 including a motor drive device 2 according to the first embodiment.
  • the motor drive system 1 shown in FIG. 1 includes a single-phase motor 12, a motor drive device 2, a battery 10, a voltage detector 20, and a switch 102.
  • the motor drive device 2 supplies AC power to the single-phase motor 12 to drive the single-phase motor 12.
  • the battery 10 is a power source that outputs a DC voltage V dc to the motor drive device 2.
  • the voltage detector 20 detects the DC voltage V dc output from the battery 10 to the motor drive device 2.
  • the single-phase motor 12 is used as a rotary electric machine for rotating an electric blower (not shown).
  • the single-phase motor 12 and the electric blower are mounted on devices such as a vacuum cleaner and a hand dryer.
  • the voltage detector 20 detects the DC voltage V dc , but the detection target of the voltage detector 20 is not limited to the DC voltage V dc output from the battery 10.
  • the detection target of the voltage detector 20 may be the inverter output voltage, which is the output voltage of the motor drive device 2.
  • Inverter output voltage is synonymous with “motor applied voltage” described later.
  • the motor drive device 2 includes an inverter 11, a control unit 25, and a drive signal generation unit 32.
  • the inverter 11 is connected to the single-phase motor 12 and applies an AC voltage to the single-phase motor 12.
  • a capacitor (not shown) (not shown) may be inserted between the battery 10 and the inverter 11 for voltage stabilization.
  • the control unit 25 controls the AC voltage output by the inverter 11.
  • the motor driving apparatus 2 is provided with a current flowing to the single-phase motor 12, i.e., a current detector 22 for detecting the motor current I m.
  • the current detector 22 if detected current corresponding to the motor current I m or the motor current I m,, where may be disposed.
  • the current detector 22 may be arranged in series with the wiring of the single-phase motor 12, or may be arranged in series with the switching element of the inverter 11. It may be arranged in the power line or the ground line of the inverter 11.
  • the current detection method in the current detector 22 a method of calculating the current value from Ohm's law by inserting a resistor having a known resistance value and detecting the voltage value, a detection method using a transformer, and a Hall effect are used. While such a detection method had the like, the motor current I m may if detected using any method.
  • a method of inserting a current sensor of a transformer in series with the wiring of the single-phase motor 12 will be described.
  • the current detector 22 detects the current in the motor drive device 2, the motor drive device 2 may be controlled as described later by using a current converted into a voltage.
  • the inverter 11 is assumed to be a single-phase inverter, it may be any one capable of driving the single-phase motor 12.
  • the control unit 25 the detection value of the DC voltage V dc detected by the voltage detector 20, the detection value of the motor current I m which is detected by the current detector 22, command value output from the switch 102, not shown A protection signal etc. is input.
  • command values include an effective current command value Ip * due to torque, a rotation speed command value ⁇ *, and the like.
  • Control unit 25 the detected value of the DC voltage V dc, the detected value of the motor current I m, based on the command values, PWM signals Q1, Q2, Q3, Q4 (hereinafter to as "Q1 ⁇ Q4" Notation) is generated.
  • the switch 102 is, for example, a physical switch, and is a changeover switch for strong operation or weak operation at hand, which is used for an electric vacuum cleaner or the like.
  • the switch 102 is not limited to the physical switch, and may be a process on software in the case of a configuration in which the command value is automatically switched according to the usage time and the state.
  • the drive signal generation unit 32 drives the drive signals S1, S2, S3, S4 (hereinafter, appropriately “S1 to S4") for driving the switching element of the inverter 11 based on the PWM signals Q1 to Q4 output from the control unit 25. (Notation) is generated.
  • the drive signal generation unit 32 converts each of the PWM signals Q1 to Q4 output from the control unit 25 into drive signals S1 to S4 for driving the inverter 11 and outputs the PWM signals to the inverter 11.
  • FIG. 1 is merely an example of the drive signal generation unit 32, and the structure may be built in the inverter 11 or may be integrated with the control unit 25.
  • An example of the single-phase motor 12 is a brushless motor.
  • the single-phase motor 12 is a brushless motor
  • a plurality of permanent magnets are arranged in the circumferential direction on the rotor 12a of the single-phase motor 12. That is, the single-phase motor 12 has a permanent magnet. These plurality of permanent magnets are arranged so that the magnetizing directions are alternately reversed in the circumferential direction, and form a plurality of magnetic poles of the rotor 12a.
  • a winding (not shown) is wound around the stator 12b of the single-phase motor 12. An alternating current flows through the winding.
  • the current flowing through the winding of the single-phase motor 12 is appropriately referred to as "motor current".
  • the number of magnetic poles of the rotor 12a is assumed to be four poles, but the number of magnetic poles of the rotor 12a may be other than four poles.
  • FIG. 2 is a circuit configuration diagram of the inverter 11 shown in FIG.
  • the inverter 11 has a plurality of bridge-connected switching elements 51, 52, 53, 54 (hereinafter, appropriately referred to as “51 to 54”).
  • the switching elements 51 and 52 form the first leg 5A.
  • the switching elements 53 and 54 form the second leg 5B.
  • the switching element 53 and the switching element 54 are connected in series.
  • the first leg 5A and the second leg 5B are connected in parallel with each other.
  • the switching elements 51 and 53 are located on the high potential side, and the switching elements 52 and 54 are located on the low potential side.
  • the high potential side is generally referred to as an "upper arm” and the low potential side is generally referred to as a "lower arm”.
  • the switching element 51 of the first leg 5A is referred to as the “upper arm first element” or the “first switching element”
  • the switching element 53 of the second leg 5B is referred to as the "upper arm second element”.
  • switching element 52 of the first leg 5A is called a “lower arm first element” or “second switching element”
  • switching element 54 of the second leg 5B is called a “lower arm second element” or “second element”. It may be called “switching element of 4”.
  • connection point 6A which is the first connection point in the inverter 11
  • connection point 6B which is the second connection point in the inverter 11.
  • the connection point 6A is a connection point between the switching element 51 and the switching element 52.
  • the connection point 6B is a connection point between the switching element 53 and the switching element 54.
  • the connection points 6A and 6B form an AC end in the bridge circuit.
  • the current detector 22 may be inserted anywhere as long as the current flowing through the single-phase motor 12 can be detected, and the method for detecting the current in the current detector 22 is not limited.
  • a MOSFET Metal-Oxide-Semiconductor Field-Effective Transistor
  • MOSFET is an example of FET (Field-Effective Transistor).
  • a MOSFET is a semiconductor element having a function of passing a current in both directions, that is, a function of passing a current from a drain to a source or from a source to a drain. This function is sometimes referred to as the "reverse conduction function". That is, the MOSFET is a semiconductor element in which the transistor element itself has a reverse conduction function.
  • the semiconductor element having a reverse conduction function there is a reverse conduction insulated gate bipolar transistor (Reverse-Conducing Integrated Gate Bipolar Transistor: RC-IGBT).
  • the switching element 51 is formed with a body diode 51a connected in parallel between the drain and the source of the switching element 51.
  • the switching element 52 is formed with a body diode 52a connected in parallel between the drain and the source of the switching element 52.
  • the switching element 53 is formed with a body diode 53a connected in parallel between the drain and the source of the switching element 53.
  • a body diode 54a connected in parallel between the drain and the source of the switching element 54 is formed in the switching element 54.
  • Each of the plurality of body diodes 51a, 52a, 53a, 54a is a parasitic diode formed inside the MOSFET and is used as a freewheeling diode. A freewheeling diode may be connected separately. Further, although the MOSFET is illustrated in the first embodiment, the RC-IGBT described above may be used.
  • the plurality of switching elements 51 to 54 are not limited to MOSFETs formed of silicon-based materials, and may be MOSFETs formed of wide bandgap semiconductors such as silicon carbide, gallium nitride, gallium oxide, or diamond.
  • wide bandgap semiconductors have higher withstand voltage and heat resistance than silicon semiconductors. Therefore, by using the wide bandgap semiconductors for the plurality of switching elements 51 to 54, the withstand voltage resistance and the allowable current density of the switching elements are increased, and the semiconductor module incorporating the switching elements can be miniaturized. In addition, since wide bandgap semiconductors have high heat resistance, it is possible to reduce the size of the heat dissipation part for dissipating heat generated by the semiconductor module, and simplify the heat dissipation structure that dissipates heat generated by the semiconductor module. It is possible.
  • FIG. 3 is a block diagram showing a functional part that generates a PWM signal among the functional parts of the control unit 25 shown in FIG.
  • the PWM signal generation unit 38 is input with the phase ⁇ v used when generating the voltage command V m described later. Further, the PWM signal generation unit 38 is input with the phase ⁇ v , the carriers generated by the carrier generation unit 33, the DC voltage V dc, and the voltage amplitude command V * which is the amplitude value of the voltage command V m. ..
  • the PWM signal generation unit 38 generates PWM signals Q1 to Q4 based on the carrier, the phase ⁇ v , the DC voltage V dc, and the voltage amplitude command V *.
  • FIG. 4 is a block diagram showing an example of the PWM signal generation unit 38 shown in FIG. FIG. 4 shows a detailed configuration of the PWM signal generation unit 38A and the carrier generation unit 33.
  • a carrier frequency f C [Hz] which is a carrier frequency
  • f C a carrier frequency
  • a triangular wave carrier that moves up and down between “0” and “1” is shown.
  • the PWM control of the inverter 11 includes synchronous PWM control and asynchronous PWM control. In the case of synchronous PWM control, it is necessary to synchronize the carriers with the phase ⁇ v. On the other hand, in the case of asynchronous PWM control, it is not necessary to synchronize the carriers with the phase ⁇ v.
  • the PWM signal generation unit 38A includes an absolute value calculation unit 38a, a division unit 38b, a multiplication unit 38c, a multiplication unit 38d, a multiplication unit 38f, an addition unit 38e, a comparison unit 38g, a comparison unit 38h, and an output. It has an inversion unit 38i, an output inversion unit 38j, and an output selection unit 38p.
  • the absolute value calculation unit 38a calculates the absolute value
  • the division unit 38b divides the absolute value
  • the battery voltage which is the output voltage of the battery 10, fluctuates as the current continues to flow.
  • the value of the modulation factor can be adjusted so that the motor applied voltage does not decrease due to the decrease in the battery voltage.
  • the multiplication unit 38c calculates the sine value of the phase ⁇ v.
  • the multiplication unit 38c multiplies the sine value of the phase ⁇ v by the modulation factor which is the output of the division unit 38b.
  • Multiplier unit 38d multiplies the "1/2" to the voltage command V m is the output of the multiplication unit 38c.
  • the addition unit 38e adds "1/2" to the output of the multiplication unit 38d.
  • the multiplication unit 38f multiplies the output of the addition unit 38e by "-1".
  • the output of the addition unit 38e is input to the comparison unit 38g as a positive voltage command V m1 for driving the two switching elements 51 and 53 of the upper arm among the plurality of switching elements 51 to 54.
  • the output of the multiplier unit 38f is input to the comparison unit 38h as a negative side voltage instruction V m2 for driving the two switching elements 52, 54 of the lower arm.
  • the comparison unit 38 g compares the positive voltage command V m1 with the amplitude of the carrier.
  • the output of the output inversion unit 38i which is the inverted output of the comparison unit 38g, becomes the PWM signal Q1'to the output selection unit 38p, and the output of the comparison unit 38g becomes the PWM signal Q2'to the output selection unit 38p.
  • the comparison unit 38h compares the negative voltage command V m2 with the amplitude of the carrier.
  • the output of the output inversion unit 38j which is the inverted output of the comparison unit 38h, becomes the PWM signal Q3'to the output selection unit 38p, and the output of the comparison unit 38h becomes the PWM signal Q4'to the output selection unit 38p.
  • the PWM signals Q1', Q2', Q3', and Q4' are input to the output selection unit 38p. Further, as shown in FIG. 4, the phase ⁇ v is input to the output selection unit 38p.
  • Output selection unit 38p includes a phase theta v, the PWM signal Q1 ' ⁇ Q4', and the direction of the motor current I m flowing through the single-phase motor 12, based on, generates a PWM signal Q1 ⁇ Q4. Details of the processing by the output selection unit 38p will be described later.
  • the PWM signals Q1'to Q4' are output as they are as PWM signals Q1 to Q4, respectively.
  • FIG. 5 is a time chart showing a waveform example of a main part of the PWM signal generation unit 38A shown in FIG.
  • the waveform of the positive voltage command V m1 output from the addition unit 38e, the waveform of the negative voltage command V m2 output from the multiplication unit 38f, and the waveforms of the PWM signals Q1'to Q4' are shown. It is shown. Further, in the lowermost part of FIG. 5, the waveform of the inverter output voltage when the switching elements 51 to 54 are controlled by the PWM signals Q1'to Q4' is shown.
  • PWM signal Q1 ' is “high (High)” when “low (Low)” next when the positive voltage command V m1 is greater than the carrier, the positive voltage command V m1 is smaller than the carrier.
  • the PWM signal Q2' is an inverted signal of the PWM signal Q1'.
  • PWM signal Q3 ' is “high (High)” when “low (Low)” becomes when negative voltage instruction V m2 is larger than the carrier, the negative-side voltage instruction V m2 smaller than the carrier.
  • the PWM signal Q4' is an inverted signal of the PWM signal Q3'.
  • the circuit shown in FIG. 4 is configured with “Low Active", but even if each signal is configured with "High Active” having opposite values. Good.
  • the waveform of the inverter output voltage includes a voltage pulse due to the difference voltage between the PWM signal Q1'and the PWM signal Q4'and a voltage pulse due to the difference voltage between the PWM signal Q3'and the PWM signal Q2'. Appears. These voltage pulses are applied to the single-phase motor 12 as the motor applied voltage.
  • Bipolar modulation and unipolar modulation are known as modulation methods used when generating PWM signals Q1'to Q4'.
  • Bipolar modulation is a modulation method that outputs a voltage pulse that changes with a positive or negative potential every cycle of the voltage command V m.
  • Unipolar modulation is a voltage pulse, i.e. a positive potential and the negative modulation mode for outputting a voltage pulse that changes the potential of the zero that changes at three potentials per cycle of the voltage command V m.
  • the waveform shown in FIG. 5 is due to unipolar modulation.
  • any modulation method may be used. In applications where it is necessary to control the motor current waveform to a more sinusoidal wave, it is preferable to employ unipolar modulation having a lower harmonic content than bipolar modulation.
  • the waveforms shown in FIG. 5 show the switching elements 51 and 52 constituting the first leg 5A and the switching elements 53 constituting the second leg 5B in the section of the half-cycle T / 2 of the voltage command V m. , 54 is obtained by a method of switching operation of four switching elements.
  • This method is called “both-sided PWM” because the switching operation is performed by both the positive side voltage command V m1 and the negative side voltage command V m2.
  • the switching operation of the switching elements 51 and 52 is suspended, and in the other half cycle of the one cycle T of the voltage command V m, the switching operation is suspended.
  • This method is called “one-sided PWM”.
  • “one-sided PWM” will be described.
  • FIG. 6 is a block diagram showing another example of the PWM signal generation unit 38 shown in FIG.
  • FIG. 6 shows an example of a PWM signal generation circuit by the above-mentioned “one-sided PWM”, and specifically, a detailed configuration of the PWM signal generation unit 38B and the carrier generation unit 33 is shown.
  • the configuration of the carrier generation unit 33 shown in FIG. 6 is the same as or equivalent to that shown in FIG.
  • the same or equivalent components as the PWM signal generation unit 38A shown in FIG. 4 are designated by the same reference numerals.
  • the PWM signal generation unit 38B includes an absolute value calculation unit 38a, a division unit 38b, a multiplication unit 38c, a multiplication unit 38k, an addition unit 38m, an addition unit 38n, a comparison unit 38g, a comparison unit 38h, and an output. It has an inversion unit 38i, an output inversion unit 38j, and an output selection unit 38q.
  • the absolute value calculation unit 38a calculates the absolute value
  • the division unit 38b divides the absolute value
  • the multiplication unit 38c calculates the sine value of the phase ⁇ v.
  • the multiplication unit 38c multiplies the sine value of the phase ⁇ v by the modulation factor which is the output of the division unit 38b.
  • Multiplying unit 38k multiplies "-1" to the voltage command V m is the output of the multiplication unit 38c.
  • Adding section 38m adds "1" to the voltage command V m is the output of the multiplication unit 38c.
  • Addition unit 38n adds "1" output of the multiplying unit 38k, that is, the inverted output of the voltage command V m.
  • the output of the adder 38n is input to the comparison unit 38h as a second voltage command V m4 for driving the two switching elements 52, 54 of the lower arm.
  • the comparison unit 38g compares the first voltage command V m3 with the amplitude of the carrier.
  • the output of the output inversion unit 38i which is the inverted output of the comparison unit 38g, becomes the PWM signal Q1'to the output selection unit 38q, and the output of the comparison unit 38g becomes the PWM signal Q2'to the output selection unit 38q.
  • the comparison unit 38h compares the second voltage command Vm4 with the amplitude of the carrier.
  • the output of the output inversion unit 38j which is the inverted output of the comparison unit 38h, becomes the PWM signal Q3'to the output selection unit 38q, and the output of the comparison unit 38h becomes the PWM signal Q4'to the output selection unit 38q.
  • the PWM signals Q1'to Q4' are input to the output selection unit 38q. Further, as shown in FIG. 6, the phase ⁇ v is input to the output selection unit 38q.
  • Output selection unit 38q includes a phase theta v, the PWM signal Q1 ' ⁇ Q4', and the direction of the motor current I m flowing through the single-phase motor 12, based on, generates a PWM signal Q1 ⁇ Q4. Details of the processing by the output selection unit 38q will be described later.
  • the PWM signals Q1'to Q4' are output as they are as PWM signals Q1 to Q4, respectively.
  • FIG. 7 is a time chart showing a waveform example of a main part of the PWM signal generation unit 38B shown in FIG.
  • the waveform of the first voltage command V m3 output from the adder 38 m, the waveform of the second voltage command V m4 output from the adder 38n, and the waveforms of the PWM signals Q1'to Q4' are shown. It is shown. Further, in the lowermost part of FIG. 7, the waveform of the inverter output voltage when the switching elements 51 to 54 are controlled by the PWM signals Q1'to Q4' is shown.
  • FIG. 7 the waveform of the inverter output voltage when the switching elements 51 to 54 are controlled by the PWM signals Q1'to Q4' is shown.
  • the waveform portion of the first voltage command V m3 whose amplitude value is larger than the peak value of the carrier and the second voltage command V m4 whose amplitude value is larger than the peak value of the carrier is represented by a flat straight line.
  • PWM signal Q1 ' is “low (Low)” next when the first voltage command V m3 is greater than the carrier, the first voltage command V m3 is "high (High)” when less than the carrier.
  • the PWM signal Q2' is an inverted signal of the PWM signal Q1'.
  • PWM signal Q3 ' is “low (Low)” next when a second voltage command V m4 is greater than the carrier, the second voltage command V m4 is "high (High)” when less than the carrier.
  • the PWM signal Q4' is an inverted signal of the PWM signal Q3'.
  • the circuit shown in FIG. 6 is configured with “Low Active", but even if each signal is configured with "High Active” having opposite values. Good.
  • the waveform of the inverter output voltage includes a voltage pulse due to the difference voltage between the PWM signal Q1'and the PWM signal Q4'and a voltage pulse due to the difference voltage between the PWM signal Q3'and the PWM signal Q2'. Appears. These voltage pulses are applied to the single-phase motor 12 as the motor applied voltage.
  • the waveform of the inverter output voltage is unipolar modulation that changes at three potentials for each cycle T of the voltage command V m.
  • bipolar modulation may be used instead of unipolar modulation, but unipolar modulation is preferably adopted in applications where it is necessary to control the motor current waveform to a more sinusoidal wave.
  • the carrier to be used for generation of these PWM signals are generated a triangular wave peaks and troughs from the desired carrier frequency f C.
  • the carrier frequency f C is variable according to the rotation speed of the motor, and the higher the rotation speed of the motor, the higher the frequency. It is desirable to generate carriers at a frequency that is at least twice the rotation speed. Further, the carrier to be generated may be a sawtooth wave or the like instead of a triangular wave.
  • FIG. 8 is a diagram showing a configuration of a power conversion circuit 50, which is a circuit including the inverter 11 and the single-phase motor 12 shown in FIG.
  • FIG. 9 is a diagram showing a switching pattern defined by a combination of drive signals that control conduction or non-conduction of each switching element of the power conversion circuit 50 shown in FIG.
  • FIG. 10 is a diagram used for explaining a characteristic circuit operation in the power conversion circuit 50 shown in FIG.
  • FIG. 11 is a diagram showing a path of a current flowing through the power conversion circuit 50 when controlled by the pattern 1 defined in FIG. FIG.
  • FIG. 12 is a diagram showing a path of a current flowing through the power conversion circuit 50 when controlled by the pattern 3 defined in FIG.
  • FIG. 13 is a diagram showing a path of a current flowing through the power conversion circuit 50 when controlled by the pattern 5 defined in FIG.
  • FIG. 14 is a diagram showing a path of a current flowing through the power conversion circuit 50 when controlled by the pattern 7 defined in FIG.
  • FIG. 15 is a diagram showing a path of a current flowing through the power conversion circuit 50 when controlled by the pattern 8 defined in FIG.
  • FIG. 16 is a diagram showing an equivalent circuit of the switching element of the power conversion circuit 50 shown in FIG.
  • FIG. 17 is a diagram showing an equivalent circuit of the power conversion circuit 50 shown in FIG. 8 when the switching element is controlled to be conductive.
  • FIG. 18 is a diagram showing an equivalent circuit of the power conversion circuit 50 shown in FIG. 8 when the switching element is controlled to be non-conducting.
  • the direction of this current is defined as the "first direction”.
  • the opposite of the first direction is defined as the "second direction”. That is, the first direction is a direction in which the motor current I m is directed to a connection point 6B from the connection point 6A.
  • the second direction is the direction in which the motor current I m is directed to a connection point 6A from the connection point 6B.
  • the single-phase motor 12 connected between the connection point 6A and the connection point 6B is equivalently used by the motor winding 41 and the voltage source 42.
  • L m is an inductance component of the motor winding 41.
  • R m is a resistance component of the motor winding 41.
  • e m is the induced voltage generated in the motor windings 41.
  • it represents the single-phase motor 12 as a power source with a voltage source 42 of the induced voltage e m.
  • a circuit including the inverter 11 and the single-phase motor 12 is defined as a power conversion circuit 50.
  • FIG. 8 shows a power supply capacitor 40 connected in parallel to each of the first leg 5A and the second leg 5B.
  • the power supply capacitor 40 is a power storage device capable of storing electric power.
  • the power supply capacitor 40 holds the DC power supplied from the battery 10. Further, the power supply capacitor 40 can recover the electric power supplied from the single-phase motor 12 and hold it as DC electric power when the single-phase motor 12 operates as a generator.
  • patterns 1 to 9 are shown.
  • patterns 10 to 18 are shown.
  • patterns 19 to 25 are shown.
  • patterns 26 to 32 are shown.
  • Each of pattern 1 to pattern 9 and pattern 19 to pattern 25 is a pattern when the motor current Im is flowing in the first direction. Further, each of pattern 10 to pattern 18 and pattern 26 to pattern 32 is a pattern when the motor current Im is flowing in the second direction.
  • pattern 1 and pattern 10 are patterns defined as power running.
  • Power running is a state in which a voltage for passing a current required to rotate the single-phase motor 12 is applied to the single-phase motor 12.
  • the motor current Im is expressed by the following equation (1) using the Laplace operator s.
  • v mi is the motor applied voltage applied by the inverter 11 to the single-phase motor 12.
  • the motor winding 41 of the single-phase motor 12 has an inductance component L m and a resistance component R m . Therefore, when the inverter 11 continuously applied voltage, as shown in equation (1) increases the voltage applied to the motor v mi, by the difference between the induced voltage e m, the motor current I m is the primary delay Continue to do. If this state continues, the resistance component R m of the motor windings 41 is small, the current value of the motor current I m becomes excessive, sometimes heating of the single-phase motor 12 becomes a problem. When the single-phase motor 12 is a PM motor, it may cause a problem such as demagnetization of the rotor magnet.
  • the PWM control described above is a method of providing a section in which a voltage is applied and a section in which a voltage is not applied to the single-phase motor 12. That is, the use of the PWM control, the motor current I m is can be adjusted so as not to excessively.
  • patterns 1 and 10 are patterns of sections in which voltage is applied, and are sections of power running. Further, the patterns other than the patterns 1 and 10 are patterns in the section where no voltage is applied, and are patterns in the section other than the power running.
  • patterns 19 to 32 are basically not used. This is because these patterns are patterns in which both switching elements of the same leg connected in series are conductive in the inverter 11. Specifically, it is a pattern in which both the switching element 51 and the switching element 52 are conductive, and a pattern in which both the switching element 53 and the switching element 54 are conductive.
  • the circuit configuration is such that the power supply capacitor 40 connected to the inverter 11 and the ground are short-circuited through the switching elements of the upper and lower arms in a conductive state. This phenomenon is called "upper and lower arm short circuit". When the upper and lower arm short circuit occurs, regardless of the direction of flow of the motor current I m, a large current flows to the inverter 11, in the worst case, lead to damage of the switching element.
  • controlling not only switching elements of the same leg but also a plurality of switching elements to be conductive and non-conducting at the same time is a control mode to be avoided. This is clear when considering the variation in the timing at which the switching elements conduct, the delay of the signal transmitted from the processor controlling the continuity to each switching element, and the like.
  • FIG. 10 shows the waveform of the drive signal when shifting from the state of pattern 1 to the state of pattern 4.
  • FIG. 10 shows the waveform of the drive signal when shifting from the state of pattern 1 to the state of pattern 4.
  • FIG. 10 shows an enlarged waveform of a section surrounded by a broken line.
  • the state of pattern 1 is transferred to the state of pattern 4 after passing through the state of pattern 2. Further, unlike FIG. 10, when the timing at which the switching element 54 becomes conductive is delayed from the timing at which the switching element 53 becomes conductive, the state of pattern 1 is changed to the state of pattern 4 via the state of pattern 23. After that, it will be migrated.
  • the pattern 23 is a pattern in which both switching elements of the same leg connected in series are conductive. Therefore, it is not preferable to go through the pattern 23.
  • the transition from the powering state to the next state is narrowed down to two patterns.
  • the transition destination from pattern 1, which is one of the power running patterns is any of patterns 2 and 3.
  • the transition destination from the pattern 10, which is another power running pattern is any of the patterns 11 and 12.
  • each switching element of the inverter 11 is a gate voltage applying element such as a MOSFET
  • a bootstrap circuit for the gate power supply for the switching elements 51 and 53 located on the high potential side. is there.
  • the gate voltage is raised by charging the boot capacitor with an electric charge, but it is necessary to charge the boot capacitor with an electric charge periodically. Therefore, it is difficult to keep the switching elements 51 and 53 on all the time.
  • the time that the switching elements 51 and 53 can be kept on is determined by the capacity of the boot capacitor. Considering the cost, we want to avoid the boot capacitor becoming large. Therefore, basically, it is preferable to avoid a state in which the switching elements 51 and 53 are continuously turned on. From the above, pattern 3 is more practical as the migration destination of pattern 1. Further, the pattern 12 is more practical as the migration destination of the pattern 10. Needless to say, patterns 2 and 11 may be used because it is not a technical problem.
  • the pattern 3 is shifted to the pattern 5.
  • the transition from the pattern 3 to the pattern 5 may be carried out by conducting the switching element 52.
  • the motor current I m the body interior of the switching element 52, i.e., to flow through the channel of the switching element 52.
  • the current flowing through the current loop via the body diode 52a of the switching element 52 becomes smaller.
  • a voltage is applied to the motor winding 41 in the pattern 1 to shift to the pattern 5 via the pattern 3.
  • This makes it possible to stop applying the voltage to the motor winding 41 and control the current flowing through the motor winding 41.
  • the motor current I m flowing while stopping voltage application is consumed as heat in all the resistance component. Therefore, in the first embodiment, rather than consuming the motor current I m, performs control of storing electric power by the motor current I m to the power capacitor 40 as a capacitor.
  • the power source is a storage battery such as a battery
  • the battery can be used for a longer time than in the past.
  • the state of the pattern 5 shown in FIG. 13 is further shifted to the state of the pattern 7 shown in FIG.
  • the switching element 54 is controlled to be non-conducting from the state shown in FIG.
  • the current loop via the switching element 52, the motor winding 41, and the switching element 54 disappears.
  • a body diode 53a is connected in parallel to the switching element 53.
  • a new current loop is formed via the body diode 53a of the switching element 53.
  • the state is shifted to the pattern 8.
  • the switching element 53 is controlled to be conductive from the state shown in FIG.
  • the motor current I m the body interior of the switching element 53, i.e., to flow through the channel of the switching element 53.
  • FIGS. 16 to 18 a switching element in which a body diode is connected in antiparallel has an on-resistance R on , which is a resistance component at the time of conduction, and a forward voltage V f , which is a forward voltage drop component. It can be replaced with an equivalent circuit connected in parallel.
  • FIG. 17 shows an equivalent circuit when the power conversion circuit 50 is controlled by the pattern 8.
  • FIG. 18 shows an equivalent circuit when the power conversion circuit 50 is controlled by the pattern 7.
  • R on 2 is the on-resistance of the switching element 52
  • R on 3 is the on-resistance of the switching element 53.
  • R m, L m, I m, the e m are as described above.
  • the induced voltage generated by rotation of the single-phase motor 12 expressed as a voltage source as e m, represents the motor current I m flowing through the motor windings 41 by a current source.
  • the voltage drop caused by the on-resistance R on is very small compared to the forward voltage V f of the body diode.
  • the relationship when the power consumption is compared between when the switching element is conducting and when it is not conducting is expressed by the following equation (2).
  • the power loss of the pattern 8 is smaller than that of the pattern 7. Therefore, in the first embodiment, the control of shifting from the pattern 5 to the pattern 8 via the pattern 7 is performed.
  • FIG. 19 is a time chart showing an example of waveforms of PWM signals Q1 to Q4 generated by the PWM signal generation unit 38B shown in FIG.
  • FIG. 20 is a flowchart showing an operation flow when a PWM signal is generated by the PWM signal generation unit 38B shown in FIG.
  • the waveform of the first voltage command V m3 output from the addition unit 38 m of the PWM signal generation unit 38B and the second voltage command V m4 output from the addition unit 38n of the PWM signal generation unit 38B are shown.
  • the waveforms of the PWM signals Q1 to Q4 generated by the output selection unit 38q of the PWM signal generation unit 38B are shown.
  • the enlarged waveform of the portion surrounded by the broken line square frame K1 in the upper part of FIG. 19 is shown.
  • each of the two broken vertical lines penetrating the frame K1 corresponds to each of the two broken vertical lines shown in the lower part.
  • the output selection unit 38q switches the processing between the A section and the B section.
  • the section A is a flat straight line in which the first voltage command V m3 does not intersect the carrier, and is a section in which the second voltage command V m 4 changes so as to intersect the carrier.
  • the section B is a section in which the first voltage command V m3 changes so as to intersect the carrier, and the second voltage command V m4 is a flat straight line that does not intersect the carrier.
  • Whether it is the A section or the B section is determined by using the phase ⁇ v input to the output selection unit 38q. Specifically, when the phase ⁇ v is 0 ° ⁇ ⁇ v ⁇ 180 °, it is determined as “A section”. When the phase ⁇ v is 180 ° ⁇ ⁇ v ⁇ 360 °, it is determined as “B interval”.
  • the output selection unit 38q switches the processing according to the phase ⁇ v.
  • the main body of the operation in the flowchart of FIG. 20 is the PWM signal generation unit 38B.
  • the motor current Im is flowing in the second direction.
  • the state immediately after the start is a state in which the inverter 11 is controlled by the pattern 10 which is a power running pattern.
  • step S100 it is determined whether or not the phase ⁇ v is 0 ° ⁇ ⁇ v ⁇ 180 °. If the phase ⁇ v is 0 ° ⁇ ⁇ v ⁇ 180 °, the process proceeds to step S101. If the phase ⁇ v is 180 ° ⁇ ⁇ v ⁇ 360 °, the process proceeds to a flow chart of opposite phases (not shown). The flow chart of the opposite phase is the same process as the flowchart shown in FIG. 20, and the description in this paper is omitted.
  • step S101 it is determined whether or not the phase ⁇ v is 0 ° ⁇ v ⁇ 1 or ⁇ 2 ⁇ v ⁇ 180 °. ⁇ 1 and ⁇ 2 are set values that satisfy ⁇ 1 ⁇ 2. If the phase ⁇ v is 0 ° ⁇ v ⁇ 1 or ⁇ 2 ⁇ v ⁇ 180 °, the process proceeds to step S102.
  • step S102 the PWM signals Q1'to Q4' input to the output selection unit 38q are directly output as PWM signals Q1 to Q4.
  • the processing of steps S101 and S102 means that the processing of steps S104 to S118 described later is not performed at the switching portion between the A section and the B section. When the process of step S102 is completed, the process returns to step S100.
  • step S103 the carrier and the second voltage command V m4 are compared. If the carrier does not fall below the second voltage command V m4 , the process proceeds to step S102. If the carrier is below the second voltage command V m4 , the process proceeds to step S104. In step S104, the process of shifting to the pattern 11 is performed. The process proceeds to step S105, and in step S105, the passage of time Ts11 is determined. By steps S104 and S105, the state of the pattern 11 is continued for the time Ts11. When the process of step S105 is completed, the process proceeds to step S106. In the waveform in the lower part of FIG. 19, “T sx ” described between the pattern 10 and the pattern 11 is a delay time required for switching the conduction of the switching element.
  • step S106 the process of shifting to the pattern 13 is performed.
  • the process proceeds to step S107, and in step S107, the passage of time Ts13 is determined.
  • steps S106 and S107 the state of the pattern 13 is continued for the time Ts13.
  • the process proceeds to step S108.
  • step S108 the process of shifting to the pattern 15 is performed.
  • the process proceeds to step S109, and in step S109, the passage of time Ts15 is determined.
  • steps S108 and S109 the state of the pattern 15 is continued for the time Ts15.
  • the process proceeds to step S110.
  • step S110 the process of shifting to the pattern 17 is performed.
  • the process proceeds to step S111, and in step S111, the passage of time Ts17 is determined.
  • steps S110 and S111 the state of the pattern 17 is continued for the time Ts17.
  • the process proceeds to step S112.
  • step S112 a process of shifting to the pattern 15 is performed.
  • the process proceeds to step S113, and in step S113, the passage of time Ts15'is determined.
  • steps S112 and S113 the state of the pattern 15 is continued for the time Ts15'.
  • the process proceeds to step S114.
  • step S114 a process of shifting to the pattern 13 is performed.
  • the process proceeds to step S115, and in step S115, the carrier and the second voltage command V m4 are compared. If the carrier does not exceed the second voltage command V m4 , the process returns to step S114, and the state of pattern 13 is continued. If the carrier exceeds the second voltage command V m4 , the process proceeds to step S116.
  • step S116 the process of shifting to the pattern 11 is performed.
  • the process proceeds to step S117, and in step S117, the passage of time Ts11'is determined.
  • steps S116 and S117 the state of the pattern 11 is continued for the time Ts11'.
  • the process proceeds to step S118.
  • step S118 the process of shifting to the pattern 10 is performed.
  • the process returns to step S100. After that, the process from step S100 is repeated.
  • the time Ts11 and time Ts11', the time Ts13 and time Ts13', and the time Ts15 and time Ts15' may be the same time or different times. Further, it is necessary to make the sum of these times and the delay time T sx required for switching the switching element shorter than the half cycle of the carrier. Furthermore, the time consume the motor current I m as a heat TS13, TS15, it is desirable to reduce as much as possible. Further, since the pattern 15 has a larger loss due to the body diode of the switching element than the pattern 17, it is desirable that the time Ts15 is shorter than the time Ts17.
  • the delay time T sx is the time required for the switching element to turn on or off, and is a time that cannot be omitted although it varies depending on the switching element. Therefore, it is necessary to secure at least the delay time T sx for each pattern.
  • the process proceeds from the pattern 15 and 17 to short the motor windings 41 to the pattern 11 or pattern 13, thereafter the pattern 15 or pattern 17 You may put it back.
  • the motor current I m which the energy of the induced voltage generated during the rotation of the single-phase motor 12 through the motor windings 41.
  • This is an operation of generating a boosted voltage in the motor winding 41 by temporarily recirculating the current flowing through the motor winding 41.
  • This operation can be performed based on the detected value of the current detector 22. Specifically, when the detected value of the motor current I m is below the specified current, it may be migrated to the pattern for short-circuiting the motor windings 41.
  • the voltage of the power supply capacitor 40 is excessively increased by the motor current I m flows to the power supply capacitor 40 side, there is a risk that the equipment may be damaged beyond the breakdown voltage of the device connected to the power supply capacitor 40. Therefore, it is preferable to monitor the power supply capacitor 40 with a voltage detector 20 or the like.
  • the detection value of the voltage detector 20 rises to the specified voltage, the switching element is controlled so as to shift from the state of the pattern 15 or the pattern 17 to the state of another pattern. For example, if to reflux motor current I m in the interior of the power conversion circuit 50, the excess energy can be consumed by the body diode or the internal resistance, it is possible to avoid damage to the equipment in advance ..
  • FIG. 20 shows a processing flow when the motor current Im is flowing in the second direction, but when the motor current Im is flowing in the first direction, each pattern is shown. The same processing flow is obtained only by changing to the corresponding pattern.
  • the motor current I m flows in the first direction, instead of the respective patterns 10,11,13,15,17, pattern 1,3,5,7,8 is used.
  • FIGS. 19 and 20 were operation examples by the PWM signal generation unit 38B shown in FIG. 6, that is, application examples to the one-sided PWM method.
  • the method of the first embodiment can also be applied to the two-sided PWM method.
  • FIGS. 21 and 22 an application example to the double-sided PWM method will be described with reference to FIGS. 21 and 22.
  • FIG. 21 is a time chart showing an example of waveforms of PWM signals Q1 to Q4 generated by the PWM signal generation unit 38A shown in FIG.
  • FIG. 22 is a flowchart showing an operation flow when a PWM signal is generated by the PWM signal generation unit 38A shown in FIG.
  • the waveform of the positive side voltage command V m1 output from the addition unit 38e of the PWM signal generation unit 38A and the negative side voltage command V m2 output from the multiplication unit 38f of the PWM signal generation unit 38A are shown.
  • the waveforms of the PWM signals Q1 to Q4 generated by the output selection unit 38p of the PWM signal generation unit 38A are shown.
  • the enlarged waveform of the portion surrounded by the broken line square frame K2 in the upper part of FIG. 21 is shown.
  • each of the two dashed vertical lines penetrating the frame K2 corresponds to each of the two dashed vertical lines shown in the lower part. As shown in FIGS.
  • the output selection unit 38p switches the processing between the A section and the B section.
  • the section A is a section in which the amplitude of the positive voltage command V m1 is a positive value.
  • the B section is a section in which the amplitude of the negative voltage command V m2 is a positive value. Whether it is the A section or the B section is determined by using the phase ⁇ v input to the output selection unit 38p. Specifically, when the phase ⁇ v is 0 ° ⁇ ⁇ v ⁇ 180 °, it is determined as “A section”. When the phase ⁇ v is 180 ° ⁇ ⁇ v ⁇ 360 °, it is determined as “B interval”. The output selection unit 38p switches the processing according to the phase ⁇ v.
  • the main body of the operation in the flowchart of FIG. 22 is the PWM signal generation unit 38A.
  • the motor current Im is flowing in the second direction.
  • the state immediately after the start is a state in which the inverter 11 is controlled by the pattern 10 which is a power running pattern.
  • step S100 to step S134 among the processes from step S100 to step S134, the PWM signals Q1 to Q4 of the portion surrounded by the frame K3 in the upper part of FIG. 21 are generated by the processes from step S100 to step S118. .. Further, by the processes from step S119 to step S134, PWM signals Q1 to Q4 of the portion surrounded by the frame K2 in the upper part of FIG. 21 are generated.
  • the processing from step S100 to step S118 is the destination when the second voltage command V m4 is replaced with the negative voltage command V m2 and the determination in step S103 is “No”.
  • step S119 is performed. Except for these differences, the process is the same as that in FIG. 20, and the description here is omitted.
  • step S118 the process of shifting to the pattern 10 is performed.
  • the process proceeds to step S119.
  • step S119 the carrier and the positive voltage command V m1 are compared. If the carrier does not exceed the positive voltage command V m1 , the process returns to step S102. If the carrier exceeds the positive voltage command V m1 , the process proceeds to step S120. In step S120, a process of shifting to the pattern 12 is performed. The process proceeds to step S121, and in step S121, the passage of time Ts12 is determined. By steps S120 and S121, the state of the pattern 12 is continued for the time Ts12. When the process of step S121 is completed, the process proceeds to step S122.
  • step S122 the process of shifting to the pattern 14 is performed.
  • the process proceeds to step S123, and in step S123, the passage of time Ts14 is determined.
  • steps S122 and S123 the state of pattern 14 is continued for time Ts14.
  • the process proceeds to step S124.
  • step S124 the process of shifting to the pattern 16 is performed.
  • the process proceeds to step S125, and in step S125, the passage of time Ts16 is determined.
  • steps S124 and S125 the state of the pattern 16 is continued for the time Ts16.
  • the process of step S125 is completed, the process proceeds to step S126.
  • step S126 the process of shifting to the pattern 17 is performed.
  • the process proceeds to step S127, and in step S127, the passage of time Ts17 is determined.
  • steps S126 and S127 the state of pattern 17 is continued for time Ts17.
  • the process proceeds to step S128.
  • step S128 the process of shifting to the pattern 16 is performed.
  • the process proceeds to step S129, and in step S129, the passage of time Ts16'is determined.
  • steps S128 and S129 the state of pattern 16 is continued for time Ts16'.
  • the process proceeds to step S130.
  • step S130 a process of shifting to the pattern 14 is performed.
  • the process proceeds to step S131, and in step S131, the carrier and the positive voltage command V m1 are compared. If the carrier does not fall below the positive voltage command V m1 , the process returns to step S130 and the state of pattern 13 is continued. If the carrier is below the second voltage command V m4 , the process proceeds to step S132.
  • step S132 the process of shifting to the pattern 12 is performed.
  • the process proceeds to step S133, and in step S133, the passage of time Ts12'is determined.
  • steps S132 and S133 the state of the pattern 12 is continued for the time Ts12'.
  • the process proceeds to step S134.
  • step S134 the process of shifting to the pattern 10 is performed.
  • the process returns to step S100. After that, the process from step S100 is repeated.
  • the state of pattern 16 and pattern 17 is further shifted to each state. There is. That is, instead of recirculating the motor current I m between the motor windings 41 and each of the switching elements, by shifting to the state of the pattern 16 and pattern 17, recovering power by the motor current I m to the power supply capacitor 40 I'm letting you. This makes it possible to reduce the power consumption of the motor drive device 2.
  • the time Ts12 and time Ts12', the time Ts14 and time Ts14', and the time Ts16 and time Ts16' may be the same time or different times. Further, it is necessary to make the sum of these times and the delay time T sx required for switching the switching element shorter than the half cycle of the carrier. Furthermore, the time consume the motor current I m as a heat TS14, TS16, it is desirable to reduce as much as possible. Further, since the pattern 16 has a larger loss due to the body diode of the switching element than the pattern 17, it is desirable that the time Ts16 is shorter than the time Ts17.
  • the same processing as the one-sided PWM method can be performed.
  • the parasitic inductance between the battery 10 as a power source and the power supply capacitor 40 connected in parallel is large, the supply of power from the battery 10 to the power supply capacitor 40 is delayed due to the parasitic inductance.
  • the output to the load is large and the output is large, a large amount of power is required, and the delay of the parasitic inductance cannot be ignored.
  • the technique of the first embodiment the power of the motor current I m can be reused without consuming as heat. This makes it possible to stably supply electric power to the load.
  • the physical wiring distance between the battery and the inverter board is increased. Occurs. In the case of such a design, a parasitic inductance is always generated, so that the effect of using the method of the first embodiment can be expected. Further, since the power of the motor current I m can be efficiently utilized, it is possible to reduce the capacity of the power supply capacitor to be mounted on the inverter board. Therefore, it can contribute to the reduction in size and weight of the inverter board.
  • the control according to the first embodiment is performed regardless of whether the single-phase motor 12 is in operation or stopped.
  • the operation during the dead time in switching the switching element is included.
  • the first embodiment is a method of intentionally using the drive pattern of the switching element having a small current loss, and the period corresponding to the dead time can be shortened. This makes it possible to reduce the loss even with high carrier control.
  • the PWM control for comparing the applied voltage of the inverter 11 with the amplitude of the carrier and the voltage command value has been described, but the present invention is not limited to this.
  • PWM control there are many methods for controlling the motor, and any method may be used.
  • the control for recovering the motor current Im to the power supply capacitor 40 is positively performed. Therefore, any type of motor control can be implemented.
  • the motor drive device includes an inverter that converts a DC voltage output from a power source into an AC voltage and applies an AC voltage to the single-phase motor.
  • the inverter has a first leg in which the first switching element of the upper arm and the second switching element of the lower arm are connected in series, and a third switching element of the upper arm and a fourth switching element of the lower arm. Has a second leg connected in series with.
  • the motor drive device performs a first control for controlling the second and third switching elements to be conductive after controlling the first and fourth switching elements to be non-conducting.
  • the first period is a period in which the application of the AC voltage to the single-phase motor is stopped and the motor current is flowing in the first direction from the first connection point to the second connection point.
  • the first connection point is a connection point between the first switching element and the second switching element.
  • the second connection point is a connection point between the third switching element and the fourth switching element.
  • the motor drive device controls the first, second, and third switching elements to be non-conducting, controls the fourth switching element to be conductive, and then controls the second switching element.
  • the first control may be performed by controlling the continuity, then controlling the fourth switching element to be non-conducting, and then controlling the third switching element to be conductive.
  • the motor drive device controls the third switching element to be non-conducting and then controls the fourth switching element to be conductive. After that, the fourth switching element may be controlled to be non-conducting, and then the third switching element may be controlled to be conductive. In this way, a boosted voltage can be generated in the motor winding 41. As a result, the energy of the motor current can be efficiently recovered.
  • the motor drive device controls the first and third switching elements to be non-conducting, and the second and fourth The switching element may be controlled to be conductive.
  • the motor driving device controls the second and third switching elements to be non-conducting in the second period, and then controls the first and fourth switching elements to be conductive.
  • the second period is a period in which the application of the AC voltage to the single-phase motor is stopped and the motor current flows in the second direction from the second connection point to the first connection point.
  • the energy of the motor current flowing through the single-phase motor can be efficiently recovered by the second control performed by the motor drive device. This makes it possible to obtain a motor drive device capable of efficiently using the energy of the motor current to reduce power consumption.
  • the motor drive device controls the first, third, and fourth switching elements to be non-conducting, controls the second switching element to be conductive, and then controls the fourth switching element.
  • the second control may be performed by controlling the continuity, then controlling the second switching element to be non-conducting, and then controlling the first switching element to be conductive.
  • the motor drive device controls the first switching element to be non-conducting and then controls the second switching element to be conductive. After that, the second switching element may be controlled to be non-conducting, and then the first switching element may be controlled to be conductive. In this way, a boosted voltage can be generated in the motor winding 41. As a result, the energy of the motor current can be efficiently recovered.
  • the motor drive device controls the first and third switching elements to be non-conducting, and the second and fourth switching elements are non-conducting.
  • the switching element may be controlled to be conductive.
  • FIG. 23 is a block diagram showing an example of a hardware configuration that realizes the function of the control unit 25 according to the first embodiment.
  • FIG. 24 is a block diagram showing another example of the hardware configuration that realizes the function of the control unit 25 in the first embodiment.
  • the processor 200 that performs the calculation, the memory 202 in which the program read by the processor 200 is stored, And the interface 204 for inputting / outputting signals can be included.
  • the processor 200 may be an arithmetic unit, a microprocessor, a microcomputer, a CPU (Central Processing Unit), or a DSP (Digital Signal Processor).
  • the memory 202 includes a non-volatile or volatile semiconductor memory such as a RAM (Random Access Memory), a ROM (Read Only Memory), a flash memory, an EPROM (Erasable Program ROM), and an EPROM (registered trademark) (Electrically EPROM). Examples thereof include magnetic disks, flexible disks, optical disks, compact disks, mini disks, and DVDs (Digital entirely Disc).
  • the memory 202 stores a program that executes the function of the control unit 25 according to the first embodiment.
  • the processor 200 sends and receives necessary information via the interface 204, the processor 200 executes a program stored in the memory 202, and the processor 200 refers to a table stored in the memory 202 to perform the above-described processing. It can be carried out.
  • the calculation result by the processor 200 can be stored in the memory 202.
  • the processing circuit 203 shown in FIG. 24 can also be used.
  • the processing circuit 203 corresponds to a single circuit, a composite circuit, an ASIC (Application Specific Integrated Circuit), an FPGA (Field-Programmable Gate Array), or a combination thereof.
  • the information input to the processing circuit 203 and the information output from the processing circuit 203 can be obtained via the interface 204.
  • control unit 25 may be performed in the processing circuit 203, and processing not performed in the processing circuit 203 may be performed in the processor 200 and the memory 202.
  • Embodiment 2 In the second embodiment, an application example of the motor drive device 2 described in the first embodiment will be described.
  • FIG. 25 is a diagram showing a configuration example of the electric blower 64 according to the second embodiment.
  • the electric blower 64 includes the motor drive device 2 described in the first embodiment, and the propeller 69 is attached to the single-phase motor 12 driven by the motor drive device 2.
  • the electric blower 64 has a structure in which the motor driving device 2 rotates the single-phase motor 12 to send out or suck the wind.
  • FIG. 26 is a diagram showing a configuration example of a vacuum cleaner 61 including the electric blower 64 according to the second embodiment.
  • the vacuum cleaner 61 includes a battery 67 corresponding to the battery 10 shown in FIG. 1, a motor driving device 2 shown in FIG. 1, and an electric blower 64 driven by a single-phase motor 12 shown in FIG. .. Further, the vacuum cleaner 61 includes a dust collecting chamber 65, a sensor 68, a suction port 63, an extension pipe 62, and an operation unit 66.
  • the user who uses the vacuum cleaner 61 has an operation unit 66 and operates the vacuum cleaner 61.
  • the motor drive device 2 of the vacuum cleaner 61 drives the electric blower 64 using the battery 67 as a power source. By driving the electric blower 64, dust is sucked from the suction port 63. The sucked dust is collected in the dust collecting chamber 65 via the extension pipe 62.
  • the vacuum cleaner 61 is a product that uses the battery 67 as a power source. Using the technique of the first embodiment described above, it is possible to reduce power consumption by using efficiently the motor current I m. As a result, the battery 67 can be used for a long time to obtain a vacuum cleaner 61 that can be used for a long time.
  • the switching elements 51 to 54 of the inverter 11 are formed of a wide bandgap semiconductor, so that the heat dissipation parts can be simplified and the size and weight can be reduced.
  • FIG. 27 is a diagram showing a configuration example of a hand dryer 90 provided with the electric blower 64 according to the second embodiment.
  • the hand dryer 90 includes a casing 91, a hand detection sensor 92, a water receiving portion 93, a drain container 94, a cover 96, a sensor 97, an intake port 98, and an electric blower 64.
  • the sensor 97 is either a gyro sensor or a motion sensor.
  • the hand dryer 90 when the hand is inserted into the hand insertion portion 99 at the upper part of the water receiving portion 93, the water is blown off by the blown air by the electric blower 64, and the blown water is collected by the water receiving portion 93. After that, it is stored in the drain container 94.
  • Hand dryer 90 is a product that is used continuously all year round regardless of the season. Therefore, by using the product to which the method of the first embodiment is applied, the effect of continuous reduction of power consumption can be obtained.
  • the motor drive device 2 is applied to an electric device equipped with a motor.
  • Electrical equipment equipped with motors includes incinerators, crushers, dryers, dust collectors, printing machines, cleaning machines, confectionery machines, tea making machines, woodworking machines, plastic extruders, cardboard machines, packaging machines, hot air generators, and OA.
  • Equipment, electric blowers, etc. The electric blower is a blower means for transporting an object, collecting dust, or for general blowing and exhausting.
  • the configuration shown in the above-described embodiment shows an example of the content of the present invention, can be combined with another known technique, and is one of the configurations without departing from the gist of the present invention. It is also possible to omit or change the part.

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Inverter Devices (AREA)

Abstract

La présente invention concerne un système d'entraînement de moteur (2) pourvu d'un onduleur (11), d'un détecteur de courant (22) et d'une unité de commande (25). L'onduleur (11) a une première et une seconde patte (5A, 5B) et convertit une tension continue délivrée par une batterie (10) en une tension alternative et l'applique à un moteur monophasé (12). L'unité de commande (25) commande la conduction d'éléments de commutation (51, 52, 53, 54) sur la base d'une valeur détectée du courant de moteur circulant dans le moteur monophasé (12), qui est relié entre un point de raccordement (6A) de la première patte (5A) et un point de raccordement (6B) de la deuxième patte (5B). Pendant une première période dans laquelle l'application de la tension alternative au moteur monophasé (12) est arrêtée et le courant du moteur circule dans une première direction à partir du point de raccordement (6A) vers le point de raccordement (6B), l'unité de commande (25) met en œuvre une première commande dans laquelle les éléments de commutation (51, 54) sont commandés pour être non conducteurs, puis les éléments de commutation (52, 53) sont commandés pour être conducteurs.
PCT/JP2019/033171 2019-08-23 2019-08-23 Dispositif d'entraînement de moteur, ventilateur électrique, aspirateur électrique et sèche-mains WO2021038665A1 (fr)

Priority Applications (2)

Application Number Priority Date Filing Date Title
JP2020521389A JP6739691B1 (ja) 2019-08-23 2019-08-23 モータ駆動装置、電動送風機、電気掃除機及びハンドドライヤ
PCT/JP2019/033171 WO2021038665A1 (fr) 2019-08-23 2019-08-23 Dispositif d'entraînement de moteur, ventilateur électrique, aspirateur électrique et sèche-mains

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
PCT/JP2019/033171 WO2021038665A1 (fr) 2019-08-23 2019-08-23 Dispositif d'entraînement de moteur, ventilateur électrique, aspirateur électrique et sèche-mains

Publications (1)

Publication Number Publication Date
WO2021038665A1 true WO2021038665A1 (fr) 2021-03-04

Family

ID=71949350

Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/JP2019/033171 WO2021038665A1 (fr) 2019-08-23 2019-08-23 Dispositif d'entraînement de moteur, ventilateur électrique, aspirateur électrique et sèche-mains

Country Status (2)

Country Link
JP (1) JP6739691B1 (fr)
WO (1) WO2021038665A1 (fr)

Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2018073869A1 (fr) * 2016-10-17 2018-04-26 三菱電機株式会社 Dispositif d'excitation de moteur, ventilateur électrique, aspirateur électrique et sèche-mains
WO2018138807A1 (fr) * 2017-01-25 2018-08-02 三菱電機株式会社 Dispositif d'entraînement de moteur, ventilateur électrique, nettoyeur électrique et sèche-mains
WO2018229874A1 (fr) * 2017-06-13 2018-12-20 三菱電機株式会社 Dispositif d'entraînement de moteur, souffleur électrique d'air, aspirateur électrique, et séchoir à mains

Family Cites Families (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2005237050A (ja) * 2004-02-17 2005-09-02 Sharp Corp 単相モータの制御方法
JP2011188638A (ja) * 2010-03-09 2011-09-22 Denso Corp 電力変換回路の制御装置
JP6889166B2 (ja) * 2016-09-08 2021-06-18 三菱電機株式会社 モータ駆動装置、電動送風機、および電気掃除機

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2018073869A1 (fr) * 2016-10-17 2018-04-26 三菱電機株式会社 Dispositif d'excitation de moteur, ventilateur électrique, aspirateur électrique et sèche-mains
WO2018138807A1 (fr) * 2017-01-25 2018-08-02 三菱電機株式会社 Dispositif d'entraînement de moteur, ventilateur électrique, nettoyeur électrique et sèche-mains
WO2018229874A1 (fr) * 2017-06-13 2018-12-20 三菱電機株式会社 Dispositif d'entraînement de moteur, souffleur électrique d'air, aspirateur électrique, et séchoir à mains

Also Published As

Publication number Publication date
JPWO2021038665A1 (fr) 2021-03-04
JP6739691B1 (ja) 2020-08-12

Similar Documents

Publication Publication Date Title
JP2016509464A (ja) ブラシレスモータ用の駆動回路
JP6644159B2 (ja) モータ駆動装置、電動送風機、電気掃除機及びハンドドライヤー
JP6889166B2 (ja) モータ駆動装置、電動送風機、および電気掃除機
WO2019180971A1 (fr) Dispositif d'excitation de moteur, ventilateur électrique, aspirateur et sèche-mains
JP6847195B2 (ja) モータ駆動装置、電動送風機、電気掃除機及びハンドドライヤー
JP5045622B2 (ja) 電力変換装置
WO2021106205A1 (fr) Dispositif d'entraînement de moteur, aspirateur électrique et sèche-mains
JP6739691B1 (ja) モータ駆動装置、電動送風機、電気掃除機及びハンドドライヤ
JP7019025B2 (ja) モータ駆動装置、電動送風機、電気掃除機及びハンドドライヤ
KR101864278B1 (ko) 전동기 구동장치 및 이를 구비하는 청소기
JP7237197B2 (ja) モータ駆動装置、電気掃除機及び手乾燥機
JP6925497B2 (ja) 電気掃除機
JP7150152B2 (ja) モータ駆動装置、電動送風機、電気掃除機及びハンドドライヤ
JP6910538B2 (ja) モータ駆動装置、電気掃除機及び手乾燥機
JP7150150B2 (ja) モータ駆動装置、電動送風機、電気掃除機及びハンドドライヤ
US11863104B2 (en) Motor drive device, electric blower, electric vacuum cleaner, and hand dryer
JP7462788B2 (ja) モータ駆動装置、電動送風機、電気掃除機及びハンドドライヤ
KR101882215B1 (ko) 전동기 구동장치 및 이를 구비하는 청소기
JP7105914B2 (ja) モータ制御装置、電動送風機及び電気掃除機
WO2019180969A1 (fr) Dispositif d'entraînement de moteur, ventilateur électrique, aspirateur, et sèche-mains
EP3952103A1 (fr) Dispositif d'entraînement de moteur, aspirateur électrique, et sèche-mains
WO2020208789A1 (fr) Dispositif d'entraînement de moteur, ventilateur électrique, aspirateur électrique et sèche-mains
WO2020194754A1 (fr) Dispositif d'entraînement de moteur, aspirateur électrique, et sèche-mains

Legal Events

Date Code Title Description
ENP Entry into the national phase

Ref document number: 2020521389

Country of ref document: JP

Kind code of ref document: A

121 Ep: the epo has been informed by wipo that ep was designated in this application

Ref document number: 19943353

Country of ref document: EP

Kind code of ref document: A1

NENP Non-entry into the national phase

Ref country code: DE

122 Ep: pct application non-entry in european phase

Ref document number: 19943353

Country of ref document: EP

Kind code of ref document: A1