WO2020183553A1 - Dispositif d'alimentation électrique en courant continu et dispositif de cycle de réfrigération - Google Patents

Dispositif d'alimentation électrique en courant continu et dispositif de cycle de réfrigération Download PDF

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Publication number
WO2020183553A1
WO2020183553A1 PCT/JP2019/009535 JP2019009535W WO2020183553A1 WO 2020183553 A1 WO2020183553 A1 WO 2020183553A1 JP 2019009535 W JP2019009535 W JP 2019009535W WO 2020183553 A1 WO2020183553 A1 WO 2020183553A1
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Prior art keywords
power supply
operation mode
current
reactor
power
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PCT/JP2019/009535
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English (en)
Japanese (ja)
Inventor
鹿嶋　美津夫
篠本　洋介
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三菱電機株式会社
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Application filed by 三菱電機株式会社 filed Critical 三菱電機株式会社
Priority to DE112019006992.6T priority Critical patent/DE112019006992T5/de
Priority to CN201980093589.5A priority patent/CN113544962A/zh
Priority to PCT/JP2019/009535 priority patent/WO2020183553A1/fr
Priority to JP2021504633A priority patent/JP7034373B2/ja
Publication of WO2020183553A1 publication Critical patent/WO2020183553A1/fr

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
    • H02M5/40—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc
    • H02M5/42—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters
    • H02M5/44—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac
    • H02M5/453—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M5/458—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M5/4585—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only having a rectifier with controlled elements
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0006—Arrangements for supplying an adequate voltage to the control circuit of converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0009—Devices or circuits for detecting current in a converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0067—Converter structures employing plural converter units, other than for parallel operation of the units on a single load
    • H02M1/007—Plural converter units in cascade
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/4233—Arrangements for improving power factor of AC input using a bridge converter comprising active switches
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1584—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel
    • H02M3/1586—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel switched with a phase shift, i.e. interleaved
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1588—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load comprising at least one synchronous rectifier element
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/539—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency
    • H02M7/5395—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency by pulse-width modulation
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • the present invention relates to a DC power supply device that converts alternating current into direct current and outputs it, a power conversion device including a direct current power supply device, and a refrigeration cycle device including a power conversion device.
  • Patent Document 1 discloses a DC power supply device in which a technique called synchronous rectification is applied to reduce loss.
  • Patent Document 1 is intended to reduce the switching loss due to the reverse recovery current generated in the high-side diode, and its application to a product having a wide range of power consumption has not been studied. That is, the technique shown in Patent Document 1 has a problem that the improvement of efficiency according to the power consumption is not sufficient.
  • the present invention has been made in view of the above, and an object of the present invention is to obtain a DC power supply device that can be applied to a product having a wide range of power consumption and can improve efficiency according to the power consumption. ..
  • the DC power supply device includes a plurality of metal oxide semiconductor field effect transistors having a parasitic diode inside, and the plurality of metal oxide semiconductor field effect transistors are bridged. It is equipped with a rectifier circuit that is connected and connected to an AC power supply via a reactor. Further, the DC power supply device includes a capacitor connected between the output terminals of the rectifier circuit, a first detector for detecting the polarity or phase of the power supply voltage which is the output voltage of the AC power supply, and a first current flowing through the rectifier circuit. A first current detector for detecting the above.
  • the control unit controls the first operation mode in which the metal oxide semiconductor field effect transistor is turned on at the timing when the current flows in the same direction as the parasitic diode, and the pulse width modulation control of the metal oxide semiconductor field effect transistor. It has a second operation mode for boosting the voltage across the capacitor, and activates the first operation mode when the power consumption is low, and activates the second operation mode when the power consumption is high.
  • the DC power supply device According to the DC power supply device according to the present invention, it can be applied to a product having a wide range of power consumption, and has an effect that efficiency can be improved according to the power consumption.
  • FIG. 1 is a first diagram used for explaining the operation of a metal oxide semiconductor field effect transistor (Metal Oxide Semiconductor Field Effect Transistor: MOSFET) in the DC power supply device according to the first embodiment.
  • FIG. 2 used to explain the operation of the MOSFET in the DC power supply device according to the first embodiment.
  • a block diagram showing an example of a hardware configuration that realizes the functions of the control unit shown in FIG. A block diagram showing another example of a hardware configuration that realizes the function of the control unit shown in FIG.
  • the figure used for the explanation of the operation mode in the control part of Embodiment 1. A circuit diagram showing a circuit configuration of a drive circuit in the rectifier circuit of the second embodiment.
  • the figure used for the explanation of the detection timing of the direct current in Embodiment 4. The figure which shows the 1st operation waveform which operates the switching element of the rectifier circuit in Embodiment 4.
  • FIG. 1 is a diagram showing a configuration of a motor drive device including a power conversion device according to the first embodiment.
  • the motor drive device 100 according to the first embodiment includes a reactor 2, a rectifier circuit 3, a capacitor 4, an inverter circuit 5, a power supply voltage zero cross detection circuit 7, a DC voltage detection circuit 8, and a DC. It includes current detection circuits 9 and 10 and a control unit 11.
  • the reactor 2, the rectifier circuit 3, the capacitor 4, the power supply voltage zero cross detection circuit 7, the DC voltage detection circuit 8, and the control unit 11 constitute the DC power supply device 50 according to the first embodiment.
  • the DC power supply device 50, the inverter circuit 5, the DC current detection circuit 10, and the control unit 11 constitute the power conversion device 70 according to the first embodiment.
  • the control unit 11 is configured as a common control unit that controls each of the rectifier circuit 3 and the inverter circuit 5, but two rectifier circuits 3 and the inverter circuit 5 are individually controlled. It may be configured to include a control unit.
  • the reactor 2 may be an external component when viewed from the DC power supply device 50.
  • the capacitor 4 is a component of the DC power supply device 50 here, it may be a component of the inverter circuit 5.
  • the rectifier circuit 3 has switching elements SW3-1 to SW3-4 which are MOSFETs, and is connected to the AC power supply 1 via the reactor 2.
  • the four switching elements SW3-1 to SW3-4 are bridge-connected, and each of the switching elements SW3-1 to SW3-4 has a parasitic diode D3-1 to D3-4 inside.
  • the switching elements SW3-1 to SW3-4 the switching elements SW3-1 and SW3-2 may be referred to as "upper arm switching element” or simply "upper arm”.
  • the switching elements SW3-3 and SW3-4 may be referred to as a "lower arm switching element” or simply a "lower arm”.
  • each of the set of switching elements SW3-1 and SW3-3 and the set of switching elements SW3-2 and SW3-4 may be referred to as "upper and lower arms”.
  • the rectifier circuit 3 further includes drive circuits 3a to 3d for driving each of the switching elements SW3-1 to SW3-4.
  • the rectifier circuit 3 converts the AC power of the AC power supply 1 supplied via the reactor 2 into DC power.
  • the reactor 2 is connected between the AC power supply 1 and the rectifier circuit 3 and smoothes the power supply current Is supplied from the AC power supply 1 to the rectifier circuit 3.
  • the capacitor 4 is a smoothing capacitor.
  • the capacitor 4 has a positive electrode terminal and a negative electrode terminal.
  • the capacitor 4 is connected between the output terminals of the rectifier circuit 3 and smoothes the output voltage of the rectifier circuit 3.
  • the inverter circuit 5 has six switching elements SW5-1 to SW5-6 connected by a bridge, and is connected to the output end of the rectifier circuit 3.
  • the rectifier circuit 3 and the inverter circuit 5 are connected by a pair of DC bus lines 16a on the positive side and a DC bus line 16b on the negative side.
  • the connection point on the positive electrode side of the capacitor 4 on the positive DC bus 16a is shown as P
  • the connection point on the negative electrode side of the capacitor 4 on the negative DC bus 16b is shown as N.
  • the inverter circuit 5 converts the DC power output by the rectifier circuit 3 into three-phase AC power and supplies it to the motor 6 which is a three-phase motor. That is, the motor 6 is driven by the three-phase electric power output from the inverter circuit 5.
  • an example of the switching elements SW5-1 to SW5-6 is the MOSFET shown in the figure, but an insulated gate bipolar transistor (IGBT) may be used.
  • Each of the switching elements SW5-1 to SW5-6 includes diodes D5-1 to D5-6 connected in antiparallel.
  • the anti-parallel connection means that the drain of the MOSFET and the cathode of the diode are connected, and the source of the MOSFET and the anode of the diode are connected.
  • the power supply voltage zero cross detection circuit 7 determines the polarity of the power supply voltage Vs based on the power supply voltage Vs which is the output voltage of the AC power supply 1.
  • the DC voltage detection circuit 8 detects the voltage across the capacitor 4.
  • the DC current detection circuit 9 detects the current flowing through the rectifier circuit 3.
  • the DC current detection circuit 10 detects the current flowing through the inverter circuit 5.
  • Each detection signal of the power supply voltage zero cross detection circuit 7, the DC voltage detection circuit 8, the DC current detection circuit 9, and the DC current detection circuit 10 is input to the control unit 11.
  • the power supply voltage zero cross detection circuit 7 may be referred to as a "first detector”
  • the DC voltage detection circuit 8 may be referred to as a "second detector”.
  • the current flowing through the rectifier circuit 3 may be referred to as a "first current”, and the DC current detection circuit 9 for detecting the first current may be referred to as a "first current detector”.
  • the current flowing through the inverter circuit 5 may be referred to as a "second current”, and the DC current detection circuit 10 for detecting the second current may be referred to as a "second current detector”.
  • the DC current detection circuit 9 amplifies the voltage drop in the shunt resistor 9a caused by the DC current flowing in the shunt resistor 9a by the amplifier 9b and gives it to the control unit 11.
  • the DC current detection circuit 10 amplifies the voltage drop in the shunt resistor 10a caused by the DC current flowing through the shunt resistor 10a by the amplifier 10b and gives it to the control unit 11.
  • the amplifiers 9b and 10b can be configured by using an operational amplifier.
  • the DC current detection circuits 9 and 10 of the first embodiment are configured to detect the DC current by amplifying the voltage drop in the shunt resistor 9a or the shunt resistor 10a, but the current transformer capable of detecting the DC current. (Curent Tracer: CT) may be used. Further, in FIG. 1, one resistor is shown as the shunt resistor 9a or the shunt resistor 10a, but two or three or more resistors may be provided.
  • the control unit 11 includes analog-digital (AD) conversion units 12 to 14.
  • the detection signal of the DC voltage detection circuit 8 is an analog signal, and is converted into a digital signal indicating a detection value by the AD conversion unit 12.
  • Each of the detection signals of the DC current detection circuits 9 and 10 is also an analog signal, and each of them is converted into a digital signal indicating a detection value by the AD conversion units 13 and 14.
  • the control unit 11 turns on or off the switching elements SW3-1 to SW3-4 of the rectifier circuit 3 based on the polarity discrimination signal zc by the power supply voltage zero cross detection circuit 7 and the detection value of the DC current detection circuit 9.
  • the control signals Sa to Sd to be controlled are generated.
  • the control signals Sa to Sd are output to the corresponding drive circuits 3a to 3d.
  • the drive circuits 3a to 3d drive the corresponding switching elements SW3-1 to SW3-4 based on the control signals Sa to Sd, respectively.
  • control unit 11 controls the on / off of the switching elements SW5-1 to SW5-6 of the inverter circuit 5 based on the detected values of the DC voltage detection circuit 8 and the DC current detection circuit 10.
  • the control signals UP, VP, WP, UN, VN, and WN are output to the corresponding drive circuits 5a to 5f.
  • the drive circuits 5a to 5f drive the corresponding switching elements SW5-1 to SW5-6 based on the control signals UP, VP, WP, UN, VN, and WN, respectively.
  • the motor 6 is connected to the output end of the inverter circuit 5.
  • the inverter circuit 5 drives the motor 6 by supplying AC power to the motor 6.
  • An example of the motor 6 is a permanent magnet electric motor.
  • the motor 6 includes a stator 6a with a three-phase Y-type connection in which three-phase windings including U-phase, V-phase, and W-phase windings are connected in a Y shape, and a permanent magnet rotor 6b.
  • One ends of the U-phase, V-phase, and W-phase windings are connected to each other, and the other ends of the respective windings form a U terminal, a V terminal, and a W terminal, respectively.
  • the stator 6a of the motor 6 exemplifies a stator of a three-phase Y-type connection, but may be composed of a stator of a three-phase delta-type connection. Needless to say, the phase current information that can be detected from the DC current changes between the three-phase Y-type connection and the three-phase ⁇ -type connection.
  • connection point between the switching element SW5-1 and the switching element SW5-4 of the inverter circuit 5 is connected to the terminal U of the motor 6, and the connection point between the switching element SW5-2 and the switching element SW5-5 is connected to the terminal V. It is connected, and the connection point between the switching element SW5-3 and the switching element SW5-6 is connected to the terminal W.
  • the current flowing through the U-phase winding is called a U-phase current and is represented by "Iu”.
  • V-phase current and W-phase current are referred to as V-phase current and W-phase current, respectively, and are represented by "Iv” and "Iw", respectively.
  • FIG. 2 is a first diagram used for explaining the operation of the MOSFET in the DC power supply device 50 according to the first embodiment.
  • FIG. 3 is a second diagram used for explaining the operation of the MOSFET in the DC power supply device 50 according to the first embodiment.
  • FIG. 2 shows the current flow when the gate is off. Gate-off is a state in which a current flows through a parasitic diode formed inside the MOSFET. Further, FIG. 3 shows the current flow when the gate is on. Gate-on is a state in which a voltage is applied between the gate and the source of the MOSFET and a current is flowing to the FET main body side of the MOSFET. When the gate is turned on, the current flows on the FET main body side because the impedance on the FET main body side is lower than that on the parasitic diode.
  • synchronous rectification is a control method in which the MOSFET is turned on at the timing when a current flows in the same direction as the parasitic diode to flow a current to the FET main body side.
  • a forward voltage drop (so-called Vf) in the parasitic diode occurs by about 3V. Therefore, the voltage characteristics on the parasitic diode side are worse than those on the FET main body side, and the loss is large. Further, in the case of a MOSFET formed of a WBG semiconductor, the on-resistance of the FET body is also low. Therefore, by positively utilizing synchronous rectification, further reduction in loss can be achieved.
  • the MOSFET formed of the WBG semiconductor has been described here, the present invention is not limited to this. Any element may be used as long as it can utilize synchronous rectification.
  • FIG. 4 is a block diagram showing an example of a hardware configuration that realizes the function of the control unit 11 of FIG.
  • FIG. 5 is a block diagram showing another example of a hardware configuration that realizes the function of the control unit 11 of FIG.
  • the processor 300 that performs the calculation, the memory 302 that stores the program read by the processor 300, and the input / output of the signal are performed.
  • the configuration can include the interface 304.
  • the processor 300 may be a computing means such as an arithmetic unit, a microprocessor, a microcomputer, a CPU (Central Processing Unit), or a DSP (Digital Signal Processor).
  • the memory 302 includes a non-volatile or volatile semiconductor memory such as a RAM (Random Access Memory), a ROM (Read Only Memory), a flash memory, an EEPROM (Erasable Programmable ROM), or an EEPROM (registered trademark) (Electrically EPROM). It can be exemplified.
  • the memory 302 stores a program that executes the control function of the control unit 11.
  • the processor 300 sends and receives necessary information via the interface 304, the processor 300 executes a program stored in the memory 302, and the processor 300 refers to a table stored in the memory 302. Control can be performed.
  • the calculation result by the processor 300 can be stored in the memory 302.
  • the processor 300 and the memory 302 shown in FIG. 4 may be replaced with the processing circuit 305 as shown in FIG.
  • the processing circuit 305 corresponds to a single circuit, a composite circuit, an ASIC (Application Specific Integrated Circuit), an FPGA (Field-Programmable Gate Array), or a combination thereof.
  • the information input to the processing circuit 305 and the information output from the processing circuit 305 can be performed via the interface 304.
  • FIG. 6 is a diagram showing a first operation waveform for operating the switching elements SW3-1 to SW3-4 of the rectifier circuit 3 in the first embodiment.
  • FIG. 6A shows the waveform of the power supply voltage Vs which is the output voltage of the AC power supply 1
  • FIG. 6B shows the polarity discrimination signal zc output from the power supply voltage zero cross detection circuit 7. ing.
  • the polarity of the polarity discrimination signal zc is treated as positive in the direction of the arrow of the power supply voltage Vs shown in FIG. According to this definition, the polarity of the polarity discrimination signal zc is as shown in FIG.
  • the polarity discrimination signal zc becomes “H” (high: High).
  • the polarity discrimination signal zc becomes “L” (low).
  • FIG. 6C shows the waveform of the direct current Idc1.
  • the polarity of the direct current Idc1 is positive in the direction of the arrow shown in FIG.
  • the current in the direction of the arrow is detected negatively in the shunt resistor 9a in relation to the ground (GND) position shown in FIG. 1, but is polar in the processing of the control unit 11.
  • the reversal can be done freely.
  • the waveform of the direct current Idc1 is shown as a positive electrode for ease of viewing.
  • the cause of the overcurrent can be determined only by the polarity of the direct current Idc1.
  • the direct current Idc1 flows in the direction of the arrow shown in FIG. 1, the negative electrode property is defined.
  • a positive overcurrent it can be determined that the overcurrent is an overcurrent generated when the upper and lower arms are short-circuited. This is because when the upper and lower arms are short-circuited, a positive DC current Idc1 flows.
  • a negative electrode overcurrent it can be determined that the overcurrent is an overcurrent generated at the time of overload. This is because the negative electrode direct current Idc1 flows when the load is overloaded.
  • the DC current detection circuit 9 is inserted between the common GND terminal and the connection point on the source terminal side of the switching elements SW3 and SW3-4 which are MOSFETs.
  • the power conversion device 70 shown in FIG. 1 can be configured as a non-isolated power conversion device using a common GND.
  • the device can be configured without using an insulating circuit such as an insulating amplifier or a photocoupler, so that signal transmission / reception can be speeded up. Further, a highly responsive power conversion device can be provided at low cost.
  • the switching elements SW3-1 to SW3-4 are controlled based on the polarity discrimination signal zc by the power supply voltage zero cross detection circuit 7 and the detection value of the DC current detection circuit 9.
  • the control unit 11 turns on the switching element described below when the detected value of the direct current Idc1 is equal to or higher than a predetermined threshold value, and turns off the switching element described below when the detected value is equal to or lower than the threshold value.
  • This threshold is indicated by "Idc_on" in FIG. 6 (c).
  • the on threshold value and the off threshold value are shown with the same value, but the present invention is not limited to this. Hysteresis may be provided between the on threshold and the off threshold so that the on threshold and the off threshold are different. Further, although it has been described here that it is above the threshold value and below the threshold value, it goes without saying that the threshold value may be exceeded or below the threshold value.
  • Two of SW3-1 to 3-4 are switching elements that are turned on when the detected value of the DC current Idc1 exceeds a predetermined threshold value. These two are determined based on the polarity of the AC power supply 1 detected by the power supply voltage zero cross detection circuit 7, that is, the polarity discrimination signal zc.
  • the switching elements SW3-1 and SW3-4 are controlled to be ON as shown in FIGS. 6 (d) and 6 (g).
  • the switching elements SW3 and SW3-3 are controlled to be ON as shown in FIGS. 6 (e) and 6 (f).
  • the rectifier circuit 3 is composed of MOSFETs, as shown in FIG. 1, a parasitic diode is added to the MOSFETs. Therefore, even if the ON signal is not supplied to the gate of the MOSFET, the parasitic diode is turned on and a current called a capacitor input flows from the AC power supply 1. By turning on the MOSFET at the timing when this current flows, as shown in FIG. 2, the loss of the rectifier circuit 3 can be reduced by the synchronous rectification in which the current flows to the FET main body side having a low on-resistance.
  • FIG. 7 is a diagram showing a second operation waveform for operating the switching elements SW3-1 to SW3-4 of the rectifier circuit 3 in the first embodiment.
  • the arrangement of the signal waveforms in FIG. 7 is the same as that in FIG.
  • the switching elements SW3-1 and SW3-3 are controlled by the control unit 11 for pulse width modulation (PWM).
  • PWM control it is possible to generate a sine wave waveform of the current flowing from the AC power supply 1 to the rectifier circuit 3.
  • boost control that raises the voltage between the connection point PN, which is the voltage across the capacitor 4, to ⁇ 2 times or more the effective value of the power supply voltage Vs is also possible.
  • the power supply factor can be controlled to be substantially 1, and the power supply harmonic current can be controlled to be approximately 0.
  • the voltage across the capacitor 4 can be boosted by PWM-controlling the switching elements SW3-1 and SW3-3. Therefore, by increasing the boosted voltage, an operating range with large power consumption is satisfied. be able to.
  • the current capacities of the inverter circuit 5 and the motor 6 are fixed, and the current capacities of the switching elements SW5-1 to SW5-6 in the inverter circuit 5 are selected according to the current capacity of the motor 6. For example, when a switching element having a large current capacity is used in the inverter circuit 5, the conduction loss and the switching loss generated when the switching elements SW5-1 to SW5-6 are turned on tend to be larger than those of the switching element having a small current capacity. There is.
  • the inverter circuit 5 becomes a very expensive circuit. Therefore, in order to provide a product with a wide range of power consumption to a user at an appropriate selling price, it is required to select a switching element having a small current capacity.
  • the technique of the first embodiment is applied. Specifically, in the operating range where the power consumption is large, the switching elements SW3-1 and SW3-3 constituting the rectifier circuit 3 are PWM-controlled. The output voltage of the rectifier circuit 3 is boosted by PWM control. Since the output voltage of the rectifier circuit 3 is boosted, it is possible to increase the power consumption by the amount of the voltage increase without increasing the current capacity of the inverter circuit 5 and the motor 6. As a result, it is possible to obtain a power conversion device that can be applied to a highly efficient product.
  • the technique of the first embodiment is applied, a switching element having a small current capacity can be used. As a result, the loss of the inverter circuit 5 can be reduced in the operating range where the power consumption is small. Then, it is possible to configure the power conversion device with less loss under any condition from the condition that the range of power consumption is narrow to the condition that the range of power consumption is wide. Further, it is possible to increase the maximum load amount by boosting the output voltage of the rectifier circuit 3. Therefore, according to the power conversion device according to the first embodiment, it is possible to achieve both the energy saving characteristic by improving the efficiency at the time of low load and the high power characteristic with the maximum load raised.
  • FIG. 8 is a diagram showing a third operation waveform for operating the switching elements SW3-1 to SW3-4 of the rectifier circuit 3 in the first embodiment.
  • FIG. 8 shows an operation waveform different from that of FIGS. 6 and 7.
  • the signal waveforms of (a), (b), (d) to (g) excluding (c) are shown for 1.5 cycles.
  • a waveform of the power supply current Is is shown between (b) and (d).
  • the power supply short-circuit operation is performed for only one pulse in the power supply half cycle, but the present invention is not limited to this. Even if a power short-circuit operation of a plurality of pulses is performed in a power supply half cycle, it can be carried out without deviating from the object of the present invention.
  • the threshold value Idc_on in FIG. 8 is set higher than that in FIG. In FIG. 8, when “H” is output from the polarity discrimination signal zc when the power supply voltage Vs is positive, the switching element SW3-3 is first turned on and the power supply is short-circuited after a preset time has elapsed. The state is formed. Then, the switching elements SW3-1 and SW3-4, which are positively operated, are turned on by the threshold value Idc_on. In this operation, if the switching elements SW3-1 and SW3-4 are turned off at the threshold value Idc_on, the synchronous rectification state ends early, and the time for the current to flow through the parasitic diode becomes long. Therefore, in FIG.
  • the timing for ending the synchronous rectification that is, the timing for turning off the switching elements SW3-1 and SW3-4 is set by the threshold value Idc_off.
  • the state of synchronous rectification in which a current flows through the FET main body can be maintained for a longer time than when the switching elements SW3-1 and SW3-4 are turned off at the threshold value Idc_on.
  • FIG. 9 is a diagram showing a fourth operation waveform for operating the switching elements SW3-1 to SW3-4 of the rectifier circuit 3 in the first embodiment.
  • FIG. 9 shows an operation waveform different from each of the drawings of FIGS. 6 to 8.
  • the arrangement of the signal waveforms in FIG. 9 is the same as that in FIG.
  • the value of the threshold value Idc_on in FIG. 9 is the same as that in FIG.
  • the switching element SW3-1 is controlled to be OFF only when the switching element SW3-3 is controlled to be ON.
  • the control unit 11 sets a threshold value different from the threshold value Idc_on, and controls the switching elements SW3-1 and SW3-3 so that the ON operation is switched from the switching element SW3-1 to the switching element SW3-3. become.
  • the control of FIGS. 6 and 7 is selectively carried out by the control unit 11. Specifically, the control unit 11 performs the control shown in FIG. 6 when the power supplied from the AC power supply 1 is lower than the preset set value, and when it is higher than the preset set value, FIG. 7 The control shown in is performed.
  • the case where the power supplied from the AC power supply 1 is lower than the preset set value means that the power consumption of a load (not shown) connected to the motor 6 is low. Such a state is called “low power consumption”.
  • the case where the power supplied from the AC power source 1 is higher than the preset set value means the case where the power consumption of the load is high. Such a state is called "high power consumption”.
  • an intermediate state between the time of low power consumption and the time of high power consumption is called “medium power consumption”.
  • the power supplied from the rectifier circuit 3 to the inverter circuit 5 also becomes large. Therefore, each state according to the level of the power supplied from the rectifier circuit 3 to the inverter circuit 5 may be referred to as “low power consumption”, “medium power consumption”, and “high power consumption”. ..
  • FIG. 10 is a diagram used for explaining the operation mode in the control unit 11 of the first embodiment.
  • the control unit 11 has at least three operation modes, that is, a first operation mode, a second operation mode, and a third operation mode.
  • the first operation mode is an operation mode in which each switching element of the rectifier circuit 3 is subjected to the synchronous rectification shown in FIG.
  • the second operation mode is an operation mode in which each switching element of the rectifier circuit 3 is subjected to the PWM control shown in FIG. 7.
  • the third operation mode is an operation mode in which each switching element of the rectifier circuit 3 is subjected to the control shown in FIG.
  • the control unit 11 activates any one of these three operation modes according to the power consumption of the load to control each switching element of the rectifier circuit 3.
  • Ps_PS is a threshold value at the time of shifting from the first operation mode to the third operation mode.
  • Ps_SP is a threshold value when shifting from the third operation mode to the first operation mode
  • Ps_SF is a threshold value when shifting from the third operation mode to the second operation mode. It is a threshold value
  • Ps_FS is a threshold value when shifting from the second operation mode to the third operation mode.
  • the first operation mode is an operation mode carried out at the time of low power consumption
  • the second operation mode is an operation mode carried out at the time of high and low power consumption
  • the third operation mode is a medium power consumption. This is the operation mode that is sometimes implemented.
  • the two threshold values "Ps_PS" and “Ps_SP” are provided with a hysteresis characteristic in order to stabilize the control. The same applies to the two thresholds "Ps_SF" and "Ps_FS".
  • control shown in FIG. 8 is performed in the third operation mode, but the control shown in FIG. 9 may be performed instead of FIG.
  • the power supplied from the AC power source 1 is used for determining whether the power consumption Ps of the load is low power consumption, medium power consumption, or high power consumption.
  • the electric power obtained by calculation from the detected values detected by the DC current detection circuit 9 and the DC voltage detection circuit 8 may be used. Further, the determination may be made based on a detection value in a power detection circuit (not shown) that detects the power supplied from the AC power supply 1.
  • switching may be performed based on the rotation speed of the motor 6 or the motor current flowing through the motor 6.
  • any detected value may be used as long as it does not deviate from the object of the present invention.
  • the first operation mode in which the MOSFET is turned on at the timing when the current flows in the same direction as the parasitic diode and the MOSFET are pulse-width. It has a second operation mode in which modulation control is performed to boost the voltage across the capacitor. Then, the control unit provided in the DC power supply device activates the first operation mode when the power consumption is low, and activates the second operation mode when the power consumption is high. As a result, it can be applied to products having a wide range of power consumption, and efficiency can be improved according to the power consumption.
  • the DC power supply device when the power consumption is low, the number of switchings can be reduced as much as possible, and a low loss effect can be obtained by synchronous rectification of the MOSFET. Further, when the power consumption is high, the DC voltage can be boosted by PWM control of the MOSFET, and the current flowing through the inverter circuit and the motor can be reduced. This makes it possible to apply an inexpensive MOSFET with low loss. As a result, it is possible to provide a low-loss power conversion device.
  • FIG. 11 is a circuit diagram showing a circuit configuration of drive circuits 3a to 3d in the rectifier circuit 3 of the second embodiment.
  • the drive circuit 3a is a drive circuit that drives the switching element SW3-1 in which the source terminal of the MOSFET is electrically connected to the AC power supply 1 via the reactor 2.
  • the drive circuit 3b is a drive circuit that drives the switching element SW3-2 in which the source terminal of the MOSFET is electrically connected to the AC power supply 1 via the reactor 2.
  • the same or equivalent components as those in the first embodiment shown in FIG. 1 are designated by the same reference numerals, and redundant description will be omitted.
  • the source terminal of the MOSFET is electrically connected to the common GND via the DC current detection circuit 9. Therefore, the drive circuits 3c and 3d can receive the drive power of the MOSFET directly from the control power supply 22 connected to the common GND.
  • the switching elements SW3-1 and SW3-2 since the source terminal of the MOSFET is electrically connected to the AC power supply 1, the driving power cannot be directly supplied from the control power supply 22.
  • the drive circuit 3a is connected to the control power supply 22 via a series circuit of the diode 20a and the resistor 21a.
  • the control power supply 22 and the drive circuit 3a are electrically connected, and the drive power for driving the MOSFET at the gate can be supplied.
  • the electric power supplied at this time is charged in the capacitor 23a. Therefore, even when the diode 20a is turned off and the driving power is not supplied, the driving power can be supplied to the switching element SW3-1.
  • the drive circuit 3b is also connected to the control power supply 22 via a series circuit of the diode 20b and the resistor 21b.
  • Diodes 20a and 20b and capacitors 23a and 23b are important key components for this bootstrap.
  • the diodes 20a and 20b will be referred to as “boot diodes 20a and 20b”
  • the capacitors 23a and 23b will be referred to as “boot capacitors 23a and 23b”.
  • the operation will be described focusing on the boot diode 20a and the boot capacitor 23a.
  • the negative electrode terminal of the boot capacitor 23a is connected to the source terminal of the switching element SW3-1 which is a MOSFET, and the positive electrode terminal of the boot capacitor 23a is connected to the control power supply 22 via a series circuit of the diode 20a and the resistor 21a.
  • the boot capacitor 23a When the switching element SW3-3 connected to the negative electrode side of the boot capacitor 23a is turned on, the boot capacitor 23a is charged with electric charge and the driving power is secured.
  • the rectifier circuit 3 of the first embodiment even if the MOSFET of the switching element SW3-3 is not turned on, the parasitic diode D3-3 is turned on when the charging current from the AC power supply 1 flows through the capacitor 4. , The charge of the boot capacitor 23a is realized. Charging of the boot capacitor 23b is also realized by the same operation.
  • the voltage characteristics of the parasitic diode are poor and the voltage effect of the parasitic diode is large. Therefore, the charge voltage of the boot capacitor needs to be as high as the Vf of the parasitic diode. Due to this Vf, the drive of the MOSFET may become unstable.
  • the term "unstable" as used herein means that, for example, the balance of switching characteristics such as dv / dt is lost between the switching element of the upper arm and the switching element of the lower arm connected in series. If the switching characteristics are out of balance, the behavior of the rectifier circuit 3 may become unstable.
  • FIG. 12 is a diagram showing an operation waveform in the charge mode according to the second embodiment. The arrangement of the signal waveforms in FIG. 12 is the same as that in FIG.
  • the switching element SW3-4 is controlled to be turned on in a half cycle in which the polarity of the power supply voltage Vs is positive.
  • the negative electrode terminal of the boot capacitor 23b is electrically connected to the GND potential via the FET main body side of the MOSFET instead of the parasitic diode.
  • the switching element SW3-3 In the half cycle when the polarity of the power supply voltage Vs is negative, the switching element SW3-3 is controlled to be ON, and the charging operation of the boot capacitor 23a is improved.
  • the subsequent operation is the same as that of the boot capacitor 23b, and the duplicate description is omitted.
  • the switching elements SW3-1 and SW3-2 can be driven by charging the boot capacitor with an electric charge. Further, since the switching elements SW3-1 and SW3-2 can be driven without providing a control power supply exclusively for the drive circuits 3a and 3b, the DC power supply device and the power conversion device can be miniaturized.
  • FIG. 13 is a diagram showing an operation waveform of the rectifier circuit 3 according to the third embodiment.
  • the operation waveform diagram corresponding to FIG. 13 is FIG. 7.
  • the switching element that operates in PWM is replaced every power cycle, which is the cycle of the AC power supply 1. More specifically with reference to FIG. 13, first, the switching element SW3-1 and the switching element SW3-4 operate as a set, and the switching element SW3-2 and the switching element SW3-3 operate as a set. Then, when the switching element SW3-1 is in PWM operation, the switching element SW3-4 continues to operate independently of PWM in order to realize synchronous rectification. Further, after the PWM operation of the switching element SW3-1, the switching element SW3-4 becomes the PWM operation, and the switching element SW3-1 changes to the operation of continuing the on operation unrelated to the PWM. These operations are the same in the set of the switching element SW3-2 and the switching element SW3-3.
  • an embodiment in which the PWM operations are not alternately replaced is also effective from another viewpoint.
  • the heat dissipation design can be integrated into the two switching elements.
  • the reliability of the entire device can be increased by increasing the reliability of the two switching elements. That is, in terms of product quality, the operation shown in FIG. 7 or the operation shown in FIG. 13 may be performed, and any operation may be performed.
  • the set of two switching elements is exchanged for each cycle of the AC power supply 1, but the present invention is not limited to this.
  • the replacement cycle may be replaced every two cycles, or may be replaced at a cycle of an integral multiple of 3 or more.
  • the variation of the four switching elements causes an imbalance in which the positive and negative waveforms of the input current have an asymmetrical shape in the input current flowing from the AC power supply 1.
  • the variation between the elements is made uniform. As a result, the waveform imbalance in the input current is suppressed.
  • the switching element by PWM operation is used as a reference so that the relative imbalance is suppressed with reference to any of the four switching elements. You may adjust the on-time of. Even with such control, the imbalance of the waveform in the input current can be suppressed. As a result, it is possible to suppress the generation of harmonic currents that do not originally occur, such as the even-numbered order of the AC power supply 1. Further, since the harmonic current can be reduced, it is possible to provide a power conversion device that does not cause a failure to the AC power supply 1.
  • the imbalance is not suppressed even if the correction is made to a certain threshold value, it is judged that one of the switching elements is open failure.
  • An open failure cannot be detected by normal control because the path through which the current flows is open.
  • the imbalance generation pattern changes. From this change, it is possible to determine which switching element has an open failure.
  • the open failure of the switching element may be determined only by the amount of imbalance generated without performing the correction up to a certain threshold value. Further, in order to detect imbalance, an operation mode in which correction is not performed may be intentionally or forcibly created. In addition, although some other applications can be assumed, any method may be used as long as it does not deviate from the object of the present invention.
  • FIG. 14 is a diagram showing an operation waveform of the rectifier circuit 3 according to the fourth embodiment.
  • FIG. 14 shows the drive waveforms of the switching elements SW3-1 and SW3-3 when the PWM operation shown in FIG. 7 or 13 is performed, and the waveforms of the carriers used for generating the PWM signal.
  • “Sa” is a control signal for controlling the switching element SW3-1
  • “Sc” is a control signal for controlling the switching element SW3-3.
  • a method called complementary PWM is adopted.
  • control signals having an exclusive relationship are generated so that the switching elements of the upper and lower arms are not turned on at the same time.
  • one or both of the peaks and valleys of the triangular wave which is the reference of the PWM cycle, is set as the control reference time. Specifically, the time when the control algorithm starts operating is based on a peak or a valley. Further, in the AD conversion units 12 to 14 that perform AD conversion of the detection signal, a peak or a valley is used as a reference for the time for holding the detection signal, the timing time for starting the AD conversion, and the like.
  • the modulated wave signal is changed every carrier cycle.
  • the duty of the modulated wave signal is set with reference to the peak of the carrier of the triangular wave.
  • the control signal Sa that controls the switching element SW3-1 has a waveform that is symmetrical with respect to the dotted line in the figure with respect to the mountain.
  • the control signal Sc that controls the switching element SW3-3 has a left-right asymmetric waveform with respect to the dotted line in the figure with respect to the valley. Further, the center of the control signal Sc is deviated from the carrier cycle.
  • the detected current will not be at the center timing of turning on the switching element, and a detection error will occur.
  • This detection error causes an imbalance in the input current and can also be a trigger to break the control algorithm.
  • the switching elements SW3-1 and SW3-3 of the upper and lower arms connected in series always have a direct current at the center timing of the period during which the control signals Sa and Sc are turned on.
  • the control unit 11 is configured to generate a timing signal for sampling in a time shorter than the half cycle of the carrier so as to be detected. As a result, an unintended detection error can be suppressed, and the operational stability of the rectifier circuit 3 can be improved.
  • the central timing of the period during which the control signals Sa and Sc are turned on does not have to be the central timing of the period during which the control signals Sa and Sc are turned on.
  • the time ratio between the first time between the time when the on-pulse rises and the time when the direct current is detected and the second time which is the width of the on-pulse is the control signal Sa As long as it is the same as Sc, it may be a pulse head portion or a pulse rear portion.
  • the switching element SW3-1 and the switching element SW3-3 do not have the same duty, and the on-pulse widths of the two are different. Therefore, it is complicated to calculate the timing time at which the above time ratios are the same. Therefore, the method of detecting the central portion of the pulse may be simple.
  • FIG. 15 is a diagram used for explaining the detection timing of the direct current Idc1 in the fourth embodiment.
  • FIG. 15 shows a waveform of the direct current Idc1, and black circle dots representing the time of detection timing of the direct current Idc1 are plotted on the waveform.
  • the plot interval of the black circle points is a half carrier period.
  • FIG. 15 is an example of a case where the current detection sampling is relatively rough.
  • the processing start timing in the processor is indicated by a downward arrow.
  • the intervals between the arrows are two carrier cycles. These two carrier cycles are the cycles of the control algorithm, and thinning control is performed by thinning out some of the detected currents detected in the carrier half cycle.
  • the current detection control is performed on the assumption that the sampling cycle of the current detection cannot be shortened. Specifically, the current detected current is estimated from the past detected current. Then, when it is predicted that the threshold will be exceeded between the previous sampling time and the current sampling time, the sampling interval is controlled so that the time predicted to exceed the threshold becomes the sampling time, and forced at the sampling time. The control is to detect the current. Alternatively, the switching element may be forcibly switched on and off at the predicted time. With these controls, even with the thinning control as shown in FIG. 15, current sampling can be performed at the required time, and the required current can be detected relatively accurately. This makes it possible to provide a power conversion device having a higher performance boosting function while using an inexpensive processor.
  • FIG. 16 is a diagram showing a first operation waveform for operating the switching element of the rectifier circuit 3 according to the fourth embodiment.
  • the operation waveform diagram corresponding to FIG. 16 is FIG. 6 or FIG.
  • the waveform of the phase ⁇ s of the power supply voltage Vs is shown. That is, in the rectifier circuit 3 of the fourth embodiment that controls the operation of FIG. 16, a function of detecting or calculating the phase ⁇ s of the power supply voltage Vs is added.
  • control signal Sa that controls the on / off of the switching element SW3-1 is controlled based on the phase ⁇ s of the power supply voltage Vs.
  • a simultaneous on prevention phase angle ( ⁇ 5 degrees in the figure) is set in order to avoid simultaneous on of the switching element when the polarity is reversed. As a result, it is possible to reliably suppress the short circuit between the upper and lower arms.
  • FIG. 17 is a diagram showing a second operation waveform for operating the switching element of the rectifier circuit 3 in the fourth embodiment.
  • the control signal Sa that controls the switching element SW3-1 is controlled based on the phase ⁇ s of the power supply voltage Vs, but in FIG. 17, the control signal Sd that controls the switching element SW3-4 is controlled. ing.
  • synchronous rectification can be performed while the parasitic diode of the MOSFET on the upper arm side maintains the reverse recovery characteristic. This makes it possible to operate the power conversion device more stably.
  • FIG. 18 is a diagram showing a configuration of a motor drive device including the power conversion device according to the fifth embodiment.
  • the DC power supply device 50 in the configuration of the motor drive device 100 according to the first embodiment shown in FIG. 1, the DC power supply device 50 is replaced with the DC power supply device 50A to convert power.
  • the device 70 has been replaced by the power converter 70A.
  • a relay 15 connected in parallel to the reactor 2 and a reactor 2a connected in series to the reactor 2 are added.
  • the reactor 2a may be referred to as a "second reactor".
  • other configurations are the same as or equivalent to the configuration of the first embodiment, and the same or equivalent components are designated by the same reference numerals, and duplicate description will be omitted.
  • the relationship between the inductance value L0 of the reactor 2 and the inductance value La of the second reactor 2a is set to L0> La.
  • the opening and closing of the relay 15 is controlled by the control unit 11 according to the operation modes of the switching elements SW3-1 to SW3-4.
  • the relay 15 is controlled to the open state.
  • the inductance value of the circuit is L0 + La.
  • the relay 15 is controlled to the closed state. At this time, the inductance value of the circuit becomes the minimum necessary inductance value La. Thereby, the inductance value of the reactor suitable for the second operation mode can be set.
  • the second operation mode is an operation mode in which PWM control is performed. If a reactor having an inductance value larger than necessary is used in PWM control, the voltage across the reactor becomes too large, which may cause insulation deterioration. Therefore, if a common reactor is used in the first operation mode and the second operation mode, more expensive parts are required.
  • the relay 15 can control the inductance value of a suitable reactor according to the operation mode. As a result, the rectifier circuit 3 can be operated with higher efficiency and higher power factor. In addition, the rectifier circuit 3 can be operated with less generation of harmonic current. Moreover, the power conversion device can be realized with inexpensive and small parts.
  • the relay 15 is used to switch the inductance value of the reactor, but the configuration is not limited to this. Any means may be used as long as it is a switch capable of short-circuiting both ends of the reactor 2.
  • FIG. 19 is a diagram showing a configuration of a motor drive device including the power conversion device according to the sixth embodiment.
  • the DC power supply device 50A in the configuration of the motor drive device 100A according to the fifth embodiment shown in FIG. 18, the DC power supply device 50A is replaced with the DC power supply device 50B to convert power.
  • the device 70A has been replaced by the power converter 70B.
  • the rectifier circuit 3 is replaced with the rectifier circuit 3A, and the reactor 2a'that is connected in parallel to the reactor 2 is added.
  • the reactor 2a' may be referred to as a "third reactor".
  • the rectifier circuit 3A is composed of 6 switching elements.
  • a switching element SW3-1'having a parasitic diode D3-1'inside and a switching element SW3-3' having a parasitic diode D3-3'inside are added to the rectifier circuit 3A.
  • drive circuits 3a'and 3c'that drive each of the switching elements SW3-1'and SW3-3' are added to the rectifier circuit 3A.
  • the control unit 11 outputs control signals Sa'and Sc'for controlling each of the switching elements SW3-1'and SW3-3'.
  • Other configurations are the same as or equivalent to the configuration of the fifth embodiment, and the same or equivalent components are designated by the same reference numerals, and duplicate description will be omitted.
  • the reactor 2a is connected to the connection point of the switching elements SW3-1 and SW3-3 which are the element pairs connected in series, and the reactor 2a'is the switching element SW3-1 which is the element pair connected in series. It is connected to the connection point of', SW3-3'.
  • the set of switching elements SW3-1 and SW3-3 may be referred to as a "first element pair", and the set of switching elements SW3-1'and SW3-3' may be referred to as a "second element pair".
  • Reactor 2a' is composed of the same inductance value as reactor 2a. If the nominal inductance values are the same, the two inductance values can be regarded as equal, and even if there are measurement errors, errors due to aging, errors due to deterioration, etc., they may be treated as the same. Further, the switching element SW3-1 and the switching element SW3-1'operate in a state in which the phases are reversed by 180 degrees. The relationship with the switching elements SW3-3 and SW3-3'is the same. The control of operating in a state where the phase is inverted by 180 degrees is a control method known as interleaving, and the description thereof is omitted here.
  • the DC power supply device by configuring the DC power supply device as an interleaved configuration, it is possible to configure it by using a reactor having a smaller inductance value.
  • the number of inductors increases, since it can be configured with an inexpensive reactor, it is possible to suppress the harmonic current while suppressing the increase in cost.
  • a general six-element module for an inverter can be applied as the rectifier circuit 3A.
  • versatility and parts procurement can be improved, and a DC power supply device can be constructed at low cost.
  • the current ripple during PWM operation can be substantially halved and noise can be reduced by adopting the interleaved configuration. Further, since the heat life of the parts can be equalized by dispersing the calorific value, the life of the DC power supply device can be extended at low cost.
  • FIG. 20 is a diagram showing a configuration of a motor drive device including the power conversion device according to the seventh embodiment.
  • the DC power supply device 50 is replaced with the DC power supply device 50C to convert power.
  • the device 70 has been replaced by the power converter 70C.
  • a thermistor 16 connected in series to the reactor 2 and a relay 15 connected in parallel to the thermistor 16 are added.
  • Other configurations are the same as or equivalent to the configuration of the first embodiment, the same or equivalent components are designated by the same reference numerals, and duplicate description is omitted.
  • the thermistor 16 is a PTC (Positive Temperature Coafficient) thermistor having a positive temperature coefficient.
  • FIG. 21 is a diagram showing a configuration example of the refrigeration cycle device according to the eighth embodiment.
  • the refrigeration cycle device 120 shown in FIG. 21 is an application example of the motor drive device according to the first to seventh embodiments.
  • FIG. 21 illustrates a separate type air conditioner, it is not limited to the separate type.
  • the refrigeration cycle device 120 is not limited to the air conditioner and can be applied to devices having a refrigeration cycle such as a refrigerator and a freezer.
  • the motor drive device 100 according to the first to fourth embodiments is used for the refrigeration cycle device 120, but the present invention is not limited to this.
  • any one of the motor drive devices 100A to 100C according to the fifth to seventh embodiments may be used for the refrigeration cycle device 120.
  • the refrigeration cycle device 120 includes a compressor 101, a four-way valve 102, an outdoor heat exchanger 103, an expansion valve 104, an indoor heat exchanger 105, a refrigerant pipe 106, and a motor drive device. It has 100.
  • the compressor 101, the four-way valve 102, the outdoor heat exchanger 103, the expansion valve 104, and the indoor heat exchanger 105 form a refrigeration cycle to which the compressor 101 is attached via the refrigerant pipe 106.
  • a compression mechanism 107 for compressing the refrigerant and a motor 6 for operating the compression mechanism 107 are provided inside the compressor 101 in the refrigeration cycle device 120.
  • the motor 6 of the compressor 101 is electrically connected to the motor drive device 100.
  • the motor drive device 100 is used to drive the motor 6 used in the compressor 101 that compresses the refrigerant.
  • the AC power supply 1 is described as a single-phase power supply, but the present invention is not limited to this. If the effects of each of the above-described embodiments can be obtained, a three-phase power supply or a multi-phase power supply may be used instead of the single-phase power supply. This kind of deformation can be done flexibly.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Rectifiers (AREA)
  • Inverter Devices (AREA)

Abstract

Le présent dispositif d'alimentation en courant continu (50) comprend : un circuit redresseur (3) qui comprend une pluralité de MOSFET ayant chacun une diode parasite à l'intérieur, la pluralité de MOSFET étant connectés en pont, et qui est connecté à une alimentation électrique en courant alternatif (1) par l'intermédiaire d'un réacteur (2) ; un condensateur (4) connecté entre des bornes de sortie du circuit redresseur (3) ; un circuit de détection de passage par zéro de tension d'alimentation électrique (7) qui détecte la polarité d'une tension d'alimentation électrique qui est une tension de sortie de l'alimentation électrique en courant alternatif (1) ; et un circuit de détection de courant continu (9) qui détecte un premier courant circulant à travers le circuit redresseur (3). L'unité de commande (11) a un premier mode de fonctionnement dans lequel un redressement synchrone est effectué pour allumer le MOSFET à une synchronisation lorsqu'un courant circule dans la même direction que la diode parasite, et un second mode de fonctionnement dans lequel le MOSFET est commandé par PWM pour amplifier la tension à travers le condensateur (4), active le premier mode de fonctionnement pendant une faible consommation d'énergie, et active le second mode de fonctionnement pendant une consommation d'énergie élevée.
PCT/JP2019/009535 2019-03-08 2019-03-08 Dispositif d'alimentation électrique en courant continu et dispositif de cycle de réfrigération WO2020183553A1 (fr)

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DE112019006992.6T DE112019006992T5 (de) 2019-03-08 2019-03-08 Gleichstromsversorgungsvorrichtung, Leistungswandlungsvorrichtung und Kühlkreislaufvorrichtung
CN201980093589.5A CN113544962A (zh) 2019-03-08 2019-03-08 直流电源装置、电力转换装置以及制冷循环装置
PCT/JP2019/009535 WO2020183553A1 (fr) 2019-03-08 2019-03-08 Dispositif d'alimentation électrique en courant continu et dispositif de cycle de réfrigération
JP2021504633A JP7034373B2 (ja) 2019-03-08 2019-03-08 直流電源装置、電力変換装置及び冷凍サイクル装置

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JP2017042003A (ja) * 2015-08-21 2017-02-23 Ｊｍエナジー株式会社 蓄電装置

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