WO2018055935A1 - Dispositif d'excitation de charge - Google Patents

Dispositif d'excitation de charge Download PDF

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Publication number
WO2018055935A1
WO2018055935A1 PCT/JP2017/028798 JP2017028798W WO2018055935A1 WO 2018055935 A1 WO2018055935 A1 WO 2018055935A1 JP 2017028798 W JP2017028798 W JP 2017028798W WO 2018055935 A1 WO2018055935 A1 WO 2018055935A1
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Prior art keywords
voltage
wiring
threshold
driving device
switch element
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PCT/JP2017/028798
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English (en)
Japanese (ja)
Inventor
鳴 劉
山脇　大造
良介 石田
泰志 杉山
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日立オートモティブシステムズ株式会社
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Publication of WO2018055935A1 publication Critical patent/WO2018055935A1/fr

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/06—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider
    • H02M3/07—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider using capacitors charged and discharged alternately by semiconductor devices with control electrode, e.g. charge pumps
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/51—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used
    • H03K17/56—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices
    • H03K17/60—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being bipolar transistors
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/51—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used
    • H03K17/56—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices
    • H03K17/687—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being field-effect transistors
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/51—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used
    • H03K17/74—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of diodes
    • H03K17/76—Switching arrangements with several input- or output-terminals, e.g. multiplexers, distributors

Definitions

  • the present invention relates to a load driving device.
  • a battery power compensator that compensates for a battery mounted in a vehicle, a small ship, etc., whose voltage drops extremely due to a load change or the like is described in, for example, Japanese Patent Laid-Open No. 2000-60027 (Patent Document 1).
  • Patent Document 1 Japanese Patent Laid-Open No. 2004-133826 detects “a change in the input voltage to the load 11 in a device in which the battery 10 and the load 11 are coupled by the cable 13 and the compensation capacitor 12 is inserted on the input side of the load 11.
  • a voltage detection circuit 27 that compares the detected value with a reference value, a switch circuit 25 that is controlled by a comparison output, and an auxiliary capacitor 26 that is connected in parallel to the compensation capacitor 12 by the switch circuit 25.
  • Patent Document 1 Japanese Patent Laid-Open No. 2000-60027
  • a conventional load driving device equipped with an in-vehicle ECU uses a capacitor of several hundred ⁇ F (for example, the compensation capacitor 12 of Patent Document 1 described above).
  • FIG. 20 is an explanatory diagram of a conventional load driving device 1 equipped with an in-vehicle ECU.
  • FIG. 20A shows a block diagram of the load driving device 1.
  • Loads 2 and 3 such as a microcomputer and a sensor are driven at 5V and 3.3V, respectively. Since the voltage (BATT) of the battery 8 is as high as 13.5 V, the step-down power supply 4 and the input circuit 7 are installed between the battery 8 and the loads 2 and 3.
  • the step-down power supply 4 is a circuit that converts a high voltage into a low voltage.
  • the input circuit 7 includes a diode 5 (D) and an input capacitor 6 (C1). The role of the input circuit 7 is as follows.
  • the battery 8 is also connected to an inductive load 9 such as a solenoid and an injector.
  • an inductive load 9 such as a solenoid and an injector.
  • the diode 5 (D) is for preventing a current from flowing backward from the loads 2 and 3 to the BATT when the BATT is lowered.
  • the input capacitor 6 (C 1) is connected to the input terminal of the step-down power supply 4. This is because the loads 2 and 3 are driven by the energy stored in the input capacitor 6 (C1) during the BATT decrease period.
  • the discharge operation of the input capacitor 6 (C1) is shown in FIG.
  • the input capacitor 6 (C1) is discharged, and the input voltage (VB) of the step-down power supply 4 decreases from the initial voltage (VB_initial).
  • the lower limit (VB_min) of the input voltage (VB) of the step-down power supply 4 is the lower limit of the input voltage at which the step-down power supply 4 can generate 5V and 3.3V, and is determined by the maximum value of the load current and the power supply efficiency.
  • VB_initial is a differential voltage between the normal voltage (13.5 V) of BATT and the forward voltage (VD) of the diode 5 (D).
  • the capacitance value of the input capacitor 6 (C1) is determined by the maximum load current (Imax) of each of the loads 2 and 3, the efficiency (E) of the step-down power supply 4, and the maximum decrease period (Tmax) of BATT, and is obtained from the equation (1). It is done.
  • the required capacitance value of the input capacitor 6 (C1) is obtained using the following numerical value, it is about 440 uF.
  • VB_min 7V
  • VB_initial 12.5V
  • Imax 1A
  • Tmax 2ms
  • E 70%
  • Vo1 5V
  • Vo2 3.3V.
  • ECU1 packaging (1kg ECU) technology has been developed to reduce the cost of in-vehicle ECUs.
  • One challenge for this is the elimination of electrolytic capacitors. Since the electrolytic capacitor contains an electrolytic solution inside, the electrolytic solution evaporates when the resin is sealed at a high temperature for 1 pcg ECU. As a result, the function of the capacitor may be lost.
  • the electrolytic capacitor is simply replaced with a ceramic capacitor, the capacity per ceramic capacitor is smaller than that of the electrolytic capacitor, and thus a large number of capacitors must be arranged in parallel, increasing the mounting area of the 1 kgg ECU. For example, in the case of a ceramic capacitor with a withstand voltage of DC 50 V, the maximum capacitance value is only 10 uF. For this reason, it is necessary to reduce the capacitance value of the capacitor used in the ECU as much as possible.
  • An object of the present invention is to provide a load driving device having a load such as a microcomputer using a small-capacitance capacitor in an in-vehicle ECU.
  • the load when the battery voltage drops, the load is driven by the auxiliary capacitor having a voltage higher than the normal voltage of the battery voltage. Can be small. Problems, configurations, and effects other than those described above will be clarified by the following description of embodiments.
  • FIG. 1 is a block diagram showing the configuration of the load driving device 11 according to the first embodiment of the present invention.
  • the load driving device 11 includes an input circuit 41 and a step-down power supply 12.
  • the step-down power supply 12 is a circuit that converts a high voltage into a low voltage.
  • the difference between the step-down power supply 12 and the step-down power supply 4 shown in FIG. 20A is that the voltage range of the input voltage VB that can be input to the step-down power supply 12 is wider than that of the step-down power supply 4. (I.e., higher values of VB can be converted to desired voltages (eg, 5V and 3.3V) and applied to loads 2 and 3).
  • the input circuit 41 includes a diode 5 (D), a booster circuit 14, a Vbis monitor 18, a boost controller 17, an auxiliary capacitor 40 (Cbis), a capacitor 39 (C2), a VB monitor 15, a BATT monitor 19, a capacitor connection unit 13, and It is composed of a capacity connection controller 16.
  • the booster circuit 14 is a circuit that converts a low voltage into a high voltage.
  • the entire load driving device 11 is integrally resin-sealed.
  • FIG. 2 is an explanatory diagram showing an example of the booster circuit 14 according to the first embodiment of the present invention.
  • the booster circuit 14 is a Dickson type charge pump including, for example, diodes 60 to 62, boost capacitors 63 to 64, and a phase inverting circuit 65.
  • the booster circuit 14 is a circuit that boosts the voltage (BATT) of the battery 8 three times by a control signal (CP_C) and outputs the boosted voltage as an output voltage (Vbis).
  • the multiple of boosting can be adjusted by adjusting the number of diodes and boosting capacitors. The greater the number of diodes and boost capacitors, the higher the boost multiple.
  • the BATT monitor 19 is a circuit that determines the voltage level of the battery voltage (BATT) based on the threshold 2 and generates a determination signal (BATT_C).
  • FIG. 3 is an explanatory diagram showing an example of the circuit of the BATT monitor 19 according to the first embodiment of the present invention.
  • the BATT monitor 19 includes a comparator 26, an input terminal 27, an output terminal 29, and a reference voltage 28 (Vref1).
  • the BATT monitor 19 compares with the reference voltage 28 (Vref1).
  • the BATT monitor 19 When the battery voltage (BATT) drops below the reference voltage 28 (Vref1), the BATT monitor 19 When the determination signal (BATT_C) of “” is generated and rises from the reference voltage 28 (Vref1), the determination signal (BATT_C) of “H” is generated, and the generated determination signal (BATT_C) is output from the output terminal 29.
  • the reference voltage 28 (Vref1) is a threshold value 2.
  • the VB monitor 15 is a circuit that determines the voltage level of the input voltage (VB) of the step-down power supply 12 based on the threshold 1 and generates a determination signal (VB_C).
  • FIG. 4 is an explanatory diagram illustrating an example of a circuit of the VB monitor 15 according to the first embodiment of this invention.
  • the VB monitor 15 includes a comparator 31, an input terminal 30, an output terminal 33, and a reference voltage 32 (Vref2).
  • the VB monitor 15 compares with the reference voltage 32 (Vref2), and when the input voltage (VB) falls below the reference voltage 32 (Vref2),
  • the determination signal (VB_C) of “L” is generated and rises from the reference voltage 32 (Vref2)
  • the determination signal (VB_C) of “H” is generated and the generated determination signal (VB_C) is output from the output terminal 33.
  • the reference voltage 32 (Vref2) is a threshold value 1.
  • the Vbis monitor 18 is a circuit that determines the voltage level of the output voltage (Vbis) of the booster circuit 14 based on the threshold 3 and the threshold 4, and generates a determination signal (Vbis_C).
  • FIG. 5 is an explanatory diagram showing an example of the circuit of the Vbis monitor 18 according to the first embodiment of the present invention.
  • the Vbis monitor 18 includes a resistor 23 (R1), a resistor 24 (R2), a hysteresis controller 22, an input terminal 20, an output terminal 21, and a reference voltage 25 (Vref3).
  • the Vbis monitor 18 compares the threshold voltage 3 and 4 when the output voltage (Vbis) of the booster circuit 14 is input to the input terminal 20. When the output voltage (Vbis) rises above the threshold 3, the Vbis monitor signal 18 When (Vbis_C) is generated and falls below the threshold 4, a determination signal (Vbis_C) of “H” is generated, and the generated determination signal (Vbis_C) is output from the output terminal 21.
  • the thresholds 3 and 4 can be adjusted by the resistor 23 (R1), the resistor 24 (R2), and the reference voltage 25 (Vref3).
  • the boost controller 17 controls the start or stop of the boost operation of the booster circuit 14 based on the determination signal (BATT_C) from the BATT monitor 19, and the booster circuit 14 determines whether the booster circuit 14 detects the booster circuit 14 based on the determination signal (Vbis_C) from the Vbis monitor 18.
  • This circuit generates a control signal (CP_C) for controlling the voltage level of the output voltage (Vbis).
  • FIG. 6 is an explanatory diagram showing an example of the boost controller 17 according to the first embodiment of the present invention.
  • the boost controller 17 includes an input terminal 43, an input terminal 44, an output terminal 45, and a logical product 42.
  • the boost controller 17 receives the determination signal (BATT_C) from the BATT monitor 19 at the input terminal 43, and receives the determination signal (Vbis_C) from the Vbis monitor 18 at the input terminal 44 of the boost controller 17.
  • BATT_C determination signal
  • Vbis_C determination signal
  • the control signal (CP_C) is generated so that the voltage range is up to the threshold value 4, and the generated control signal (CP_C) is output from the output terminal 45.
  • the boost controller 17 when the determination signal (BATT_C) is “L”, the boost controller 17 generates a control signal (CP_C) so as to stop the boosting operation of the booster circuit 14 and outputs it from the output terminal 45.
  • the capacity connecting unit 13 is a circuit that connects or disconnects the auxiliary capacitor 40 (Cbis) and the capacitor 39 (C2) in parallel.
  • the capacity connection controller 16 uses a determination signal (VB_C) from the VB monitor 15 and a determination signal (BATT_C) from the BATT monitor 19 to provide a control signal (SW_C) for controlling connection or disconnection of the capacity connection unit 13. This is a circuit to be generated.
  • FIG. 7 is an explanatory diagram showing an example of the capacity connection controller 16 according to the first embodiment of the present invention.
  • the capacity connection controller 16 includes an input terminal 34, an input terminal 35, an output terminal 38, a negative logical product 36, a negative logical product 37, and a logical negative 46.
  • a determination signal (VB_C) from the VB monitor 15 is input to the input terminal 34, and a determination signal (BATT_C) from the BATT monitor 19 is input to the input terminal 35.
  • the capacity connection controller 16 generates an “H” control signal (SW_C) based on the falling edge of the determination signal (VB_C) from the VB monitor 15 and outputs it from the output terminal 38.
  • the capacity connection controller 16 generates an “L” control signal (SW_C) in response to the rising edge of the determination signal (BATT_C) from the BATT monitor 19 and outputs the control signal from the output terminal 38.
  • the output terminal 38 is connected to the capacitor connection unit 13.
  • the capacitor connection unit 13 When the “H” control signal (SW_C) is input from the output terminal 38, the capacitor connection unit 13 is connected, and the auxiliary capacitor 40 (Cbis) and the capacitor 39 (C2) are connected in parallel.
  • the “L” control signal (SW_C) is input, the capacitance connecting unit 13 is cut off, and the connection between the auxiliary capacitor 40 (Cbis) and the capacitor 39 (C2) is cut off.
  • the auxiliary capacitor 40 (Cbis) is a capacitor for storing energy for driving the loads 2 and 3 when the voltage (BATT) of the battery 8 is lowered.
  • the capacitor 39 (C2) is a capacitor for reducing noise such as switching noise.
  • the input circuit 41 has the following role.
  • auxiliary capacitor 40 (Cbis) having a voltage (Vbis) higher than the normal voltage of the voltage (BATT) of the battery 8 drives the loads 2 and 3 when the voltage (BATT) of the battery 8 decreases.
  • the total capacitance value of the capacitor 40 (Cbis) and the capacitor 39 (C2) can be made smaller than that of the conventional input capacitor 6 (C1).
  • the operation mode of the input circuit 41 is set to any one of the three listed in Table 1 below.
  • FIG. 8 is a timing chart showing the operation of the load driving device 11 according to the first embodiment of the present invention.
  • FIG. 9 is a flowchart showing the operation of the load driving device 11 according to the first embodiment of the present invention.
  • the normal mode is set. It continues (S901).
  • the input voltage (VB) has not dropped below the threshold 1 (S902: No)
  • the voltage (BATT) of the battery 8 exceeds the threshold 2 (S908: Yes)
  • the voltage (Vbis) of the auxiliary capacitor 40 (Cbis) ) Exceeds the threshold 3 (S909: Yes)
  • the input circuit 41 is set to the Cbis charge mode (S906).
  • the input voltage (VB) has not dropped below the threshold 1 (S902: No), the voltage (BATT) of the battery 8 exceeds the threshold 2 (S908: Yes), and the voltage (Vbis) of the auxiliary capacitor 40 (Cbis) ) Does not exceed the threshold 3 (S909: No), the normal mode is continued (S901).
  • Threshold values 1 to 4 are set as shown in Table 2 below. In the example of FIG. 8, the threshold values 1 to 4 are set to 7V, 7.5V, 30V, and 32V, respectively.
  • the total capacitance value of the auxiliary capacitor 40 (Cbis) and the capacitor 39 (C2) can be made smaller than that of the conventional input capacitor 6 (C1).
  • the threshold value 4 is desirably a value equal to or greater than the value of Vbis that satisfies Cbis ⁇ Vbis> C2 ⁇ VB.
  • ceramic capacitors are employed as the auxiliary capacitor 40 (Cbis) and the capacitor 39 (C2), and the entire load driving device 11 (or the entire ECU including the load driving device 11) is resin-sealed into one package. Therefore, cost reduction can be realized.
  • the capacitor connection 13 of the input circuit 41 of the load driving device 11 may use a MOSFET (Metal Oxide Semiconductor Field Effect Transistor) or a bipolar transistor, or a circuit having a step-down function. .
  • MOSFET Metal Oxide Semiconductor Field Effect Transistor
  • a bipolar transistor or a circuit having a step-down function.
  • connection and disconnection between the auxiliary capacitor 40 (Cbis) to which a sufficient voltage satisfying the above conditions is applied and the capacitor 39 (C2) can be switched as necessary.
  • the capacitor connecting portion 13 is, for example, a MOSFET
  • the electric charge stored in the auxiliary capacitor 40 (Cbis) passes through the capacitor connecting portion 13 and the capacitor 39 (C2 )
  • VB rises more than the normal value for example, about 12V.
  • the capacitor connection unit 13 includes a circuit having a step-down function
  • the capacitor connection is made by stepping down Vbis, which is significantly higher than the normal value of VB, to a desired voltage (for example, a voltage comparable to the normal VB).
  • Vbis which is significantly higher than the normal value of VB
  • a desired voltage for example, a voltage comparable to the normal VB
  • Example 2 of the present invention will be described. Except for the differences described below, each part of the system of the second embodiment has the same function as each part denoted by the same reference numeral in the first embodiment shown in FIGS. Is omitted.
  • Example 2 was proposed in order to simplify the control circuit and use the step-down power supply 4 as it is.
  • FIG. 10 is a block diagram showing the configuration of the load driving device 49 according to the second embodiment of the present invention. 10, 1, and 20 are assigned the same reference numerals.
  • the battery 8, the load 2 and the load 3 of the second embodiment are the same as those shown in FIG. 1, and the step-down power supply 4 is the same as that shown in FIG.
  • the load driving device 49 includes an input circuit 48 and a step-down power supply 4.
  • the diode 5 (D) and the capacitor C2 of the input circuit 48 are the same as those shown in FIG.
  • the input circuit 48 includes a diode 5 (D), a booster circuit 50, a Vbis monitor 52, a boost controller 53, a capacitor 51 (Cbis1), a capacitor 39 (C2), a BATT monitor 54, and a diode 47.
  • the booster circuit 50 is a circuit that converts a low voltage into a high voltage.
  • the difference between the booster circuit 50 and the booster circuit 14 of FIG. 1 is that the booster circuit 50 can generate a positive output voltage Vbis from a negative input voltage BATT.
  • the BATT monitor 54 is a circuit that determines the voltage level of the battery voltage (BATT) based on the threshold 5 and generates a determination signal (BATT1_C). The difference between the BATT monitor 54 and the BATT monitor 19 of FIG. 1 is that the BATT monitor 54 can detect that the BATT voltage becomes negative.
  • the Vbis monitor 52 is a circuit that determines the voltage level of the output voltage (Vbis) of the booster circuit 50 based on the threshold 6 and the threshold 7, and generates a determination signal (Vbis1_C).
  • Vbis the voltage level of the output voltage
  • Vbis1_C the determination signal
  • the step-up controller 53 controls starting or stopping the step-up operation of the step-up circuit 50 based on the determination signal (BATT1_C) from the BATT monitor 54, and the step-up controller 53 controls the step-up operation of the step-up circuit 50 based on the determination signal (Vbis1_C) from the Vbis monitor 52.
  • This circuit generates a control signal (CP1_C) for controlling the voltage level of the output voltage (Vbis).
  • the capacitor 51 (Cbis1) is a capacitor for smoothing the output voltage Vbis of the booster circuit 50 when the voltage (BATT) of the battery 8 drops to a negative voltage.
  • the entire load driving device 49 is integrally resin-sealed.
  • the input circuit 48 has the following role.
  • the booster circuit 50 When the voltage (BATT) of the battery 8 drops to a negative voltage, the booster circuit 50 performs a boost operation, generates a minimum voltage level (Vbis) at which at least the step-down power supply 4 can operate, and passes through the capacitor 51 (Cbis1) To drive loads 2 and 3. For this reason, the voltage Vbis of the capacitor 51 (Cbis1) can be made lower than the voltage Vbis of the capacitor 40 (Cbis) of the first embodiment, and the conventional step-down power supply 4 can be used as it is. Further, since the capacitor 51 (Cbis1) is a capacitor for smoothing the output voltage Vbis of the booster circuit 50, the total capacitance value of the capacitor 51 (Cbis1) and the capacitor 39 (C2) is set to the conventional input capacitor 6 (C1). It can be made smaller.
  • the operation mode of the input circuit 48 is set to one of the two listed in Table 3 below.
  • FIG. 11 is a timing chart showing the operation of the load driving device 49 according to the second embodiment of the present invention.
  • FIG. 12 is a flowchart showing the operation of the load driving device 49 according to the second embodiment of the present invention.
  • Boost mode In the normal mode (S1201), when the voltage (BATT) of the battery 8 falls below the threshold 5 (S1202: Yes), the boost mode is entered (S1203).
  • the capacitor 39 (C2) drives the loads 2 and 3, so that the input voltage (VB) of the step-down power supply 4 is lowered by the discharge of the capacitor 39 (C2).
  • the loads 2 and 3 are driven from the capacitor 51 (Cbis1) via the diode 47.
  • the boost controller 53 includes the boost circuit 50.
  • the control signal (CP1_C) for starting the boosting operation is output to the booster circuit 50, and the booster circuit 50 starts boosting accordingly.
  • the booster circuit 50 stops the boosting.
  • Threshold values 5-7 are set as shown in Table 4 below. In the example of FIG. 11, the threshold values 5 to 7 are set to 0V, 7V, and 7.5V, respectively.
  • the booster circuit 50 performs a boost operation, and at least the step-down power supply 4 Generates the minimum voltage level (Vbis) that can operate, and drives the loads 2 and 3 via the capacitor 51 (Cbis1). For this reason, the voltage Vbis of the capacitor 51 (Cbis1) can be made lower than the voltage Vbis of the capacitor 40 (Cbis) of the first embodiment, and the conventional step-down power supply 4 can be used as it is.
  • the capacitor 51 (Cbis1) is a capacitor for smoothing the output voltage Vbis of the booster circuit 50
  • the total capacitance value of the capacitor 51 (Cbis1) and the capacitor 39 (C2) is set to the conventional input capacitor 6 (C1). It can be made smaller.
  • Example 3 of the present invention will be described. Except for the differences described below, each part of the load driving device of the third embodiment has the same function as the parts denoted by the same reference numerals in the first and second embodiments shown in FIGS. These descriptions are omitted.
  • Embodiments 1 and 2 can be applied only when the voltage (BATT) of the battery 8 drops to a negative voltage.
  • the application of the third embodiment is applied. is necessary.
  • FIG. 13 is a block diagram showing the configuration of the load driving device 57 according to the third embodiment of the present invention.
  • FIG. 13 FIG. 1, and FIG.
  • the load driving device 57 includes an input circuit 56 and a step-down power supply 12.
  • the input circuit 56 includes a booster circuit 14, a Vbis monitor 18, a boost controller 17, an auxiliary capacitor 40 (Cbis), a capacitor 39 (C2), a VB monitor 15, a BATT monitor 19, a capacitor connection unit 13, a capacitor connection controller 16, It is composed of a Vbis monitor 2_59, a boost controller 2_58, and a booster circuit 2_55.
  • the boost circuit 14, Vbis monitor 18, boost controller 17, auxiliary capacitor 40 (Cbis), capacitor 39 (C 2), VB monitor 15, BATT monitor 19, capacitor connection unit 13, and capacitor connection controller 16 of the input circuit 56 are Since it is the same as that shown in FIG.
  • the Vbis monitor 2_59 is a circuit that determines the voltage level of the output voltage (Vbis) of the booster circuit 14 based on the threshold 8 and generates a determination signal (Vbis_C2).
  • Booster circuit 2_55 is a circuit that converts a low voltage into a high voltage.
  • the difference between the booster circuit 14 and the booster circuit 2_55 is that the current drive capability of the booster circuit 2_55 is higher than the booster circuit 14 (that is, the current supply capability is higher).
  • the booster circuit 2 (55) is an inductor type
  • the booster circuit 14 is a charge pump type.
  • the booster circuit 2_55 can drive the loads 2 and 3 via the step-down power supply 12 while the voltage (BATT) of the battery 8 is falling within a positive value range.
  • the entire load driving device 57 is integrally resin-sealed.
  • FIG. 14 is an explanatory diagram showing an example of a booster circuit 2_55 according to the third embodiment of the present invention.
  • FIG. 14 shows an inductor type booster circuit as an example.
  • the booster circuit 2_55 includes an inductor 66, a diode 5, and a MOS transistor 67 (SW3).
  • the booster circuit 2_55 is a circuit that boosts the voltage (BATT) of the battery by the control signal (Boost_C) and outputs it as an output voltage (VB).
  • the multiple of the boost can be adjusted by the ratio of the high and low periods of the control signal (Boost_C). The longer the high period of the control signal (Boost_C), the higher the boost multiple.
  • the boosting controller 2_58 controls the boosting operation of the boosting circuit 2_55 to be short-circuited (through) by the determination signal (BATT_C) from the BATT monitor 19 and controls the determination signal (from the Vbis monitor 2_59).
  • Vbis_C2 is a circuit that controls the start of the boosting operation of the boosting circuit 2_55.
  • the input circuit 56 has the following role.
  • the auxiliary capacitor 40 (Cbis) having a voltage (Vbis) higher than the normal voltage of the voltage (BATT) of the battery 8 drives the loads 2 and 3. Therefore, the total capacitance value of the auxiliary capacitor 40 (Cbis) and the capacitor 39 (C2) can be made smaller than that of the conventional input capacitor 6 (C1).
  • the booster circuit 2 boosts the voltage so that the step-down power supply 12 can operate at the lowest voltage (VB). .
  • the operation mode of the input circuit 56 is set to one of the four listed in Table 5 below.
  • a boost 2 mode was added to the same three modes as in the first embodiment.
  • FIG. 15 is a timing chart showing the operation of the load driving device 57 according to the third embodiment of the present invention.
  • FIG. 16 is a flowchart showing the operation of the load driving device 57 according to the third embodiment of the present invention.
  • the operation related to the boost 2 mode of the input circuit 56 will be described. Since other modes are the same as those in the first embodiment, description thereof is omitted. That is, the transition from the normal mode to the Cbis discharge mode and the transition from the Cbis charge mode to the normal mode are the same as in the first embodiment. Further, when the voltage (BATT) of the battery 8 decreases to a negative voltage, the load driving device 57 operates in the same manner as the load driving device 11 of the first embodiment.
  • ⁇ Cbis discharge mode ⁇ Boost 2 mode In the Cbis discharge mode (S903), when the Vbis monitor 2_59 detects that the voltage (Vbis) of the auxiliary capacitor 40 (Cbis) has dropped below the threshold value 8 (S1601: Yes), the input circuit 41 is set to the boost 2 mode. (S1602). In other words, the capacitor connection portion 13 is connected, and the booster circuit 2_55 boosts the voltage.
  • the battery 8 (BATT) drives the loads 2 and 3 via the booster circuit 2_55.
  • -Boost 2 mode-> Cbis charge mode When the Vbis monitor 18 and the BATT monitor 19 detect that the voltage (Vbis) of the auxiliary capacitor 40 (Cbis) is lower than the threshold value 3 and the voltage of the battery 8 (BATT) is higher than the threshold value 2 (S1603: Yes).
  • the input circuit 41 is set to the Cbis charge mode (S1604). That is, the capacity connecting unit 13 is cut off, and the voltage (Vbis) of the auxiliary capacitor 40 (Cbis) is boosted by the booster circuit 14 while the battery 8 (BATT) drives the loads 2 and 3.
  • the Vbis monitor 18 detects that the voltage (Vbis) of the auxiliary capacitor 40 (Cbis) has risen above the threshold 4 (S1605: Yes)
  • the input circuit 41 is set to the normal mode (S901). This process is the same as S907 in the first embodiment.
  • Threshold 8 is set as described in Table 6 below. Since the threshold values 1 to 4 are the same as those in the first embodiment, description thereof is omitted. In the example of FIG. 15, the threshold value 8 is set to 10.5V.
  • Example 3 when Example 3 is applied, it is possible to deal with two types of states, that is, a state where the voltage (BATT) of the battery 8 is reduced to a negative voltage and a state where the voltage is reduced to a positive voltage lower than usual.
  • each part of the load driving device according to the fourth embodiment has the same function as the parts denoted by the same reference numerals as those of the first to third embodiments shown in FIGS. These descriptions are omitted.
  • the booster circuit 14 and the booster circuit 2_55 are necessary.
  • the fourth embodiment is proposed in which the booster circuit 14 and the booster circuit 2_55 are integrated into one booster circuit.
  • FIG. 17 is a block diagram showing the configuration of the load driving device 68 according to the fourth embodiment of the present invention. 17, 13, 1, and 20 are assigned the same reference numerals.
  • the load driving device 68 includes an input circuit 69 and a step-down power supply 12.
  • the input circuit 69 includes a booster circuit 2_55, a Vbis monitor 18, a boost controller 72, an auxiliary capacitor 40 (Cbis), a capacitor 39 (C2), a VB monitor 15, a BATT monitor 19, a Vbis monitor 2_59, a MOS transistor 70 (SW1), And a MOS transistor 71 (SW2).
  • the booster circuit 2_55, the Vbis monitor 18, the auxiliary capacitor 40 (Cbis), the capacitor 39 (C2), the VB monitor 15, the BATT monitor 19 and the Vbis monitor 2_59 of the input circuit 69 are the same as those in FIG. .
  • the MOS transistor 70 (SW1) is a switch for selecting a connection destination of the input voltage (VB) of the step-down power supply 12.
  • the MOS transistor 71 is a switch for selecting a connection destination of the auxiliary capacitor 40 (Cbis).
  • the step-up controller 72 includes a determination signal (Vbis_C) from the Vbis monitor (18), a determination signal (Vbis_C2) from the Vbis monitor 2 (59), a determination signal (BATT_C) from the BATT monitor 19, and a signal from the VB monitor 15 This is a circuit for controlling the operation mode of the input circuit 69 by the determination signal (VB_C).
  • the entire load driving device 68 is integrally resin-sealed.
  • the role of the input circuit 69 is the same as that of the input circuit 56 of the third embodiment. In order to realize these roles, the operation mode of the input circuit 69 is set to any of the four listed in Table 7 below.
  • FIG. 18 is a timing chart showing the operation of the load driving device 68 according to the fourth embodiment of the present invention.
  • FIG. 19 is a flowchart showing the operation of the load driving device 68 according to the fourth embodiment of the present invention.
  • ⁇ Cbis discharge mode ⁇ Boost 3 mode When the Vbis monitor 2_59 detects that the voltage (Vbis) of the auxiliary capacitor 40 (Cbis) has dropped below the threshold value 8 (S2004: Yes), the input circuit 69 is set to the boost 3 mode (S2005). That is, the booster circuit 2_55 boosts the voltage (BATT) of the battery 8 so that VB and Vbis have the same voltage. The voltage (BATT) of the battery 8 drives the loads 2 and 3 via the booster circuit 2_55.
  • Boost 3 mode ⁇ Boost 4 mode: When the Vbis monitor 18 and the BATT monitor 19 detect that the voltage (Vbis) of the auxiliary capacitor 40 (Cbis) is lower than the threshold 3 and the voltage of the battery 8 (BATT) is higher than the threshold 2 (S2006: Yes).
  • the input circuit 69 is set to the boost 4 mode (S2007). That is, while the battery 8 (BATT) drives the loads 2 and 3, the booster circuit 2_55 boosts the voltage (Vbis) of the auxiliary capacitor 40 (Cbis).
  • ⁇ Cbis discharge mode ⁇ Boost 4 mode When the voltage (Vbis) of the auxiliary capacitor 40 (Cbis) is not lower than the threshold value 8 (S2004: No), the voltage (Vbis) of the auxiliary capacitor 40 (Cbis) is lower than the threshold value 3, and the battery When the Vbis monitor 18 and the BATT monitor 19 detect that the voltage 8 (BATT) has risen above the threshold 2 (S2009: Yes and S2010: Yes), the input circuit 69 is set to the boost 4 mode. That is, while the battery 8 (BATT) drives the loads 2 and 3, the booster circuit 2_55 boosts the voltage (Vbis) of the auxiliary capacitor 40 (Cbis).
  • the threshold value of the fourth embodiment is the same as that of the third embodiment, and thus the description thereof is omitted.
  • Example 4 when Example 4 is applied, there are two types of states: a state where the voltage (BATT) of the battery 8 is reduced to a negative voltage and a state where the voltage is reduced to a positive voltage lower than normal by a single booster circuit. It can correspond to.
  • this invention is not limited to the above-mentioned Example, Various modifications are included.
  • the above-described embodiments have been described in detail for better understanding of the present invention, and are not necessarily limited to those having all the configurations described.
  • a part of the configuration of one embodiment can be replaced with the configuration of another embodiment, and the configuration of another embodiment can be added to the configuration of one embodiment.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Electronic Switches (AREA)
  • Dc-Dc Converters (AREA)
  • Charge And Discharge Circuits For Batteries Or The Like (AREA)

Abstract

Ce dispositif d'excitation de charge comprend : un premier condensateur relié à un premier câblage; un second condensateur relié à un second câblage; un premier circuit survolteur qui est connecté à une alimentation électrique qui charge le premier condensateur, et qui génère, en amplifiant la tension de l'alimentation électrique, une tension à appliquer au second câblage; et une unité de raccordement pour faire passer un courant du second câblage au premier câblage dans les cas où la tension du premier câblage est réduite.
PCT/JP2017/028798 2016-09-21 2017-08-08 Dispositif d'excitation de charge WO2018055935A1 (fr)

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JP2016-184686 2016-09-21
JP2016184686A JP6654535B2 (ja) 2016-09-21 2016-09-21 負荷駆動装置

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WO2018055935A1 true WO2018055935A1 (fr) 2018-03-29

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JP7077976B2 (ja) * 2019-01-23 2022-05-31 トヨタ自動車株式会社 電源回路

Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2001508612A (ja) * 1997-01-03 2001-06-26 テレフオンアクチーボラゲツト エル エム エリクソン ドライバー回路およびドライバー動作方法
JP2007174744A (ja) * 2005-12-19 2007-07-05 Matsushita Electric Ind Co Ltd チャージポンプ回路及び電源装置
JP2007244109A (ja) * 2006-03-09 2007-09-20 Toshiba Corp 定電圧回路
JP2008035588A (ja) * 2006-07-26 2008-02-14 Fanuc Ltd モータ駆動装置
JP2013192388A (ja) * 2012-03-14 2013-09-26 Ntt Facilities Inc 組電池の放電制御システムおよび放電制御方法
JP2016092958A (ja) * 2014-11-04 2016-05-23 株式会社デンソー 電源回路装置

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* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
FR2832262A1 (fr) * 2001-11-09 2003-05-16 France Telecom Procede et dispositif d'alimentation en energie electrique d'un appareil

Patent Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2001508612A (ja) * 1997-01-03 2001-06-26 テレフオンアクチーボラゲツト エル エム エリクソン ドライバー回路およびドライバー動作方法
JP2007174744A (ja) * 2005-12-19 2007-07-05 Matsushita Electric Ind Co Ltd チャージポンプ回路及び電源装置
JP2007244109A (ja) * 2006-03-09 2007-09-20 Toshiba Corp 定電圧回路
JP2008035588A (ja) * 2006-07-26 2008-02-14 Fanuc Ltd モータ駆動装置
JP2013192388A (ja) * 2012-03-14 2013-09-26 Ntt Facilities Inc 組電池の放電制御システムおよび放電制御方法
JP2016092958A (ja) * 2014-11-04 2016-05-23 株式会社デンソー 電源回路装置

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