WO2017077939A1 - 電力変換装置 - Google Patents
電力変換装置 Download PDFInfo
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- WO2017077939A1 WO2017077939A1 PCT/JP2016/081892 JP2016081892W WO2017077939A1 WO 2017077939 A1 WO2017077939 A1 WO 2017077939A1 JP 2016081892 W JP2016081892 W JP 2016081892W WO 2017077939 A1 WO2017077939 A1 WO 2017077939A1
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- voltage
- common mode
- power
- conversion device
- mode voltage
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- 238000006243 chemical reaction Methods 0.000 title claims abstract description 15
- 239000004065 semiconductor Substances 0.000 claims abstract description 16
- 238000001514 detection method Methods 0.000 claims abstract description 7
- 239000003990 capacitor Substances 0.000 claims description 29
- 238000004804 winding Methods 0.000 claims description 7
- 230000003321 amplification Effects 0.000 claims description 5
- 238000003199 nucleic acid amplification method Methods 0.000 claims description 5
- 230000001629 suppression Effects 0.000 description 21
- 238000010586 diagram Methods 0.000 description 12
- 230000005284 excitation Effects 0.000 description 11
- 230000006698 induction Effects 0.000 description 10
- 238000000034 method Methods 0.000 description 10
- 238000004458 analytical method Methods 0.000 description 4
- 230000002238 attenuated effect Effects 0.000 description 3
- 230000000295 complement effect Effects 0.000 description 2
- 230000007935 neutral effect Effects 0.000 description 2
- 239000002131 composite material Substances 0.000 description 1
- 239000011162 core material Substances 0.000 description 1
- 238000007599 discharging Methods 0.000 description 1
- 238000012986 modification Methods 0.000 description 1
- 230000004048 modification Effects 0.000 description 1
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Classifications
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/12—Arrangements for reducing harmonics from ac input or output
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/12—Arrangements for reducing harmonics from ac input or output
- H02M1/123—Suppression of common mode voltage or current
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/4815—Resonant converters
- H02M7/4818—Resonant converters with means for adaptation of resonance frequency, e.g. by modification of capacitance or inductance of resonance circuits
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/4826—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode operating from a resonant DC source, i.e. the DC input voltage varies periodically, e.g. resonant DC-link inverters
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
- H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
- H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
- H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/4815—Resonant converters
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Definitions
- the present invention relates to a power conversion apparatus, for example, a method for canceling a common mode voltage generated when power conversion is performed based on a switching operation of a power semiconductor element represented by an inverter.
- the carrier frequency of the voltage-type PWM inverter has been increased with the expansion of the application range and the improvement of the characteristics of power semiconductor elements. ing.
- the cause of electromagnetic interference generated by the voltage-type PWM inverter is mainly the current flowing through the ground line.
- Japanese Patent Application Laid-Open No. 10-94244 proposes a method of reducing the leakage current by suppressing the output common mode voltage of the inverter using an active element.
- the present invention has been made to solve the above problems, and an object of the present invention is to provide a power converter that can be reduced in size by reducing the circuit scale.
- a power conversion device that performs power conversion by switching a power semiconductor element according to an aspect of the present invention, the voltage detection means detecting a common mode voltage generated during the switching operation of the power semiconductor element, and the voltage detection means A voltage control power source that generates a reverse polarity voltage having the same magnitude as the common mode voltage by a circuit that amplifies the common mode voltage detected by the power supply, and superimposing the voltage generated from the voltage control power source on the output of the power converter Voltage superimposing means for canceling a common mode voltage equal to or higher than a switching frequency generated when the power semiconductor element is switched.
- the voltage superimposing means includes a common mode transformer having multiple windings and a capacitor.
- the resonance frequency based on the common mode transformer and the capacitor of the voltage superimposing means is set between the zero-phase voltage frequency and the switching frequency of the power semiconductor element.
- the power converter further includes a power converter superimposed by the voltage superimposing means and a residual voltage detecting means for detecting a common mode voltage of the voltage controlled power source.
- the voltage superimposing unit adds the common mode voltage detected by the residual voltage detecting unit and superimposes the common mode voltage on the output of the power converter.
- it further includes an operational amplifier that performs inversion amplification based on a comparison between the common mode voltage detected by the residual voltage detection means and the zero-phase voltage of the common mode voltage, and adjusts the voltage to be added.
- an operational amplifier that performs inversion amplification based on a comparison between the common mode voltage detected by the residual voltage detection means and the zero-phase voltage of the common mode voltage, and adjusts the voltage to be added.
- the power converter of the present invention can be reduced in size by reducing the circuit scale.
- FIG. 10 is a circuit configuration diagram around a voltage control power supply A # of a common mode suppression circuit 7 # based on the second embodiment. It is a figure explaining the equivalent circuit of voltage control power supply A # periphery of the common mode suppression circuit 7 # based on Embodiment 2. FIG. It is a figure explaining the equivalent circuit with respect to the common mode of the common mode suppression circuit 7 # based on Embodiment 2.
- FIG. 10 is a circuit configuration diagram around a voltage control power supply A # of a common mode suppression circuit 7 # based on the second embodiment. It is a figure explaining the equivalent circuit of voltage control power supply A # periphery of the common mode suppression circuit 7 # based on Embodiment 2.
- FIG. It is a figure explaining the equivalent circuit with respect to the common mode of the common mode suppression circuit 7 # based on Embodiment 2.
- FIG. FIG. 10 is a circuit configuration diagram around a voltage control power supply A # of a common mode suppression circuit 7 # based on the second embodiment. It is a figure explaining
- FIG. 10 is another circuit configuration diagram around the voltage controlled power source A #. It is a figure explaining a common mode voltage waveform. It is a figure explaining the FFT analysis result of a common mode voltage. It is a figure explaining the attenuation amount of a common mode voltage.
- FIG. 1 is a diagram illustrating a configuration of a motor control system 1 based on the first embodiment.
- a motor control system 1 includes an induction motor 6 and a power converter 2 of the present invention.
- the power conversion device 2 includes a voltage-type PWM inverter 4 and a common mode suppression circuit 7 that suppresses the common mode voltage.
- a voltage-type PWM inverter 4 (also simply referred to as an inverter) is connected to a DC power source 3 and converts this DC voltage into a three-phase AC voltage by a switching operation of a power semiconductor element (IGBT, SiC, etc.).
- a power semiconductor element IGBT, SiC, etc.
- the AC voltage converted by the inverter 4 is connected to an induction motor (motor) 6 via a three-phase cable 5, and the frame of the induction motor 6 is connected to the ground voltage GND via a ground wire.
- a common mode suppression circuit 7 is provided between the inverter 4 and the induction motor (motor) 6.
- the common mode suppression circuit 7 uses a capacitor group 8 that is star-connected to the three-phase AC output terminal of the inverter 4 and detects a common mode voltage, and a complementary transistor that amplifies the common mode voltage obtained from its neutral point.
- Push-pull type emitter follower circuit 9 the output of the emitter follower circuit 9 is input to the primary side coil, and the secondary side coil is provided in the three-phase cable 5.
- a capacitor 10 connected in series with the primary side coil.
- the common mode suppression circuit 7 is connected to the DC power source 3 on the input side of the inverter 4 as a driving power source.
- the emitter follower circuit 9 includes bipolar transistors Tr1 and Tr2 that are connected in series with the DC power source 3 and whose gates are connected to the capacitor group 8, respectively.
- the emitter follower circuit 9 has high-speed response capable of faithfully outputting the common mode voltage of the inverter 4 and low output impedance characteristics.
- the emitter follower circuit 9 realizes a voltage control power source that amplifies the detected common mode voltage and generates a reverse polarity voltage having the same magnitude as the common mode voltage.
- capacitors in the capacitor group 8 are desirably capacitors having the same level as the output capacity of the power semiconductor element of the inverter 4.
- the emitter follower circuit 9 Since the emitter follower circuit 9 has a sufficiently high input impedance, the common mode voltage of the inverter 4 can be detected with sufficient accuracy even if a capacitor having a small capacity is used.
- the excitation current Im of the common mode transformer 11 is supplied only from the emitter follower circuit 9.
- the winding ratio of the primary side and secondary side windings of the common mode transformer 11 is 1: 1. used.
- FIG. 2 is a diagram illustrating an equivalent circuit for the common mode of the common mode suppression circuit 7 according to the first embodiment.
- the capacitance C represents the stray capacitance between the motor winding and the frame
- the inductance L represents the inductance of the wiring of the entire path
- the resistance R represents the resistance component of the wiring of the entire path.
- a transformer having an excitation inductance Lm and a winding ratio of 1: 1 is a common mode transformer 11 in which leakage inductance is ignored.
- the emitter follower circuit 9 can be represented by a voltage control power supply A that receives a common mode voltage Vinv and outputs a voltage Vc having the same magnitude.
- the voltage Vinv is the common mode voltage of the inverter output.
- the current Im is an excitation current of the common mode transformer.
- the current Ic is a common mode current flowing through the motor.
- the voltage Vo is a common mode voltage after the common mode voltage is suppressed.
- the common mode transformer 11 connected to the output terminal of the emitter follower circuit 9 is expressed only by the excitation inductance Lm ignoring the leakage inductance. Further, the capacitance C4 of the capacitor 10 is shown.
- the common mode current IC flows to the ground line through the stray capacitance between the winding of the induction motor (motor) 6 and the frame.
- the common mode voltage Vinv includes a zero-phase voltage component Vlow and a voltage Vhi having a component higher than the switching frequency.
- the value of the capacitance C4 of the capacitor 10 is set so that the resonance frequency of the excitation inductance Lm and the capacitance C4 is between the zero-phase voltage frequency and the switching frequency.
- Vt Vhi (Formula 1)
- Vt Vhi (Formula 1)
- Vcap Vlow (Formula 2)
- Vinv of the inverter output is expressed by the following equation 3.
- Vinv Vc (Formula 3)
- Vcap satisfies the relationship of the following expression 4.
- Vcap Vc-Vt (Formula 4) Furthermore, the common mode voltage satisfies the relationship of the following formula 5.
- Vo Vinv-Vt (Formula 5) Based on Equation 2, Equation 4, and Equation 5, the following relationship is established.
- the common mode voltage of the inverter output includes a low-frequency zero-phase voltage component.
- the low-frequency zero-phase voltage component hardly affects electromagnetic interference.
- the configuration based on the first embodiment only the component having the switching frequency or higher is applied to the common mode transformer 11 to cancel the common mode voltage having the switching frequency or higher. Therefore, electromagnetic interference generated by the voltage-type PWM inverter in the high frequency band can be suppressed.
- the structure based on this Embodiment 1 is a structure which applies only the component more than a switching frequency to the common mode transformer 11, it is possible to reduce a common mode transformer itself. With this configuration, it is possible to reduce the circuit scale and reduce the size of the voltage converter.
- the voltage controlled power source A actually distorts, and the common mode transformer has leakage inductance, stray capacitance, and non-linearity due to the core material.
- a feedback control method is adopted in which a residual common mode voltage higher than the switching frequency component is detected, amplified and added on the negative side of the common mode transformer. As a result, the common mode voltage can be further reduced.
- FIG. 3 is a diagram illustrating a configuration of a motor control system 1 # based on the second embodiment.
- motor control system 1 # includes an induction motor 6 and a power converter 2 #.
- Power converter 2 # differs from power converter 2 in that common mode suppression circuit 7 is replaced with common mode suppression circuit 7 #. Since other configurations are the same, detailed description thereof will not be repeated.
- the common mode suppression circuit 7 # is a capacitor that detects the remaining common mode voltage that is star-connected to the three-phase cable 5 between the common mode transformer 11 and the induction motor 6.
- the emitter follower circuit 9 # includes bipolar transistors Tr3 and Tr4 that are connected in series with the DC power supply 3 and whose gates are connected to the output of the operational amplifier OP.
- a primary coil of the common mode transformer 11 is provided between a connection node of the bipolar transistors Tr1 and Tr2 and a connection node of the bipolar transistors Tr3 and Tr4.
- connection node NA is connected to the input on one side (+ side) of the operational amplifier OP.
- connection node NA is also connected to a connection node between the DC power supplies 3A and 3B.
- the input on the other side ( ⁇ side) of the operational amplifier OP is connected to the capacitor group 8 # via the resistor R1.
- a resistor R0 is provided between the input on the other side ( ⁇ side) of the operational amplifier OP and the output of the emitter follower circuit 9 #.
- FIG. 4 is a circuit configuration diagram around the voltage control power source A # of the common mode suppression circuit 7 # according to the second embodiment.
- the current flowing in the circuit around the voltage controlled power source A # will be described. Since the resistance R0 is a high resistance, the current I4 is sufficiently smaller than Im.
- FIG. 5 is a diagram for explaining an equivalent circuit around the voltage controlled power source A # of the common mode suppression circuit 7 # according to the second embodiment.
- the voltage control power source A # is composed of an operational amplifier OP, a floating power source, and an emitter follower circuit 9 #.
- the operational amplifier OP operates as an inverting amplifier having a zero phase voltage component as a reference potential.
- FIG. 6 is a diagram illustrating an equivalent circuit for the common mode of the common mode suppression circuit 7 # according to the second embodiment.
- the base currents of the transistors Tr3 and Tr4 that are 1 / hfe (current amplification factor) of the excitation current of the common mode transformer 11 charge and discharge the capacitors 10A and 10B, and the excitation inductance Lm and the capacitor 10A , 10B and a composite capacitor C4 form a resonance circuit.
- the circuit described with reference to FIG. 2 describes a method for canceling the common mode voltage only by feedforward control.
- a method for canceling residual common mode voltage that cannot be canceled by only feedforward control by feedback control is to do.
- Vt Vc-Vcap (Formula 8)
- the equivalent circuit satisfies the relationship of the following expression 9.
- Vt Vc + Vce-Vcap (Equation 9)
- the output Vce of the voltage controlled power supply A # is a voltage that compensates for an error voltage that cannot be canceled out only by feed word control.
- the amplitude of the voltage Vce is sufficiently smaller than the amplitude of the voltage Vc. Therefore, the influence of the voltage Vce can be ignored, and the excitation current Im is mainly defined by the voltage Vc.
- the capacitor C4 when the capacitor C4 is set so that the resonance frequency of the exciting inductance Lm and the capacitor C4 is between the zero-phase voltage frequency and the switching frequency, the following equation 10 is satisfied as described in FIG. Note that the capacitance C4 is shown as a combined capacitance of the capacitors 10A and 10B.
- Vcap Vlow (Equation 10)
- Vcap Vlow (Equation 10)
- the input Ve of the voltage controlled power source A # is expressed by the following expression 11.
- Ve Vo-Vcap (Formula 11) That is, according to Equation 10, the zero-phase voltage component is removed from the common mode voltage Vo.
- the voltage controlled power supply A # is expressed by the following equation 12.
- Vce GVe (Formula 12)
- Ve becomes 0 due to an imaginary short.
- the voltage control power supply A # operates using the zero-phase voltage component as a reference potential, and inputs and outputs only the residual component having a small amplitude.
- This resonance circuit makes the potential of the node NA, which is the midpoint of the power supply and the amplification reference point of the operational amplifier, equal to the zero phase voltage of the inverter.
- the remaining common mode voltage detected by the capacitor group 8 # (C6 to C8) is inverted and amplified by the operational amplifier OP and added to the common mode transformer 11.
- feedback control is performed so that the common mode voltage applied to the inverter load is equal to the zero-phase voltage of the inverter, and only the components of the inverter output common mode voltage that are higher than the switching frequency are canceled. .
- FIG. 7 is another circuit configuration diagram around voltage control power supply A #. As shown in FIG. 7, the emitter follower circuit 9 # is connected to a floating power supply, like the operational amplifier OP.
- the resistance R1 is set to several k ⁇ or more, the current I2 is sufficiently smaller than the current Im, and the following equation is satisfied from Kirchhoff's current law.
- the circuit configuration of FIG. 4 has a smaller current flowing through the floating power source, so that the capacity of the floating power source can be reduced. Further, since the current for charging and discharging the capacitors 10A and 10B is small, the capacity can be reduced. With this configuration, the circuit scale can be further reduced.
- the power supply voltage of the inverter was 200 V and the switching frequency was 100 kHz.
- a 50 Hz sine wave with a modulation factor of 0.6 was used as the output of the inverter.
- FIG. 8 is a diagram for explaining a common mode voltage waveform.
- FIG. 8A shows an inverter output when the common mode voltage is not suppressed.
- FIGS. 8B and 8C show common mode voltages suppressed by the common mode suppression circuits 7 and 7 # according to the first and second embodiments.
- the reference potential is the neutral point of the inverter power supply. As shown in the configuration, the amplitude of 200 V shown in FIG. 8A can be reduced to about 8 V in FIG. 8B if the spike voltage is ignored. Further, in FIG. 8C, the voltage can be reduced to about 2V.
- FIG. 9 is a diagram for explaining the FFT analysis result of the common mode voltage.
- FIG. 9A shows an FFT analysis result when the common mode voltage is not suppressed.
- 9B and 9C show the FFT analysis results of the common mode voltage suppressed by the common mode suppression circuits 7 and 7 # based on the first and second embodiments.
- FIG. 10 is a diagram for explaining the attenuation of the common mode voltage.
- the attenuation amount at 100 kHz is attenuated to 10 dB up to 30 dB and 8 MHz.
- the attenuation amount at 100 kHz is attenuated by 53 dB. Moreover, it has attenuated to 5 dB up to 8 Mhz.
- the power converter including the voltage source PWM inverter according to the present invention is applied to a motor control system for operating an induction motor
- a converter for example, a DC-DC converter
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Abstract
Description
[実施形態1]
図1は、実施形態1に基づくモータ制御システム1の構成を説明する図である。
図2は、実施形態1に基づくコモンモード抑制回路7のコモンモードに対する等価回路を説明する図である。
また、コンデンサ10に生じる電圧Vcapは、零相電圧成分Vlowに基づいて次式2で示される。
また、インバータ出力のコモンモード電圧Vinvは、次式3で示される。
また、電圧Vcapは、次式4の関係を満たす。
さらに、コモンモード電圧は、次式5の関係を満たす。
式2、式4、式5に基づいて以下の関係となる。
当該式により、コモンモード電圧Voは、スイッチング周波数以上の成分が打ち消され零相電圧成分が残留する。
上記の実施形態1においては、理想的な電圧制御電源Aで、コモンモードトランスは漏れインダクタンスのない理想的な場合を例として説明した。
図3を参照して、モータ制御システム1#は、誘導電動機6と、電力変換装置2#とを含む。
抵抗R0は、高抵抗であるため電流I4はImより十分に小さい。
I5=Im/hfe・・・(式6)
電流I4,I2は、電流I5より十分に小さいため、キルヒホッフの電流則より次式7が満たされる。
図5は、実施形態2に基づくコモンモード抑制回路7#の電圧制御電源A#周辺の等価回路を説明する図である。
上記の図2で説明した式4を変形すると次式8が満たされる。
電圧制御電源A#の出力Vceに従って、等価回路においては、次式9の関係を満たす。
電圧制御電源A#の出力Vceがフィードワード制御のみでは打ち消しきれなかった誤差電圧を補償する電圧となる。
電圧制御電源A#の入力Veは、次式11で表わされる。
つまり、式10に従えば、コモンモード電圧Voから零相電圧成分を除いたものとなる。
Vce=GVe・・・(式12)
ゲインGが十分大きい場合には、イマジナリーショートによりVeは0となる。
Vo=Vcap=Vlow・・・(式13)
この時Vceは誤差電圧と等しくなる。
電圧制御電源A#は、零相電圧成分を基準電位として動作し、振幅の小さい残留成分のみを入出力する。
図7に示されるように、エミッタフォロワ回路9#が演算増幅器OPと同様に、フローティング電源に接続されている構成である。
図4の回路構成と比較すると、図4の回路構成の方がフローティング電源を流れる電流が小さいためフローティング電源の容量を小さくすることができる。また、コンデンサ10A,10Bを充放電する電流が小さいため、容量を小さくすることが可能である。当該構成により回路規模をさらに縮小することが可能である。
上記の実施形態1および2のインバータのコモンモード電圧の減衰特性を評価した場合について説明する。
図8は、コモンモード電圧波形について説明する図である。
図8(B),(C)は、実施形態1および2に基づくコモンモード抑制回路7,7#により抑制したコモンモード電圧である。
当該構成に示されるように、図8(A)で示される200Vの振幅が、図8(B)では、スパイク電圧を無視すれば約8V程度に低減することが可能である。さらに、図8(C)では、約2V程度に低減することが可能である。
図9(A)は、コモンモード電圧を抑制しない場合のFFT解析結果である。また、図9(B),(C)は、実施形態1および2に基づくコモンモード抑制回路7,7#により抑制したコモンモード電圧のFFT解析結果である。
図10は、コモンモード電圧の減衰量を説明する図である。
当該図より明らかなように本実施形態1および2に基づくコモンモード抑制回路を用いた場合には、コモンモード電圧を抑制しコモンモード電流の低減に非常に効果的であることが分かる。
Claims (4)
- 電力用半導体素子をスイッチング動作させて電力変換を行う電力変換装置であって、
前記電力用半導体素子のスイッチング動作時に発生するコモンモード電圧を検出する電圧検出手段と、
前記電圧検出手段により検出されたコモンモード電圧を電力増幅する回路により前記コモンモード電圧と同じ大きさで逆極性の電圧を発生する電圧制御電源と、
前記電圧制御電源より発生した電圧を前記電力変換装置の出力に重畳させて前記電力用半導体素子をスイッチング動作させる際に発生するスイッチング周波数以上のコモンモード電圧を相殺する電圧重畳手段とを備える、電力変換装置。 - 前記電圧重畳手段は、多巻線を有するコモンモードトランスと、コンデンサとを含み、
前記電圧重畳手段の前記コモンモードトランスと前記コンデンサとに基づく共振周波数は、前記電力用半導体素子の零相電圧周波数と前記スイッチング周波数との間に設定される、請求項1記載の電力変換装置。 - 前記電圧重畳手段により重畳された前記電力変換装置および前記電圧制御電源のコモンモード電圧を検出する残留電圧検出手段をさらに備え、
前記電圧重畳手段は、前記残留電圧検出手段により検出されたコモンモード電圧を加算して前記電力変換装置の出力に重畳する、請求項1記載の電力変換装置。 - 前記残留電圧検出手段で検出されたコモンモード電圧と、前記コモンモード電圧の零相電圧との比較に基づいて反転増幅し、前記加算する電圧を調整する演算増幅器をさらに備える、請求項3記載の電力変換装置。
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