WO2016019839A1 - 一种射频接收机及接收方法 - Google Patents

一种射频接收机及接收方法 Download PDF

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Publication number
WO2016019839A1
WO2016019839A1 PCT/CN2015/085954 CN2015085954W WO2016019839A1 WO 2016019839 A1 WO2016019839 A1 WO 2016019839A1 CN 2015085954 W CN2015085954 W CN 2015085954W WO 2016019839 A1 WO2016019839 A1 WO 2016019839A1
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Prior art keywords
signal
frequency
band
receiving
radio frequency
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PCT/CN2015/085954
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English (en)
French (fr)
Inventor
易岷
梁建
朱年勇
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华为技术有限公司
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Priority to KR1020177004280A priority Critical patent/KR101913238B1/ko
Priority to JP2017506719A priority patent/JP6340476B2/ja
Publication of WO2016019839A1 publication Critical patent/WO2016019839A1/zh

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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04J—MULTIPLEX COMMUNICATION
    • H04J1/00—Frequency-division multiplex systems
    • H04J1/02—Details
    • H04J1/12—Arrangements for reducing cross-talk between channels
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/005—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission adapting radio receivers, transmitters andtransceivers for operation on two or more bands, i.e. frequency ranges
    • H04B1/0053—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission adapting radio receivers, transmitters andtransceivers for operation on two or more bands, i.e. frequency ranges with common antenna for more than one band
    • H04B1/0057—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission adapting radio receivers, transmitters andtransceivers for operation on two or more bands, i.e. frequency ranges with common antenna for more than one band using diplexing or multiplexing filters for selecting the desired band
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/005—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission adapting radio receivers, transmitters andtransceivers for operation on two or more bands, i.e. frequency ranges
    • H04B1/0053—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission adapting radio receivers, transmitters andtransceivers for operation on two or more bands, i.e. frequency ranges with common antenna for more than one band
    • H04B1/006—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission adapting radio receivers, transmitters andtransceivers for operation on two or more bands, i.e. frequency ranges with common antenna for more than one band using switches for selecting the desired band
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/06—Receivers
    • H04B1/10—Means associated with receiver for limiting or suppressing noise or interference
    • H04B1/12—Neutralising, balancing, or compensation arrangements
    • H04B1/123—Neutralising, balancing, or compensation arrangements using adaptive balancing or compensation means
    • H04B1/126—Neutralising, balancing, or compensation arrangements using adaptive balancing or compensation means having multiple inputs, e.g. auxiliary antenna for receiving interfering signal
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04W—WIRELESS COMMUNICATION NETWORKS
    • H04W88/00—Devices specially adapted for wireless communication networks, e.g. terminals, base stations or access point devices
    • H04W88/02—Terminal devices
    • H04W88/06—Terminal devices adapted for operation in multiple networks or having at least two operational modes, e.g. multi-mode terminals

Definitions

  • the present invention relates to the field of communications, and in particular, to a radio frequency receiver and a receiving method thereof.
  • CA Carrier Aggregation
  • Advanced-LTE Advanced Long-Term Evolution
  • Intra-band in the frequency band
  • Intra-band non-contiguous CA in the frequency band
  • Inter-band non-band, non-contiguous CA, or cross-band CA
  • a and B represent two aggregated carriers, respectively.
  • the RF receiver solution can still be implemented using a traditional single frequency synthesizer; for complex intra-band non-contiguous CA and inter-band non-contiguous CA scenarios, Multiple frequency synthesizers are the only choice for RF receiver solutions, but the existence of mutual interference between multiple frequency synthesizers, including voltage controlled oscillator (VCO) mutual traction (VCO Pulling) and VCO miscellaneous Spur coupling crosstalk is a major problem that hinders the integration of multiple frequency synthesizers into a single chip. Among them, it should be noted that, 1. VCO mutual traction is a common mutual interference phenomenon when multiple VCOs work at the same time.
  • VCO voltage controlled oscillator
  • VCO Pulling VCO mutual traction
  • Spur coupling crosstalk is a major problem that hinders the integration of multiple frequency synthesizers into a single chip.
  • VCO mutual traction is a common mutual interference phenomenon when multiple VCOs work at the same time.
  • VCO spurious coupling crosstalk refers to the frequency component of the actual output of the VCO, except for the frequency components we need. Inevitably, it also contains various spurs (unwanted frequency components). These spurs have many causes, which may be caused by the reference clock, or may be the frequency synthesizer nonlinearity.
  • the spurious component of one VCO output if coupled to other receiving channels, overlaps with the spectrum of the useful signal that the receiving channel needs to receive, ie Falling in the receiving band of the receiving channel will affect the receiving performance of the channel.
  • One possible RF receiver solution is to set multiple frequency synthesizers on different chips, which can effectively solve the mutual interference problem of multiple frequency synthesizers.
  • the cost of using this multi-chip solution is This is a significant increase in area and cost, which is contrary to the current miniaturization and low cost requirements of the RF subsystem.
  • the embodiment of the invention provides a radio frequency receiver to solve the problem that the prior art cannot integrate multiple frequency synthesizers in a single chip.
  • an embodiment of the present invention provides a radio frequency receiver, including:
  • a frequency band splitter an input end of the frequency band splitter coupled to the antenna, configured to receive a radio frequency signal from the antenna, and perform frequency band separation on the radio frequency signal to obtain and output at least one frequency band signal, wherein the radio frequency signal a carrier-aggregation signal for a multi-carrier, each of the frequency band signals including at least one of the plurality of carriers;
  • Processing circuitry coupled to the output of the band splitter, for filtering and amplifying the at least one band signal to obtain at least one processed signal
  • any one of the receiving channels is configured to selectively receive the included ones from the at least one processed signal output by the processing circuit
  • the processing signal is mixed to obtain a mixed signal, and based on the mixed signal, a baseband signal corresponding to the target carrier is generated, where the target carrier is one of multiple carriers included in the radio frequency signal;
  • the plurality of receiving channels respectively suppress mutual interference between the plurality of frequency synthesizers by selecting respective frequency dividing ratios.
  • the plurality of frequency division ratios are selected from a set comprising a plurality of integer division ratios and a plurality of fractional division ratios.
  • any one of the processing units includes:
  • a band pass filter configured to receive one of the at least one frequency band signal output by the frequency band splitter, and filter out signals outside the frequency band of the one frequency band signal to obtain a signal in one frequency band;
  • a radio frequency amplifier coupled to the band pass filter for receiving signals in the one frequency band and gain amplifying the signals in the one frequency band to obtain the one processed signal.
  • the radio frequency receiver further includes: a switching unit, where the switching unit is coupled to the multiple processing units and the multiple Between the receiving channels, the switching unit is configured to selectively switch the one of the receiving channels to one of the processing circuits to receive a target carrier including the any of the receiving channels by switching control The processing signal.
  • any one of the multiple receiving channels includes:
  • a frequency divider for receiving a control signal, and selectively selecting a frequency division ratio of any one of the plurality of frequency division ratios under the control of the control signal, and based on the And frequency-dividing the oscillating signal received by any one of the receiving channels to obtain the local oscillator signal;
  • a mixer configured to perform mixing on the received processed signal by using the local oscillator signal to obtain a mixed signal
  • a low pass filter for performing noise suppression on the mixed signal
  • a baseband amplifier configured to amplify the mixed signal that performs noise suppression on the low pass filter to generate a baseband signal corresponding to the target carrier.
  • the configurable frequency divider includes: a multi-selection frequency divider, the multiple-selection frequency divider includes multiple a frequency division mode, wherein each of the frequency division modes corresponds to an integer division ratio or a fractional division ratio, and the multiple selection one frequency divider is configured to perform the plurality of frequency division modes under the control of the control signal
  • a frequency division mode is configured as a current mode of operation to selectively select the frequency division ratio of any of the plurality of frequency division ratios.
  • the configurable frequency divider includes: a plurality of frequency division units and a selector, wherein each frequency division unit corresponds to an integer value a frequency ratio or a fractional division ratio, one end of each of the plurality of frequency division units being coupled to an input of the configurable frequency divider, the other end of the plurality of frequency division units being respectively coupled to an input of the selector And an output of the selector is coupled to an output of the configurable frequency divider, the selector is configured to receive the control signal, and select the plurality of frequency divisions under control of the control signal One of the frequency dividing units in the unit is turned on to selectively select the one of the plurality of frequency dividing ratios The division ratio of a receiving channel.
  • the radio frequency receiver further includes: a control signal a generator for generating a control signal required by the configurable divider in any of the receive channels.
  • the radio frequency receiver further includes: baseband processing And performing baseband processing on the baseband signals output by the plurality of receiving channels.
  • the any receiving channel is zero intermediate frequency receiving aisle.
  • the multiple frequency synthesizer and the Multiple receive channels are integrated into one integrated circuit.
  • an embodiment of the present invention provides a receiving method, including:
  • radio frequency signal is a multi-carrier carrier aggregation signal, and each frequency band signal includes at least one of the multiple carriers;
  • the plurality of oscillating signals are divided by respectively selecting a frequency dividing ratio to suppress mutual interference between the plurality of oscillating signals.
  • the plurality of frequency division ratios are selected from a set comprising a plurality of integer division ratios and a plurality of fractional division ratios.
  • the filtering and amplifying processing, respectively, the at least one frequency band signal to obtain at least one processing signal including:
  • the selectively receiving, by the at least one processing signal, a processing signal that includes a target carrier includes:
  • the processing signal including the target carrier is selectively received from the at least one processed signal by switching control.
  • the selecting one of the plurality of frequency division ratios a frequency division ratio, using the frequency division ratio to divide the received oscillating signal to obtain a local oscillator signal including:
  • the local oscillator signal is obtained.
  • the radio frequency receiver provided by the present invention can implement the single Chip integration.
  • FIG. 1 is a schematic diagram of an application scenario of a typical carrier aggregation
  • FIG. 2 is a structural diagram of a zero intermediate frequency receiver in the prior art
  • FIG. 3 is a structural diagram of a radio frequency receiver according to Embodiment 1 of the present invention.
  • FIG. 4 is a circuit diagram of a radio frequency receiver according to Embodiment 1 of the present invention.
  • FIG. 5 is a circuit diagram of another radio frequency receiver according to Embodiment 1 of the present invention.
  • FIG. 6A is a circuit diagram of a configurable frequency divider according to Embodiment 1 of the present invention.
  • FIG. 6B is a circuit diagram of another configurable frequency divider according to Embodiment 1 of the present invention.
  • FIG. 7 is a circuit diagram of still another radio frequency receiver according to Embodiment 1 of the present invention.
  • FIG. 8A is a schematic diagram of receiving a cross-band discontinuous CA signal based on the radio frequency receiver shown in FIG. 5;
  • 8B is a schematic diagram showing mutual traction between two VCOs in a conventional radio frequency receiver
  • 9A is a schematic diagram of a discontinuous CA signal in a receiving frequency band based on the radio frequency receiver shown in FIG. 5;
  • 9B is a schematic diagram showing the presence of spurious coupling crosstalk between two VCOs in a conventional radio frequency receiver
  • FIG. 10 is a schematic diagram of receiving a cross-band discontinuous CA signal based on the radio frequency receiver shown in FIG. 7;
  • FIG. 11 is a schematic diagram of receiving another cross-band discontinuous CA signal based on the radio frequency receiver shown in FIG. 7;
  • FIG. 12 is a flowchart of a receiving method according to Embodiment 2 of the present invention.
  • Figure 2 shows the architecture of a conventional zero intermediate frequency (ZIF) receiver.
  • ZIF zero intermediate frequency
  • the most attractive aspect of the zero-IF receiver is that the intermediate frequency is not required in the down-conversion process, and the image frequency is the RF signal itself. There is no image frequency interference.
  • the super-heterodyne receiver architecture The image suppression filter and the intermediate frequency filter used can be omitted. In this way, the external components are eliminated, which facilitates the monolithic integration of the system and reduces the cost. On the other hand, the number of circuit modules and external nodes required by the system is reduced, which reduces the power consumption required by the receiver and reduces the chance of external interference of the RF signal.
  • a radio frequency receiver including:
  • the antenna 100 is configured to receive a radio frequency signal, for example, a radio frequency signal transmitted by a base station in a wireless network, where the radio frequency signal is a carrier aggregation signal of a multi-carrier, and those skilled in the art should know that, in practical applications, a carrier of a multi-carrier
  • the aggregation mode includes at least one of continuous carrier aggregation in a frequency band, discontinuous carrier aggregation in a frequency band, and discontinuous carrier aggregation in a frequency band. For details, refer to several typical multi-carrier aggregation modes shown in FIG. Those skilled in the art will appreciate that when the radio frequency receiver in an embodiment of the present invention is integrated in a chip, the antenna 100 is typically not included in the chip.
  • a band splitter 200 an input end of the band separator 200 is coupled to the antenna 100, configured to receive the radio frequency signal output by the antenna 100, and perform frequency band separation on the radio frequency signal to obtain At least one frequency band signal is outputted, wherein each frequency band signal includes at least one of the multiple carriers.
  • the frequency band separator 200 in this embodiment may include a duplexer (Diplexer, or For the transceiver, the triplexer, the quadruple, etc., the specific device is related to the number of frequency bands included in the multi-carrier CA signal, for example, the multi-carrier CA signal includes three frequency band signals.
  • the Diplexer can be used to separate the two frequency band signals; in addition, those skilled in the art should know that The couplings mentioned in the embodiments of the invention have the general meanings in the art, including but not limited to direct or indirect connections in the electrical sense, similar to the following. ,No longer;
  • the band separator 200 can perform frequency band separation on the radio frequency signal according to the carrier aggregation mode of the multi-carrier. Specifically, if the radio frequency signal received by the antenna 100 is a multi-carrier cross-band CA signal, the band separator 200 can The cross-band CA signal is divided into multiple frequency band signals according to the frequency band of the frequency band. For example, see FIG. 8A, for one carrier A on the Band 8 (carrier frequency is 935 MHz) and one carrier B on the Band 3 (carrier frequency is 1870.1 MHz).
  • the RF signal, the band separator 200 can correspondingly adopt the Diplexer, and the Diplexer can divide the RF signal into a high frequency band signal (ie, Band 3 including one carrier B) and a low frequency band signal (ie, Band 8 including one carrier A); If the radio frequency signal received by the antenna 100 is a discontinuous CA signal in the frequency band or a continuous CA signal in the frequency band, the frequency band separator 200 may divide the multiple carriers in the discontinuous CA in the frequency band or the continuous CA in the frequency band into one frequency band signal, for example, See Figure 9A.
  • Band 25 includes two discontinuous carriers A and B. Due to the accuracy limitations of the Triplex, the aggregated carriers in Band 25 cannot be separated.
  • band signal including carrier A and carrier B (ie, Band 25).
  • carrier A and carrier B ie, Band 25.
  • Band 3 Band 8 mentioned in this article.
  • Band 25 and other frequency band signals the frequency range of which can refer to the corresponding provisions in the 3GPP protocol, and will not be described in detail here.
  • Processing circuit 300 coupled to the output of the band separator 200, for filtering and amplifying the at least one band signal output by the band separator 200, respectively, to obtain at least one process signal.
  • the plurality of frequency synthesizers 400 are configured to generate a plurality of oscillating signals, wherein the frequencies of the plurality of oscillating signals are different.
  • any one of the receiving channels is configured to selectively output the at least one processed signal from the processing circuit 300
  • the plurality of receiving channels 500 respectively suppress mutual interference between the plurality of frequency synthesizers 400 by selecting respective frequency dividing ratios;
  • the mutual interference between the multiple frequency synthesizers mainly includes: 1. mutual traction, and 2, spurious coupling crosstalk.
  • any one of the receiving channels selects any one of the receiving channels. a frequency division ratio, such that an oscillating signal generated by a frequency synthesizer corresponding to any one of the receiving channels is between an oscillating signal other than the oscillating signal corresponding to any one of the plurality of oscillating signals
  • the mutual traction effect is weakened, that is, the pulling effect of the other frequency synthesizers other than the one frequency synthesizer corresponding to any of the receiving channels on the any receiving channel is suppressed, and the any receiving channel is A signal obtained by dividing a spur component of another oscillating signal does not overlap with the target carrier of any one of the receiving channels, that is, suppressing a frequency synthesizer corresponding to any one of the receiving channels
  • FIGS. 8A and 9A the carrier B in the Band 8 and the carrier B in the Band 3 are aggregated across the frequency band.
  • LO B 1969.2 MHz
  • integers are usually used.
  • the spur component of the receiving performance of the receiving channel 501A is audible. It can be seen that by flexibly selecting the respective frequency dividing ratios of the plurality of receiving channels 500, the plurality of frequency synthesizers 400 corresponding to the plurality of receiving channels 500 can be suppressed. Stray-coupled crosstalk between.
  • multiple frequency division ratios of the frequency division ratio of any one of the receiving channels may be selected from a set including multiple integer frequency division ratios and multiple fractional frequency division ratios, that is, the multiple
  • the frequency division ratio may include: a plurality of integer division ratios and at least two division ratios of the plurality of fractional division ratios, that is, the plurality of division ratios may be a set of multiple integer division ratios, or Is a set of multiple fractional division ratios, or a set of fractional division ratios and integer division ratios; in this embodiment, multiple fractions including fractional division ratio and/or integer division ratio are provided
  • the frequency ratio makes each receiving channel have strong flexibility when selecting respective frequency dividing ratios to suppress mutual interference between respective frequency synthesizers of respective receiving channels.
  • FIG. 4 only exemplarily includes two receiving channels.
  • the receiver architecture of the two frequency synthesizers in the actual application, the receiving channel can be extended on the basis of FIG. 4, and therefore the scope of protection of the present invention cannot be limited by the content of FIG.
  • the processing circuit 300 may include a plurality of processing units 301, the number of the plurality of processing units 301 may be equal to the number of outputs of the band separator 200, and the plurality of processing units 301 are respectively coupled.
  • Each of the output units 301 is configured to filter and amplify one of the at least one frequency band signal output by the band separator 200 to obtain a processing signal; Still taking the receiver shown in FIG. 8A as an example, when the carrier aggregation signal is a carrier A on Band 8 and a carrier B on Band 3 is aggregated across the frequency band, the band separator 200 can adopt a Diplexer, and correspondingly, the Diplexer has Two output terminals: a first output end and a second output end, the first output end is used for outputting a frequency band signal of a high frequency band, that is, a frequency band signal (Band 3) where the carrier B is located, and the second output end is for outputting a low frequency band
  • the frequency band signal, that is, the frequency band signal (Band 8) where the carrier A is located, and the processing circuit 300 corresponding thereto also includes two processing units, one of which is coupled to the first output The terminal is used for filtering and amplifying the high-band signal (Band 3), and the other
  • the band separator 200 outputs only one band signal, if the band separator 200 is still a Diplexer, the band signal can be outputted by the first output terminal or the second output terminal, and if the band signal is output by the first output terminal, Among the plurality of processing units, only one processing unit coupled to the first output end of the Diplexer processes the frequency band signal to obtain a processing signal including the first carrier and the second carrier;
  • any one of the plurality of processing units 301 may include: a band pass filter 3011 and a radio frequency amplifier 3012, wherein an input end of the band pass filter 3011 is coupled to one of the band separators 200 An output end of the band pass filter 3011 is coupled to an input end of the radio frequency amplifier 3012, and the band pass filter 3011 is configured to receive one of the at least one band signal output by the band separator 200, and filter A signal in a frequency band is obtained by a signal other than the frequency band of the one frequency band signal; the RF amplifier 3012 is configured to receive a signal in a frequency band obtained by filtering the band pass filter 3011, and perform a gain on the signal in the one frequency band.
  • Amplifying to obtain a processed signal it should be understood that the structure of the plurality of processing units may be the same, except that in order to process signals of different frequency bands, the band pass filters in the respective processing units are allowed to pass different frequency ranges;
  • the front-end RF amplifier of various wireless receivers when amplifying weak signals, the RF amplifier itself The interference of noise on the signal may be very serious.
  • a low-noise amplifier is usually used.
  • band-pass filtering and gain amplification of the RF signal refer to the prior art. No longer detailed.
  • the radio frequency receiver may further include: a switching unit 600, where the switching unit 600 is coupled between the plurality of processing units 301 and the plurality of receiving channels 500, The switching unit 600 is configured to selectively couple the any receiving channel to one of the processing circuits 300 to receive the processing signal of the target carrier including the any receiving channel by switching control Specifically, referring to FIG. 5, in the radio frequency receiver shown in FIG. 5, the plurality of receiving channels 500 include two receiving channels (labeled as 501A and 501B for convenience of description), and the processing circuit 300.
  • the switching unit 600 may specifically include: a first switch 601, a second switch 602, and a third switch 603; wherein the first switch 601 includes two processing units (labeled as 301A and 301B for convenience of description). One end of the first switch 601 is coupled to the RF input end of the receiving channel 501A and one end of the second switch 602; one end of the third switch 603 is coupled to the end of the first switch 601A; The other end of the third switch 603 is coupled to the radio frequency input end of the receiving channel 501B and the other end of the second switch 602.
  • the switching unit 600 can control the on and off of the three switches.
  • the first switch 601 and the third switch 603 can be simultaneously controlled. Turning on, controlling the second switch 602 to be disconnected, so that the band signal Band 3 is transmitted along the link of 301A ⁇ 601 ⁇ 501A to the receiving channel 501A, so that the band signal Band 8 is transmitted along the link of 301B ⁇ 603 ⁇ 501B to the receiving channel.
  • the target carrier of the receiving channel 501A is the carrier B, and the target carrier of the receiving channel 501B is the carrier A; and when the radio frequency signal is the discontinuous CA of the two carriers A and B in the band signal Band 25, refer to FIG. 9A,
  • the band separator 200 cannot separate a plurality of carriers in one frequency band, and the band separator 200 can select only one output terminal to output the band signal, assuming that the processing unit 301A inputs the band separator 200.
  • the third switch 603 is controlled to be turned off by simultaneously controlling the first switch 601 and the second switch 602 to be turned on, so that the band signal Band 25 is transmitted along the link of 301A ⁇ 601 ⁇ 501A.
  • the frequency receiving channel 501A is transmitted to the frequency receiving channel 501B along the link of 301A ⁇ 601 ⁇ 602 ⁇ 501B, wherein the target carrier of the receiving channel 501A is the carrier A, and the target carrier of the receiving channel 501B is the carrier B; That is, in FIGS. 8A, 8B, 9A, and 9B, the numbers of the respective devices are omitted for the sake of brevity, and the numbers in FIG. 5 may be specifically referred to.
  • the switching unit 600 can also include: The fourth switch 604 and the fifth switch 605 can receive more types of CA signals by controlling the conduction of the five switches.
  • the radio frequency signals are the carrier A in the Band 3 and the carrier B in the Band 4
  • the switching unit controls the first switch 601, the third switch 603, the fifth switch 605 to be turned on, and controls the second switch 602 and the fourth.
  • the switch 604 is disconnected, and the Band 5 can be transmitted along the 301A ⁇ 601 ⁇ 501A to the receiving channel 501A, and the Band 4 is transmitted along the 301B ⁇ 603 ⁇ 501B to the receiving channel 501B, so that the Band 3 is transmitted to and received along 301C ⁇ 605 ⁇ 501C.
  • Channel 501C wherein the target carrier of the receiving channel 501A is the carrier C, the target carrier of the receiving channel 501B is the carrier B, and the target carrier of the receiving channel 501C is the carrier A; and when the radio frequency signal is the carrier A and the B in the band 3 is discontinuous CA, and then with the carrier C in the Band 5 spanning the band CA, referring to FIG.
  • the switching unit 600 can simultaneously control the first switch 601, and the third Switch 603 and fourth switch 604
  • the Band 5 can be transmitted to the receiving channel 501A along 301A ⁇ 601 ⁇ 501A
  • the Band 3 can be transmitted to the receiving channel 501B along 301B ⁇ 603 ⁇ 501B
  • along 301B ⁇ 603 ⁇ 604 ⁇ 501C is transmitted to the receiving channel 501C
  • the target carrier of the receiving channel 501A is the carrier C
  • the target carrier of the receiving channel 501B is the carrier B
  • the target carrier of the receiving channel 501C is the carrier A
  • the numbers of the respective devices are omitted, and the numbers in FIG. 7 may be specifically referred to.
  • the switching unit 600 can selectively receive any one of the plurality of receiving channels 500 from the at least one processed signal processed by the processing circuit 300 by using the switching control.
  • the processing signal of the target carrier of any one of the receiving channels is at the same time, so that the radio frequency receiver of the embodiment can be widely applied to multiple application scenarios such as continuous CA in the frequency band, discontinuous CA in the frequency band, and cross-band CA. Compatibility.
  • only the combination of multiple switches is used to explain the working principle of the switching unit 600. In practical applications, those skilled in the art may use other circuits or chips with switching control functions to implement corresponding functions. .
  • any one of the multiple receiving channels 500 may specifically include:
  • the frequency divider 5011 is configured to receive a control signal (control, CTRL), and selectively select a frequency division ratio of any one of the plurality of frequency division ratios under the control of the control signal And dividing the oscillating signal received by any one of the receiving channels according to the frequency dividing ratio to obtain the local oscillator signal;
  • a mixer 5012 configured to perform mixing on the received processed signal by using the local oscillator signal to obtain a mixed signal
  • a low pass filter 5013 for performing noise suppression on the mixed signal
  • the baseband amplifier 5014 is configured to amplify the mixed signal that performs noise suppression on the low pass filter to generate a baseband signal corresponding to the target carrier.
  • the configurable frequency divider 5011 may specifically include: a multi-selection frequency divider 50111, the multi-selection frequency divider 50111 includes A plurality of frequency division modes, wherein each of the frequency division modes corresponds to an integer division ratio or a fractional division ratio, for example, may include a divide by 1, a divide by 0.75, a divide by 1.25, a divide by 1.5, a divide by 1.75, and a divide of 2 a plurality of frequency division modes, the multi-selection frequency divider is configured to receive the control signal CTRL, and configure one of the plurality of frequency division modes according to the control signal a current operating mode, to selectively select the frequency dividing ratio of any one of the plurality of frequency dividing ratios;
  • the configurable frequency divider 5011 may further include: a plurality of frequency dividing units 50121A and a selector 50121B, wherein each frequency dividing unit corresponds to an integer frequency division.
  • One or more of the plurality of frequency dividing units 50121A are coupled to the input of the configurable frequency divider 5011, and the other ends of the plurality of frequency dividing units 50121A are coupled to the selector, respectively
  • An input of the selector 50121B is coupled to an output of the configurable frequency divider 5011, the selector 50121B is configured to receive the control signal CTRL and under the control of the control signal Selecting one of the plurality of frequency dividing units to be turned on to selectively select the frequency dividing ratio of any one of the plurality of frequency dividing ratios, wherein each frequency dividing unit
  • the unit may be a frequency dividing device or a circuit having a frequency dividing capability, for example, may be an integer frequency divider such as a divide by 1, a divide by two, or
  • the frequency divider is not limited in this embodiment. It should be appreciated, embodiments of the frequency divider 5011 may be configured embodiment of the present invention. It may also be another frequency dividing device having a plurality of frequency dividing ratios, or a circuit or chip having a plurality of frequency dividing ratios combined by a plurality of common frequency dividing devices, and therefore, should not be as shown in FIGS. 6A and 6B.
  • the specific circuit structure limits the scope of protection of the present invention.
  • the radio frequency receiver may further include: a control signal generator 700, configured to generate the configurable frequency divider in any one of the receiving channels. And controlling a signal to control the plurality of receiving channels to select respective frequency dividing ratios, thereby suppressing mutual interference between the plurality of frequency synthesizers.
  • a control signal generator 700 configured to generate the configurable frequency divider in any one of the receiving channels. And controlling a signal to control the plurality of receiving channels to select respective frequency dividing ratios, thereby suppressing mutual interference between the plurality of frequency synthesizers.
  • any one of the plurality of receiving channels 500 can be a zero-IF receiving channel, and the following is combined with FIG. 5 for zero-IF receiving.
  • the channel is briefly described.
  • the mixer 5012 may include two in-phase quadrature I/Q in-phase mixers 5012A and positive.
  • the cross mixer 5012B is configured to respectively receive a processing signal of the target carrier including the any receiving channel, and use the two local oscillator signals (LO I , LO Q ) with a phase difference of 90° to perform the processing on the receiving
  • the signal is mixed to obtain two mixed signals
  • the low pass filter 5013 may include an in-phase low pass filter 5013A and an orthogonal low pass filter 5013B for respectively in-phase mixer 5012A and orthogonal
  • the mixing signal obtained by mixing the mixer 5012B performs noise suppression
  • the baseband amplifier 5014 may include an in-phase baseband amplifier 5014A and a quadrature baseband amplifier 5014B for the in-phase low pass filter 5013A and the orthogonal low pass filter, respectively.
  • the mixed signal of the noise suppression after 5013B is amplified to generate two I/Q baseband signals corresponding to the target carrier. It should be known that those skilled in the art have fully studied the architecture of the zero intermediate frequency receiver, and here is not For further details, specific reference may be made to the prior art;
  • the configurable frequency divider may further include: a poly-phase filter (PPF) 50112,
  • PPF poly-phase filter
  • the polyphase filter 50112 is coupled between an input of the configurable frequency divider 5011 and an input of the multi-selection divider 50111, or coupled to an input of the configurable frequency divider 5011.
  • the vibration signals LO I and LO Q in particular, the polyphase filter 50112 can use different clock edges to phase delay the frequency-divided signals to generate a certain phase difference, wherein the phase delay mechanism using the clock edges belongs to the present invention. Public of field technicians For common sense, you can refer to the prior art and will not be described in detail here.
  • the configurable frequency divider 5011 may further include: a sixth switch 50113, a seventh switch 50114, a first integer frequency divider 50115, and a second integer frequency divider 50116.
  • the first integer frequency divider 50115 and the second integer frequency divider 50116 may be utilized to pair the multiple selected one frequency divider 50111 or the The signal output by the selector 50121B is further divided, for example, assuming that the first integer frequency divider 50115 and the second integer frequency divider 50116 are both frequency dividers, if the sixth switch 50113 is simultaneously controlled to be turned on and the seventh switch 50114 is controlled.
  • the signal output by the multi-selection frequency divider 50111 or the selector 50121B may be divided by two. If the sixth switch 50113 is simultaneously turned off and the seventh switch 50114 is controlled to be turned on, The multi-selection frequency divider 50111 or the signal output by the selector 50121B is divided by four, thereby improving the flexibility of the configurable frequency divider 5011 in the frequency division ratio configuration, and is advantageous for expanding the frequency division signal. width.
  • the radio frequency receiver may further include: a baseband processor 800,
  • the baseband signal outputted by the plurality of receiving channels 500 is subjected to baseband processing.
  • the receiving channel is a zero intermediate frequency receiving channel
  • the I/Q two baseband signals are specifically subjected to baseband processing, wherein the working principle of the baseband processor Reference can be made to the prior art and will not be described in detail herein.
  • the radio frequency receiver is a single chip integrated radio frequency receiver, that is, the plurality of frequency synthesizers 400 and the plurality of receiving channels 500 are integrated in one integrated circuit, of course, the processing circuit 300 and the switching
  • the unit 600, the control signal generator 700 for example, can be integrated in a radio frequency chip, and the technical solution of the embodiment of the present invention can effectively suppress multiple radio receivers including a plurality of frequency synthesizers
  • the mutual interference caused by the mutual proximity of the frequency synthesizers compared with the conventional multi-chip scheme for receiving multi-carrier CA signals
  • the single-chip integrated radio frequency receiver provided by the invention can save chip area and reduce cost, and it should be noted that
  • the baseband processor 800 is usually integrated in a main chip independent of the radio frequency chip.
  • the antenna 100 and the baseband processor 800 are introduced to clearly illustrate the process from receiving the radio frequency signal to completing. The complete process of baseband signal processing.
  • the embodiment of the present invention further provides a method for receiving a multi-carrier aggregated radio frequency signal, including the following steps:
  • Radio frequency signal is a carrier aggregation signal of multiple carriers.
  • each frequency band signal includes at least one of the multiple carriers
  • the plurality of oscillating signals are divided by respectively selecting a frequency dividing ratio to suppress mutual interference between the plurality of oscillating signals.
  • the radio frequency receiver selects a frequency division ratio to make a target carrier corresponding to the plurality of oscillation signals.
  • the signal obtained by dividing the corresponding one of the oscillating signals does not overlap with the target carrier corresponding to the oscillating signal other than the oscillating signal corresponding to the target carrier, and the pair of oscillating signals are
  • the spur component of the signal obtained by dividing the oscillating signal corresponding to the target carrier does not overlap with the target carrier corresponding to the oscillating signal other than the oscillating signal corresponding to the target carrier, that is, by selecting more
  • the frequency division ratio divides the plurality of oscillation signals, and suppresses mutual traction and spurious coupling crosstalk between the plurality of oscillation signals.
  • the plurality of frequency division ratios are selected from a set including a plurality of integer frequency division ratios and a plurality of fractional frequency division ratios, that is, the plurality of frequency division ratios may include multiple integer division ratios and At least two of the plurality of fractional division ratios; the RF receiver of the embodiment of the present invention is received because a plurality of division ratios including a fractional division ratio and/or an integer division ratio are provided In the case of the radio frequency signal, each of the receiving channels can more flexibly select the respective frequency dividing ratio to suppress mutual interference between the respective frequency synthesizers of the respective receiving channels.
  • filtering and amplifying the at least one frequency band signal to obtain at least one processing signal which may include:
  • the selectively receiving a processing signal including the target carrier from the at least one processed signal may include:
  • the processing signal including the target carrier of any of the receiving channels is selectively received from the at least one processed signal by switching control.
  • the selectively selecting a frequency division ratio among the plurality of frequency division ratios, and dividing the received oscillating signal by the frequency division ratio to obtain a local oscillation signal may include:
  • the local oscillator signal is obtained.
  • the second embodiment of the present invention is implemented based on the method of the radio frequency receiver provided in the first embodiment. Therefore, the related features in the first embodiment and the second embodiment can be related.

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Abstract

本发明公开一种射频接收机及接收方法，所述方法包括：对多载波聚合的射频信号进行频段分离，以得到至少一个频段信号并输出；分别对所述至少一个频段信号进行滤波和放大处理，以得到至少一个处理信号；产生多个振荡信号；选择性地从所述至少一个处理信号中接收包括目标载波的一个处理信号，以及接收与所述目标载波对应的一个振荡信号，并选择性地在多个分频比中选择一个分频比，利用所述分频比对接收的所述振荡信号进行分频，得到本振信号，利用所述本振信号对接收的包括目标载波的所述处理信号进行混频，以得到一个混频信号，并基于所述混频信号，生成与所述目标载波对应的基带信号，其中，通过分别选择分频比，抑制所述多个振荡信号之间的相互干扰。

Description

一种射频接收机及接收方法
本申请要求于2014年8月7日提交中国专利局、申请号为201410387196.4、发明名称为“一种射频接收机及接收方法”的中国专利申请的优先权，其全部内容通过引用结合在本申请中。
技术领域
本发明涉及通信领域，尤其涉及一种射频接收机及其接收方法。
背景技术
目前，为了增加通信带宽，实现更高的用户数据吞吐率，在先进的长期演进技术(Long-Term Evolution–Advanced,LTE-A)中，采用了载波聚合(Carrier Aggregation，CA)技术，CA技术的原理是将用户通信数据承载在多个载波上进行通信；然而，CA技术的引入，对原有的射频接收机解决方案造成了很大的影响。
在3GPP(第三代合作伙伴计划)协议R10(Release 10，版本10)中，定义了以下三种CA应用场景，如图1所示：
频段内连续CA(intra-band，contiguous CA)；
频段内不连续CA(intra-band，non-contiguous CA)；
跨频段不连续CA(inter-band，non-contiguous CA)，或称为跨频段CA；
其中，A和B分别表示两个聚合的载波。
对于intra-band contiguous CA应用场景，射频接收机解决方案仍然可以采用传统的单个频率综合器实现；而对于复杂的intra-band non-contiguous CA和inter-band non-contiguous CA两种应用场景，使用多个频率综合器是射频接收机解决方案唯一的选择，但是，多个频率综合器间的互扰的存在，包括电压控制震荡器(voltage controlled oscillator，VCO)相互牵引(VCO Pulling)和VCO杂散(Spur)耦合串扰，是阻碍多个频率综合器单芯片集成的主要问题。其中，需要说明的是，1、VCO相互牵引是多个VCO同时工作时常见的互扰现象，以两个VCO同时工作的场景为例，VCO1的振荡能量会耦合到VCO2，使得VCO2的输出信号中含有VCO1振荡频率的频率分量，因而影响采用VCO2作为本振信号的接收通道的接收质量；2、VCO杂散耦合串扰，是指VCO实际输出的频率成分中，除了我们需要的频率成分外，不可避免的还包含各种杂散(不需要的频率成分)，这些杂散的成因很多，可能是参考时钟造成的，也可能是频率综合器非线性 造成的，在多个频率综合器、多个接收通道的应用场景中，其中一个VCO输出的杂散分量，如果耦合到其他的接收通道，与该接收通道需要接收的有用信号的频谱重叠，即落在该接收通道的接收带内，就会影响该通道的接收性能。
一种可能的射频接收机解决方案是将多个频率综合器设置在不同的芯片内，可以比较有效的解决多个频率综合器的互扰问题，但是，采用这种多芯片方案，所付代价是面积与成本的显著增加，这和当前移动终端日益强烈的射频子系统小型化、低成本需求相违背。
发明内容
本发明实施例提供一种射频接收机，以解决现有技术无法将多个频率综合器集成在单芯片中的问题。
第一方面，本发明实施例提供了一种射频接收机，包括：
频段分离器，所述频段分离器的输入端耦合至天线，用于从所述天线接收射频信号，并对所述射频信号进行频段分离，以得到至少一个频段信号并输出，其中所述射频信号为多载波的载波聚合信号，每个频段信号上包括所述多载波中的至少一个载波；
处理电路，所述处理电路耦合至所述频段分离器的输出端，用于分别对所述至少一个频段信号进行滤波和放大处理，以得到至少一个处理信号；
多个频率综合器，用于产生多个振荡信号；
多个接收通道，所述多个接收通道与所述多个频率综合器一一对应，其中任一接收通道用于选择性地从所述处理电路输出的所述至少一个处理信号中接收包括所述任一接收通道的目标载波的一个处理信号，以及接收与所述任一接收通道对应的一个频率综合器所产生的振荡信号，并选择性地在多个分频比中选择所述任一接收通道的分频比，利用所述分频比对接收的所述振荡信号进行分频，得到所述任一接收通道的本振信号，利用所述本振信号对接收的包括目标载波的所述处理信号进行混频，以得到一个混频信号，并基于所述混频信号，生成与所述目标载波对应的基带信号，所述目标载波为所述射频信号包括的多载波中的一个；
所述多个接收通道分别通过选择各自的分频比，抑制所述多个频率综合器之间的相互干扰。
在第一方面的第一种可能的实现方式中，所述多个分频比从包括多个整数分频比和多个小数分频比的集合中选择得到。
结合第一方面，或者第一方面的第一种可能的实现方式，在第二种可能的实现方式中，其中的任一处理单元包括：
带通滤波器，用于接收所述频段分离器输出的所述至少一个频段信号中的一个频段信号，并滤除所述一个频段信号的频段之外的信号，得到一个频段内的信号；
射频放大器，耦合至所述带通滤波器，用于接收所述一个频段内的信号，并对所述一个频段内的信号进行增益放大，以得到所述一个处理信号。
结合第一方面第二种可能的实现方式，在第三种可能的实现方式中，所述射频接收机还包括：切换单元，所述切换单元耦合在所述多个处理单元和所述多个接收通道之间，所述切换单元用于通过切换控制，使得所述任一接收通道选择性地耦合至所述处理电路中的一个处理单元，以接收包括所述任一接收通道的目标载波的所述处理信号。
结合第一方面或第一方面的任意一种可能的实现方式，在第四种可能的实现方式中，所述多个接收通道中的任一接收通道包括：
可配置分频器，用于接收控制信号，并在所述控制信号的控制下选择性地在所述多个分频比中选择所述任一接收通道的分频比，并基于所述分频比对所述任一接收通道接收的所述振荡信号进行分频，得到所述本振信号；
混频器，用于利用所述本振信号对接收的所述处理信号进行混频得到混频信号；
低通滤波器，用于对所述混频信号进行噪声抑制；
基带放大器，用于对所述低通滤波器进行噪声抑制后的混频信号进行放大，以生成所述目标载波对应的基带信号。
结合第一方面的第四种可能的实施方式，在第五种可能的实施方式中，所述可配置分频器包括：多选一分频器，所述多选一分频器包括多种分频模式，其中每种分频模式对应一个整数分频比或小数分频比，所述多选一分频器用于在所述控制信号的控制下，将所述多种分频模式中的一种分频模式配置为当前工作模式，以实现选择性地在多个分频比中选择所述任一接收通道的所述分频比。
结合第一方面第四种可能的实现方式，在第六种可能的实现方式中，所述可配置分频器包括：多个分频单元和选择器，其中每个分频单元对应一个整数分频比或小数分频比，所述多个分频单元的一端分别耦合至所述可配置分频器的输入端，所述多个分频单元的另一端分别耦合至所述选择器的输入端，所述选择器的输出端耦合至所述可配置分频器的输出端，所述选择器用于接收所述控制信号，并在所述控制信号的控制下，选择所述多个分频单元中的一个分频单元导通，以实现选择性地在多个分频比中选择所述任 一接收通道的所述分频比。
结合第一方面第四种可能的实现方式，或者第五种可能的实施方式，或者第六种可能的实施方式，在第七种可能的实现方式中，所述射频接收机还包括：控制信号产生器，用于产生所述任一接收通道中的所述可配置分频器所需的控制信号。
结合第一方面，或者第一方面的第一种至第七种可能的实施方式中的任意一种的实施方式，在第八种可能的实现方式中，所述射频接收机还包括：基带处理器，用于对所述多个接收通道输出的基带信号进行基带处理。
结合第一方面，或者第一方面的第一种至第八种可能的实施方式中的任意一种的实施方式，在第九种可能的实现方式中，所述任一接收通道为零中频接收通道。
结合第一方面，或者第一方面的第一种至第九种可能的实施方式中的任意一种的实施方式，在第十种可能的实现方式中，所述多个频率综合器和所述多个接收通道集成在一个集成电路中。
第二方面，本发明实施例提供了一种接收方法，包括：
对所述射频信号进行频段分离，以得到至少一个频段信号并输出，其中，所述射频信号为多载波的载波聚合信号，每个频段信号上包括所述多载波中的至少一个载波；
分别对所述至少一个频段信号进行滤波和放大处理，以得到至少一个处理信号；
产生多个振荡信号；
选择性地从所述至少一个处理信号中接收包括目标载波的一个处理信号，以及从所述多个振荡信号中接收与所述目标载波对应的一个振荡信号，并选择性地在多个分频比中选择一个分频比，利用所述分频比对接收的所述振荡信号进行分频，得到本振信号，利用所述本振信号对接收的包括目标载波的所述处理信号进行混频，以得到一个混频信号，并基于所述混频信号，生成与所述目标载波对应的基带信号，所述目标载波为所述射频信号包括的多载波中的一个；
其中，通过分别选择分频比对所述多个振荡信号进行分频，抑制所述多个振荡信号之间的相互干扰。
在第二方面的第一种可能的实现方式中，所述多个分频比从包括多个整数分频比和多个小数分频比的集合中选择得到。
结合第二方面，或者第二方面的第一种可能的实现方式，在第二种可能的实现方式中，所述分别对所述至少一个频段信号进行滤波和放大处理，以得到至少一个处理信号，包括：
分别接收所述至少一个频段信号中的一个频段信号，并滤除所述一个频段信号的频段之外的信号，得到一个频段内的信号，对所述一个频段内的信号进行增益放大，以得到所述至少一个处理信号。
结合第二方面第二种可能的实现方式，在第三种可能的实现方式中，所述选择性地从所述至少一个处理信号中接收包括目标载波的一个处理信号，包括：
通过切换控制，以实现选择性地从所述至少一个处理信号中接收包括所述目标载波的所述处理信号。
结合第三方面，或者第一至第三种可能的实现方式中的任意一种可能的实现方式，在第四种可能的实现方式中，所述选择性地在多个分频比中选择一个分频比，利用所述分频比对接收的所述振荡信号进行分频，得到本振信号，包括：
接收控制信号，并在所述控制信号的控制下选择性地在所述多个分频比中选择所述分频比，并基于所述分频比对接收的所述振荡信号进行分频，得到所述本振信号。
本发明中，通过选择性选择各个接收通道各自的分频比，可以有效抑制各个接收通道所对应的多个频率综合器之间的相互干扰，从而使得本发明提供的的射频接收机可以实现单芯片集成。
附图说明
为了更清楚地说明本发明实施例或现有技术中的技术方案，下面将对实施例或现有技术描述中所需要使用的附图作简单地介绍，显而易见地，下面描述中的附图仅仅是本发明的一些实施例，对于本领域普通技术人员来讲，在不付出创造性劳动性的前提下，还可以根据这些附图获得其他的附图。
图1为典型的载波聚合的应用场景示意图；
图2为现有技术中的零中频接收机的架构图；
图3为本发明实施例一提供的一种射频接收机的架构图；
图4为本发明实施例一提供的一种射频接收机的电路图；
图5为本发明实施例一提供的另一种射频接收机的电路图；
图6A为本发明实施例一提供的一种可配置分频器的电路图；
图6B为本发明实施例一提供的另一种可配置分频器的电路图；
图7为本发明实施例一提供的又一种射频接收机的电路图；
图8A为基于图5所示的射频接收机接收跨频段不连续CA信号的示意图；
图8B为传统的射频接收机中两个VCO之间存在相互牵引的示意图；
图9A为基于图5所示的射频接收机接收频段内不连续CA信号的示意图；
图9B为传统的射频接收机中两个VCO之间存在杂散耦合串扰的示意图；
图10为基于图7所示的射频接收机接收跨频段不连续CA信号的示意图；
图11为基于图7所示的射频接收机接收另一种跨频段不连续CA信号的示意图；
图12为本发明实施例二提供的一种接收方法的流程图。
具体实施方式
为了便于更好的理解本发明的技术方案，首先对现有的零中频接收机做简单的介绍。图2所示为现有的零中频(zero intermediate frequency，ZIF)接收机的架构图。零中频接收机接收到的射频信号经放大后，与互为正交的两路本振信号混频，分别产生I(In-phase，同相)路，Q(Quadrature，正交)路两路基带信号。由于本振信号频率与射频信号频率相同，因此混频后直接产生基带信号，而信道选择和增益调整在基带上进行，由芯片上的低通滤波器和基带放大器完成。零中频接收机最吸引人之处在于下变频过程中不需经过中频，且镜像频率即是射频信号本身，不存在镜像频率干扰，相对超外差接收机而言，超外差接收机架构中采用的镜像抑制滤波器及中频滤波器均可省略。这样一方面取消了外部元件，有利于系统的单片集成，降低成本。另一方面系统所需的电路模块及外部节点数减少，降低了接收机所需的功耗并减少射频信号受外部干扰的机会。
下面将结合本发明实施例中的附图，对本发明实施例中的技术方案进行清楚地描述，显然，所描述的实施例仅仅是本发明一部分实施例，而不是全部的实施例。基于本发明中的实施例，本领域普通技术人员在没有作出创造性劳动前提下所获得的所有其他实施例，都属于本发明保护的范围。
实施例一
如图3所示，本发明实施例一提供了一种射频接收机，包括：
天线100，用于接收射频信号，例如，无线网络中的基站发射的射频信号，其中，所述射频信号为多载波的载波聚合信号，本领域技术人员应当知道，实际应用中，多载波的载波聚合方式包括频段内连续的载波聚合、频段内不连续的载波聚合、跨频段不连续的载波聚合中的至少一种，具体可以参见图1所示的几种典型的多载波聚合的方式。 本领域技术人员应当知道，当本发明实施例中的射频接收机集成在一个芯片中时，天线100通常不包括在该芯片内。
频段分离器(bandsplitter)200，所述频段分离器200的输入端耦合至所述天线100，用于接收所述天线100输出的所述射频信号，并对所述射频信号进行频段分离，以得到至少一个频段信号并输出，其中每个频段信号上包括所述多载波中的至少一个载波，需要说明的是，本实施例中的频段分离器200可以包括同向双工器(Diplexer，或称为收发共用器)，三工器(Triplexer)，四工器等等，具体采用那种器件跟多载波的CA信号中包括的频段数有关，例如：多载波的CA信号中包括三个频段信号时，就需要使用三工器来分离这三个频段信号；多载波的CA信号中包括两个频段信号时，使用Diplexer就可以分离这两个频段信号；此外，本领域技术人员应当知道，本发明实施例中所提及的耦合，其含义在本领域有通用解释，包括但不限于电学意义上的直接连接或间接连接，下文中与此类似，不再赘述；
本实施例中，频段分离器200可以根据多载波的载波聚合方式，对射频信号进行频段分离，具体地，若天线100接收的射频信号为多载波的跨频段CA信号，频段分离器200可以将该跨频段CA信号按照频段高低分成多个频段信号，例如：参见图8A，对于Band 8上的一个载波A(载频为935MHz)和Band 3上的一个载波B(载频为1870.1MHz)聚合的射频信号，频段分离器200可以相应的采用Diplexer，Diplexer可以将该射频信号分为高频段信号(即包括一个载波B的Band 3)和低频段信号(即包括一个载波A的Band 8)；若天线100接收的射频信号为频段内不连续CA信号或者频段内连续CA信号时，频段分离器200可以将频段内不连续CA或者频段内连续CA的多个载波分到一个频段信号中，例如：参见图9A，Band 25里面包括两个不连续的载波A和B，由于Diplexer的精度限制，无法将Band 25中聚合的载波分开，Diplexer在输出时，将会选择高频段输出和低频段输出中的一路输出一个包括载波A和载波B的频段信号(即Band 25)，需要说明的是，本文中所提及的Band 3，Band 8，Band 25等频段信号，其频段范围可以参考3GPP协议中相应的规定，这里不再详细说明。
处理电路300，所述处理电路300耦合至所述频段分离器200的输出端，用于分别对所述频段分离器200输出的所述至少一个频段信号进行滤波和放大处理，以得到至少一个处理信号。
多个频率综合器400，用于产生多个振荡信号，其中，多个振荡信号的频率各不相同。
多个接收通道500，所述多个接收通道500与所述多个频率综合器400一一对应，其中任一接收通道用于选择性地从所述处理电路300输出的所述至少一个处理信号中接收包括所述任一接收通道的目标载波的一个处理信号，以及从所述多个频率综合器400产生的所述多个振荡信号中接收与所述任一接收通道对应的一个频率综合器所产生的一个振荡信号，并选择性地在多个分频比中选择所述任一接收通道的分频比，利用所述分频比对接收的所述振荡信号进行分频，得到所述任一接收通道的本振信号，利用所述本振信号对接收的包括目标载波的所述处理信号进行混频，以得到一个混频信号，并基于所述混频信号，生成与所述目标载波对应的基带信号，所述目标载波为所述射频信号所包括的多载波中的一个；
其中，所述多个接收通道500分别通过选择各自的分频比，抑制所述多个频率综合器400之间的相互干扰；
需要说明的是，多个频率综合器之间的相互干扰主要包括：1、相互牵引，2、杂散耦合串扰，本实施例中，所述任一接收通道通过选择所述任一接收通道的分频比，使得所述任一接收通道对应的一个频率综合器所产生的振荡信号，与所述多个振荡信号中除所述任一接收通道对应的振荡信号之外的其它振荡信号之间的相互牵引效应减弱，即抑制了除所述任一接收通道对应的一个频率综合器之外的其它频率综合器对所述任一接收通道的牵引作用，以及使得所述任一接收通道对所述另一振荡信号的杂散分量分频后得到的信号，与所述任一接收通道的所述目标载波不存在重叠，即抑制了除所述任一接收通道对应的一个频率综合器之外的其它频率综合器所产生的振荡信号的杂散分量耦合到所述任一接收通道中时所造成的耦合串扰。
由此可见，采用本实施例的技术方案，有效地抑制了多个分频器之间的相互干扰，为了更好地说明本发明的技术效果，以下结合图8A和9A予以举例说明，如图8A所示，Band 8中的载波A和Band 3中的载波B跨频段聚合，载波A的载频为：FA＝1870.1MHz，载波B的载频为：FB＝935MHz；两个接收通道501A和501B各自的本振信号的频率分别为：LOA＝1870.1MHz，LOB＝935MHz；传统的解决方案中，如图8B所示，通常采用整数分频得到这两个本振信号，例如：对振荡信号(振荡频率FvcoA＝3740.2MHz)进行2分频得到LOA，对振荡信号(振荡频率FvcoB＝3740MHz)进行4分频得到LOB，由于FvcoA和FvcoB频率接近，若对应的两个频率综合器之间的隔离有限，将产生互相牵引，严重影响接收机性能，因此，本发明实施例中，通过将接收通道501A的分频比设置为2，将接收通道501B的分频比设置为3.5，则接收通道501A可以对振荡信号(振荡频率 FvcoA＝3740.2MHz)进行2分频得到LOA，接收通道501B可以对振荡信号(振荡频率FvcoB＝3272.5MHz)进行3.5分频得到LOB，从而使得FvcoA远离FvcoB，而频率综合器之间的相互牵引与振荡信号的振荡频率之间的差频，以及频率综合器之间的隔离度有关，差频越大、隔离度越好，则相互牵引的效应越弱，由此可见，通过灵活选择所述多个接收通道500各自的分频比，可以使得所述多个接收通道500对应的多个频率综合器400之间的相互牵引效应基本消失；如图9A所示，当接收的射频信号是Band 25内的载波A和载波B不连续CA时，载波A的载频为：FA＝1966.2MHz，载波B的载频为：FB＝1969.2MHz，则两个接收通道501A和501B各自的本振信号的本振频率分别为：LOA＝1966.2MHz，LOB＝1969.2MHz；传统的解决方案中，如图9B所示，通常采用整数分频得到这两个本振信号，例如：对振荡信号(振荡频率FvcoA＝3932.4MHz)进行2分频得到LOA，对振荡信号(振荡频率FvcoB＝3938.4MHz)进行2分频得到LOB，假设LOB对应的频率综合器采用19.2MHz的参考时钟源，则LOB中可能存在频率为Fspus＝1966.8MHz的杂散分量(boundary spur)，该杂散分量如果耦合到接收通道501A，与LOA混频得到Fspus-LOA＝0.6MHz的低频分量输出，假设载波A配置的频率是3MHz，则该0.6MHz的低频分量与接收通道501A要接收信号的频率重合，会严重影响载波A的接收性能，本实施例中，通过将接收通道501A的分频比设置为2，将接收通道501B的分频比设置为2.5，则接收通道501A可以对振荡信号(振荡频率FvcoA＝3932.4MHz)进行2分频得到LOA，接收通道501B可以对振荡信号(振荡频率FvcoB＝4923MHz)进行2.5分频得到LOB，从而使得FvcoA远离FvcoB，则接收通道501B分频后得到的LOB中不再存在可影响接收通道501A的接收性能的杂散分量，由此可见，通过灵活选择所述多个接收通道500各自的分频比，可以抑制所述多个接收通道500对应的多个频率综合器400之间的杂散耦合串扰。
本实施例中，所述任一接收通道的分频比的多个分频比可以从包括多个整数分频比和多个小数分频比的集合中选择得到，也就是说，所述多个分频比中可以包括：多个整数分频比和多个小数分频比中的至少两个分频比，即所述多个分频比可以是多个整数分频比的集合，或者是多个小数分频比的集合，或者是小数分频比和整数分频比的集合；本实施例中，由于提供了包括小数分频比和/或整数分频比在内的多个分频比，使得各个接收通道在选择各自的分频比，以抑制各个接收通道各自对应的频率综合器之间的相互干扰时，具有很强的灵活性。
以下结合图4所示的一种具体的射频接收机架构，对本发明实施例的技术方案做进一步地说明，需要说明的是，为了简便起见，图4只示例性给出了包括两个接收通道和两个频率综合器的接收机架构，实际应用中可以在图4的基础上对接收通道进行扩展，因此不能以图4的内容来限定本发明的保护范围。如图4所示，所述处理电路300中可以包括多个处理单元301，所述多个处理单元301的数量可以与频段分离器200的输出端的数量相等，所述多个处理单元301分别耦合至所述频段分离器200的各个输出端，其中每个处理单元301用于对频段分离器200输出的所述至少一个频段信号中的一个频段信号进行滤波和放大处理，以得到一个处理信号；仍然以图8A所示的接收机为例，当载波聚合信号是Band 8上的一个载波A和Band 3上的一个载波B跨频段聚合时，频段分离器200可以采用Diplexer，相应的，Diplexer有两个输出端：第一输出端和第二输出端，第一输出端用于输出高频段的频段信号，即载波B所在的频段信号(Band 3)，第二输出端用于输出低频段的频段信号，即载波A所在的频段信号(Band 8)，与之对应的所述处理电路300中也包括两个处理单元，其中一个处理单元耦合至第一输出端，用于对高频段信号(Band 3)进行滤波和放大处理，另一个处理单元耦合至第二输出端，用于对低频段信号(Band 8)进行滤波与放大处理；需要说明的是，在一种特殊情形中，即射频信号中只包括所述第一载波和所述第二载波，且所述第一载波和所述第二载波为频段内连续CA或者频段内不连续CA时，由于频段分离器200只输出一个频段信号，假设频段分离器200仍为Diplexer，则该频段信号可以由第一输出端或第二输出端输出，如果由第一输出端输出该频段信号时，则所述多个处理单元中，只有耦合到Diplexer的第一输出端的一个处理单元会对该频段信号进行处理，得到一个包括所述第一载波和所述第二载波的处理信号；
本实施例中，所述多个处理单元301中的任一处理单元301可以包括：带通滤波器3011和射频放大器3012，其中，带通滤波器3011的输入端耦合至频段分离器200的一个输出端，带通滤波器3011的输出端耦合至射频放大器3012的输入端，带通滤波器3011用于接收所述频段分离器200输出的所述至少一个频段信号中的一个频段信号，并滤除所述一个频段信号的频段之外的信号，得到一个频段内的信号；射频放大器3012用于接收带通滤波器3011滤波后得到的一个频段内信号，并对所述一个频段内信号进行增益放大，以得到一个处理信号；应当知道，所述多个处理单元的结构可以一样，只是为了处理不同频段的信号，各个处理单元中的带通滤波器允许通过的频率范围各不相同；此外，各种无线接收机的中前置的射频放大器，在放大微弱信号时，射频放大器自身的 噪声对信号的干扰可能很严重，为了减小这种噪声，以提高输出的信噪比，通常会选用低噪声放大器；对射频信号进行带通滤波以及增益放大，可以参考现有技术，此处不再详细说明。
本实施例中，如图4所示，所述射频接收机还可以包括：切换单元600，所述切换单元600耦合在所述多个处理单元301和所述多个接收通道500之间，所述切换单元600用于通过切换控制，使得所述任一接收通道选择性地耦合至所述处理电路300中的一个处理单元，以接收包括所述任一接收通道的目标载波的所述处理信号；具体地，请参见图5，图5所示的射频接收机中，所述多个接收通道500包括两个接收通道(为了描述方便，分别标示为501A和501B)，以及所述处理电路300包括两个处理单元(为了描述方便，分别标示为301A和301B)，则所述切换单元600具体可以包括：第一开关601，第二开关602，及第三开关603；其中，第一开关601的一端耦合至处理单元301A的输出端，第一开关601的另一端分别耦合至接收通道501A的射频输入端以及第二开关602的一端；第三开关603的一端耦合至处理单元301B的输出端，第三开关603的另一端分别耦合至接收通道501B的射频输入端以及第二开关602的另一端；切换单元600通过对这三个开关的通断进行控制，可以实现对不同类型的CA信号的接收，例如：当射频信号是Band3中的一个载波B和Band 8中的一个载波A跨频段CA时，参见图8A，可以同时控制第一开关601和第三开关603导通，控制第二开关602断开，从而使频段信号Band 3沿301A→601→501A的链路传输给接收通道501A，使频段信号Band 8沿301B→603→501B的链路传输给接收通道501B，其中，接收通道501A的目标载波为载波B，接收通道501B的目标载波为载波A；而当射频信号是频段信号Band 25内两个载波A和B不连续CA时，参见图9A，由于频段分离器200无法将一个频段内的多个载波分离开，频段分离器200只能选择一个输出端输出该频段信号，假设由处理单元301A对频段分离器200输出的Band 25进行滤波及放大处理，则通过同时控制第一开关601和第二开关602导通，控制第三开关603断开，使频段信号Band 25沿301A→601→501A的链路传输给频接收通道501A，同时沿着301A→601→602→501B的链路传输给频接收通道501B，其中，接收通道501A的目标载波为载波A，接收通道501B的目标载波为载波B；需要说明的是，图8A、8B、9A和9B中为了简便起见，省略了各个器件的编号，具体可以参考图5中的编号。
近一步地，在图5的基础上，结合图7，当射频接收机中包括三个处理单元(301A，301B，301C)，以及三个接收通道(501A，501B，501C)时，切换单元600还可以包括： 第四开关604，第五开关605，通过对这五个开关的导通进行控制，可以接收更多类型的CA信号，例如：当射频信号是Band 3中的载波A、Band 4中的载波B和Band 5中的载波C三个载波跨频段CA时，参见图10，切换单元通过同时控制第一开关601，第三开关603，第五开关605导通，并控制第二开关602和第四开关604断开，可以使Band5沿着301A→601→501A传输给接收通道501A，使Band 4沿着301B→603→501B传输给接收通道501B，使Band 3沿着301C→605→501C传输给接收通道501C，其中，接收通道501A的目标载波为载波C，接收通道501B的目标载波为载波B，接收通道501C的目标载波为载波A；而当射频信号是Band 3内的载波A和B不连续CA，再与Band 5内的载波C跨频段CA时，参见图11，假设由处理单元301B处理包括载波A和B在内的Band 3，则切换单元600可以同时控制第一开关601，第三开关603和第四开关604导通，控制第二开关602和第五开关605断开，则Band 5可以沿着301A→601→501A传输给接收通道501A，Band 3可以沿着301B→603→501B传输给接收通道501B，以及沿着301B→603→604→501C传输给接收通道501C，其中，接收通道501A的目标载波为载波C，接收通道501B的目标载波为载波B，接收通道501C的目标载波为载波A；需要说明的是，图10和11中为了简便起见，省略了各个器件的编号，具体可以参考图7中的编号。
综上，本实施例中，切换单元600通过切换控制，可以使所述多个接收通道500中的任一接收通道，从所述处理电路300处理后的至少一个处理信号中选择性地接收包括所述任一接收通道的目标载波的一个处理信号，同时，使得本实施例的射频接收机可以广泛适用于频段内连续CA，频段内不连续CA以及跨频段CA等多种应用场景，具有良好的兼容性。需要说明的是，本发明实施例中只是利用多个开关的组合来说明切换单元600的工作原理，实际应用中，本领域技术人员可以采用其他具有切换控制功能的电路或者芯片来实现相应的功能。
本实施例中，如图4所示，所述多个接收通道500中的任一接收通道具体可以包括：
可配置分频器5011，用于接收控制信号(control，CTRL)，并在所述控制信号的控制下选择性地在所述多个分频比中选择所述任一接收通道的分频比，并基于所述分频比对所述任一接收通道接收的所述振荡信号进行分频，得到所述本振信号；
混频器5012，用于利用所述本振信号对接收的所述处理信号进行混频得到混频信号；
低通滤波器5013，用于对所述混频信号进行噪声抑制；
基带放大器5014，用于对所述低通滤波器进行噪声抑制后的混频信号进行放大，以生成所述目标载波对应的基带信号。
更近一步地，如图6A所示，在一种可能的实施方式中，所述可配置分频器5011具体可以包括：多选一分频器50111，所述多选一分频器50111包括多种分频模式，其中每种分频模式对应一个整数分频比或小数分频比，例如，可以包括1分频、0.75分频、1.25分频、1.5分频、1.75分频和2分频等多个分频模式，所述多选一分频器用于接收所述控制信号CTRL，并在所述控制信号的控制下，将所述多种分频模式中的一种分频模式配置为当前工作模式，以实现选择性地在多个分频比中选择所述任一接收通道的所述分频比；
如图6B所示，在另一种可能的实施方式中，所述可配置分频器5011也可以包括：多个分频单元50121A和选择器50121B，其中每个分频单元对应一个整数分频比或小数分频比，所述多个分频单元50121A的一端分别耦合至所述可配置分频器5011的输入端，所述多个分频单元50121A的另一端分别耦合至所述选择器50121B的输入端，所述选择器50121B的输出端耦合至所述可配置分频器5011的输出端，所述选择器50121B用于接收所述控制信号CTRL，并在所述控制信号的控制下，选择所述多个分频单元中的一个分频单元导通，以实现选择性地在多个分频比中选择所述任一接收通道的所述分频比，其中，每个分频单元可以是具有分频能力的分频器件或者电路，例如，可以是1分频、2分频等整数分频器，或者是0.75分频、1.25分频、1.5分频和1.75分频等小数分频器，本实施例中对此不做限制；应当知道，本发明实施例中的可配置分频器5011。还可以是其他具有多种分频比的分频器件，或者是多个普通的分频器件组合成的具有多种分频比的电路或者芯片等，因此，不应以图6A和6B所示的具体电路结构限制本发明的保护范围。
本实施例中，进一步地，如图4所示，所述射频接收机还可以包括：控制信号产生器700，用于产生所述任一接收通道中的所述可配置分频器所需的控制信号，以便控制所述多个接收通道选择各自的分频比，进而抑制所述多个频率综合器之间的相互干扰。
由于零中频接收机在下变频过程中不需经过中频，且镜像频率即是射频信号本身，不存在镜像频率干扰，相对其他类型的接收机而言，可以省略镜像抑制滤波器及中频滤波器等器件，在低成本和单芯片集成方面具有显著的优势，因此，在本实施例中，所述多个接收通道500中的任一接收通道可以为零中频接收通道，以下结合图5对于零中频接收通道做简要说明，如图5所示，当所述任一接收通道为零中频接收通道时，所述混 频器5012，可以包括两个同相正交I/Q的同相混频器5012A和正交混频器5012B，用于分别接收包括所述任一接收通道的目标载波的处理信号，并利用相位差为90°的两个本振信号(LOI，LOQ)对接收的所述处理信号进行混频得到两个混频信号；低通滤波器5013，可以包括同相低通滤波器5013A和正交低通滤波器5013B，分别用于对同相混频器5012A和正交混频器5012B混频后得到的混频信号进行噪声抑制；基带放大器5014，可以包括同相基带放大器5014A和正交基带放大器5014B，分别用于对同相低通滤波器5013A和正交低通滤波器5013B进行噪声抑制后的混频信号进行放大，以生成所述目标载波对应的I/Q两路基带信号，应当知道，本领域技术人员对于零中频接收机的架构已有充分的研究，这里不再详细说明，具体可以参考在先技术；
进一步地，当所述任一接收通道为零中频接收通道时，如图6A和6B所示，所述可配置分频器还可以包括：多相滤波器(Poly-Phase Filter，PPF)50112，所述多相滤波器50112耦合在所述可配置分频器5011的输入端与所述多选一分频器50111的输入端之间，或者耦合在所述可配置分频器5011的输入端与所述多个分频单元50121A的输入端之间，用于对从所述任一接收通道对应的一个频率综合器401输入所述可配置分频器5011的振荡信号进行多相滤波，以产生具有一定相位差的多个振荡信号，以便所述多选一分频器50111或者所述多个分频单元50121A对多相滤波后的振荡信号进行分频，生成相位差为90°的本振信号LOI和LOQ，具体地，所述多相滤波器50112可以采用不同的时钟沿对分频信号进行相位延迟，以产生一定的相位差，其中，利用时钟沿实现相位延迟机理属于本领域技术人员的公知常识，可以参考在先技术，此处不再详细说明。
进一步地，如图6A和6B所示，所述可配置分频器5011中还可以包括：第六开关50113，第七开关50114，第一整数分频器50115，第二整数分频器50116，通过对第六开关50113和第七开关50114进行导通控制，可以利用所述第一整数分频器50115和所述第二整数分频器50116对所述多选一分频器50111或者所述选择器50121B输出的信号进一步分频，例如：假设第一整数分频器50115和第二整数分频器50116均为二分频器，如果同时控制第六开关50113导通及控制第七开关50114断开，则可以对所述多选一分频器50111或者所述选择器50121B输出的信号进行二分频；如果同时控制第六开关50113断开及控制第七开关50114导通，则可以对所述多选一分频器50111或者所述选择器50121B输出的信号进行四分频，因此，提高了可配置分频器5011在分频比配置上的灵活性，有利于拓展分频信号的宽度。
本实施例中，进一步地，如图4所示，所述射频接收机还可以包括：基带处理器800， 用于对所述多个接收通道500输出的基带信号进行基带处理，当接收通道为零中频接收通道时，则具体对I/Q两路基带信号进行基带处理，其中，基带处理器的工作原理可以参考在先技术，此处不再详述。
本实施例中，所述射频接收机为单芯片集成的射频接收机，即所述多个频率综合器400和所述多个接收通道500集成在一个集成电路中，当然，处理电路300和切换单元600，控制信号产生器700，例如，可以集成在一个射频芯片中，采用本发明实施例的技术方案，对于单芯片集成的包括多个频率综合器的射频接收机，可以有效抑制因为多个频率综合器的相互接近导致的相互干扰，相比传统的接收多载波CA信号的多芯片方案，本发明所提供的单芯片集成的射频接收机可以节省芯片面积，并降低成本，需要说明的是，以智能终端为例，基带处理器800通常是集成在与射频芯片相独立的主芯片中，本发明实施例中引入天线100和基带处理器800，是为了清楚地说明从接收射频信号到完成基带信号处理的完整过程。
实施例二
基于实施例一所述的射频接收机，如图12所示，本发明实施例还提供了一种接收多载波聚合的射频信号的方法，包括如下步骤：
S1、接收射频信号，所述射频信号为多载波的载波聚合信号；
S2、对所述射频信号进行频段分离，以得到至少一个频段信号并输出，其中每个频段信号上包括所述多载波中的至少一个载波；
S3、分别对所述至少一个频段信号进行滤波和放大处理，以得到至少一个处理信号；
S4、产生多个振荡信号；
S5、选择性地从所述至少一个处理信号中接收包括目标载波的一个处理信号，以及从所述多个振荡信号中接收与所述目标载波对应的一个振荡信号，并选择性地在多个分频比中选择一个分频比，利用所述分频比对接收的所述振荡信号进行分频，得到本振信号，利用所述本振信号对接收的包括目标载波的所述处理信号进行混频，以得到一个混频信号，并基于所述混频信号，生成与所述目标载波对应的基带信号，所述目标载波为所述射频信号包括的多载波中的一个；
其中，通过分别选择分频比对所述多个振荡信号进行分频，抑制所述多个振荡信号之间的相互干扰。
需要说明的是，在单芯片集成的射频接收机中，由多个频率综合器生成的多个振荡 信号之间的相互干扰主要包括：1、相互牵引，2、杂散耦合串扰，本发明实施例的射频接收机，通过分别选择分频比，使得对所述多个振荡信号中与目标载波相对应的一个振荡信号分频后得到的信号，与除所述与目标载波相对应的一个振荡信号外的其他振荡信号所对应的目标载波不存在重叠，以及使得对所述多个振荡信号中与目标载波相对应的一个振荡信号分频后得到的信号的杂散分量，与除所述与目标载波相对应的一个振荡信号外的其他振荡信号所对应的目标载波不存在重叠，即通过选择多个分频比对所述多个振荡信号进行分频，抑制了多个振荡信号之间的相互牵引以及杂散耦合串扰。
本实施例中，所述多个分频比从包括多个整数分频比和多个小数分频比的集合中选择得到，即所述多个分频比可以包括多个整数分频比和多个小数分频比中的至少两个分频比；由于提供了包括小数分频比和/或整数分频比在内的多个分频比，使得本发明实施例的射频接收机在接收射频信号时，各个接收通道可以更灵活地在选择各自的分频比，以抑制各个接收通道各自对应的频率综合器之间的相互干扰。
在S3中，分别对所述至少一个频段信号进行滤波和放大处理，以得到至少一个处理信号，具体可以包括：
分别接收所述至少一个频段信号中的一个频段信号，并滤除所述一个频段信号的频段之外的信号，得到一个频段内的信号，对所述一个频段内的信号进行增益放大，以得到所述至少一个处理信号。
进一步地，在S5中，所述选择性地从所述至少一个处理信号中接收包括目标载波的一个处理信号，可以包括：
通过切换控制，以实现选择性地从所述至少一个处理信号中接收包括所述任一接收通道的目标载波的所述处理信号。
在S5中，所述选择性地在多个分频比中选择一个分频比，利用所述分频比对接收的所述振荡信号进行分频，得到本振信号，可以包括：
接收控制信号，并在所述控制信号的控制下选择性地在所述多个分频比中选择所述分频比，并基于所述分频比对接收的所述振荡信号进行分频，得到所述本振信号。
需要说明的是，本发明实施例二是基于实施例一所提供的射频接收机的方法实现，因此，实施例一和实施例二中的相关特征可以相关参考。
应当理解，此处所描述的具体实施例仅为本发明的普通实施例而已，并不用以限制本发明，凡在本发明的精神和原则之内，所作的任何修改、等同替换、改进等，均应包含在本发明的保护范围之内。

Claims (16)

  1. 一种射频接收机，其特征在于，包括：
    频段分离器，所述频段分离器的输入端耦合至天线，用于从所述天线接收射频信号，并对所述射频信号进行频段分离，以得到至少一个频段信号并输出，其中所述射频信号为多载波的载波聚合信号，每个频段信号上包括所述多载波中的至少一个载波；
    处理电路，所述处理电路耦合至所述频段分离器的输出端，用于分别对所述至少一个频段信号进行滤波和放大处理，以得到至少一个处理信号；
    多个频率综合器，用于产生多个振荡信号；
    多个接收通道，所述多个接收通道与所述多个频率综合器一一对应，其中任一接收通道用于选择性地从所述处理电路输出的所述至少一个处理信号中接收包括所述任一接收通道的目标载波的一个处理信号，以及接收与所述任一接收通道对应的一个频率综合器所产生的振荡信号，并选择性地在多个分频比中选择所述任一接收通道的分频比，利用所述分频比对接收的所述振荡信号进行分频，得到所述任一接收通道的本振信号，利用所述本振信号对接收的包括目标载波的所述处理信号进行混频，以得到一个混频信号，并基于所述混频信号，生成与所述目标载波对应的基带信号，所述目标载波为所述射频信号包括的多载波中的一个；
    所述多个接收通道分别通过选择各自的分频比，抑制所述多个频率综合器之间的相互干扰。
  2. 如权利要求1所述的射频接收机，其特征在于，所述多个分频比从包括多个整数分频比和多个小数分频比的集合中选择得到。
  3. 如权利要求1或2所述的射频接收机，其特征在于，所述处理电路包括多个处理单元，所述多个处理单元与所述频段分离器的输出端一一对应，其中的任一处理单元包括：
    带通滤波器，用于接收所述频段分离器输出的所述至少一个频段信号中的一个频段信号，并滤除所述一个频段信号的频段之外的信号，得到一个频段内的信号；
    射频放大器，耦合至所述带通滤波器，用于接收所述一个频段内的信号，并对所述一个频段内的信号进行增益放大，以得到一个处理信号。
  4. 如权利要求3所述的射频接收机，其特征在于，所述射频接收机还包括：切换单元，所述切换单元耦合在所述多个处理单元和所述多个接收通道之间，所述切换单元用于通过切换控制，使得所述任一接收通道选择性地耦合至所述处理电路中的一个处理 单元，以接收包括所述任一接收通道的目标载波的所述处理信号。
  5. 如权利要求1至4任一所述的射频接收机，其特征在于，所述多个接收通道中的任一接收通道包括：
    可配置分频器，用于接收控制信号，并在所述控制信号的控制下选择性地在所述多个分频比中选择所述任一接收通道的分频比，并基于所述分频比对所述任一接收通道接收的所述振荡信号进行分频，得到所述本振信号；
    混频器，用于利用所述本振信号对接收的所述处理信号进行混频得到混频信号；
    低通滤波器，用于对所述混频信号进行噪声抑制；
    基带放大器，用于对所述低通滤波器进行噪声抑制后的混频信号进行放大，以生成所述目标载波对应的基带信号。
  6. 如权利要求5所述的射频接收机，其特征在于，所述可配置分频器包括：多选一分频器，所述多选一分频器包括多种分频模式，其中每种分频模式对应一个整数分频比或小数分频比，所述多选一分频器用于在所述控制信号的控制下，将所述多种分频模式中的一种分频模式配置为当前工作模式，以实现选择性地在多个分频比中选择所述任一接收通道的所述分频比。
  7. 如权利要求5所述的射频接收机，其特征在于，所述可配置分频器包括：多个分频单元和选择器，其中每个分频单元对应一个整数分频比或小数分频比，所述多个分频单元的一端分别耦合至所述可配置分频器的输入端，所述多个分频单元的另一端分别耦合至所述选择器的输入端，所述选择器的输出端耦合至所述可配置分频器的输出端，所述选择器用于接收所述控制信号，并在所述控制信号的控制下，选择所述多个分频单元中的一个分频单元导通，以实现选择性地在多个分频比中选择所述任一接收通道的所述分频比。
  8. 如权利要求5至7任一所述的射频接收机，其特征在于，所述射频接收机还包括：控制信号产生器，用于产生所述任一接收通道中的所述可配置分频器所需的控制信号。
  9. 如权利要求1至8任一所述的射频接收机，其特征在于，所述射频接收机还包括：基带处理器，用于对所述多个接收通道输出的基带信号进行基带处理。
  10. 如权利要求1至9任一所述的射频接收机，其特征在于，所述任一接收通道为零中频接收通道。
  11. 如权利要求1至10任一所述的射频接收机，其特征在于，所述多个频率综合 器和所述多个接收通道集成在一个集成电路中。
  12. 一种接收方法，其特征在于，包括：
    对射频信号进行频段分离，以得到至少一个频段信号并输出，其中，所述射频信号为多载波的载波聚合信号，每个频段信号上包括所述多载波中的至少一个载波；
    分别对所述至少一个频段信号进行滤波和放大处理，以得到至少一个处理信号；
    产生多个振荡信号；
    选择性地从所述至少一个处理信号中接收包括目标载波的一个处理信号，以及从所述多个振荡信号中接收与所述目标载波对应的一个振荡信号，并选择性地在多个分频比中选择一个分频比，利用所述分频比对接收的所述振荡信号进行分频，得到本振信号，利用所述本振信号对接收的包括目标载波的所述处理信号进行混频，以得到一个混频信号，并基于所述混频信号，生成与所述目标载波对应的基带信号，所述目标载波为所述射频信号包括的多载波中的一个；
    其中，通过分别选择分频比对所述多个振荡信号进行分频，抑制所述多个振荡信号之间的相互干扰。
  13. 如权利要求12所述的方法，其特征在于，所述多个分频比从包括多个整数分频比和多个小数分频比的集合中选择得到。
  14. 如权利要求12或13所述的方法，其特征在于，所述分别对所述至少一个频段信号进行滤波和放大处理，以得到至少一个处理信号，包括：
    分别接收所述至少一个频段信号中的一个频段信号，并滤除所述一个频段信号的频段之外的信号，得到一个频段内的信号，对所述一个频段内的信号进行增益放大，以得到所述至少一个处理信号。
  15. 如权利要求14所述的方法，其特征在于，所述选择性地从所述至少一个处理信号中接收包括目标载波的一个处理信号，包括：
    通过切换控制，以实现选择性地从所述至少一个处理信号中接收包括所述目标载波的所述处理信号。
  16. 如权利要求12至15任一所述的方法，其特征在于，所述选择性地在多个分频比中选择一个分频比，利用所述分频比对接收的所述振荡信号进行分频，得到本振信号，包括：
    接收控制信号，并在所述控制信号的控制下选择性地在所述多个分频比中选择所述分频比，并基于所述分频比对接收的所述振荡信号进行分频，得到所述本振信号。
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