WO2014141371A1 - Circuit de conversion de tension - Google Patents

Circuit de conversion de tension Download PDF

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Publication number
WO2014141371A1
WO2014141371A1 PCT/JP2013/056706 JP2013056706W WO2014141371A1 WO 2014141371 A1 WO2014141371 A1 WO 2014141371A1 JP 2013056706 W JP2013056706 W JP 2013056706W WO 2014141371 A1 WO2014141371 A1 WO 2014141371A1
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WO
WIPO (PCT)
Prior art keywords
reactor
winding
transformer
secondary winding
primary winding
Prior art date
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PCT/JP2013/056706
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English (en)
Japanese (ja)
Inventor
達也 北村
山田　正樹
原田　茂樹
Original Assignee
三菱電機株式会社
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Publication date
Application filed by 三菱電機株式会社 filed Critical 三菱電機株式会社
Priority to JP2015505112A priority Critical patent/JP6038282B2/ja
Priority to PCT/JP2013/056706 priority patent/WO2014141371A1/fr
Publication of WO2014141371A1 publication Critical patent/WO2014141371A1/fr

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1584—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/14—Arrangements for reducing ripples from dc input or output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0064—Magnetic structures combining different functions, e.g. storage, filtering or transformation
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1584—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel
    • H02M3/1586—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel switched with a phase shift, i.e. interleaved

Definitions

  • the present invention relates to a voltage conversion circuit.
  • This voltage converter circuit is a booster circuit (boost chopper) that releases magnetic energy stored in the reactor by arbitrarily adjusting and switching the switch element to obtain boosted voltage by obtaining an induced voltage. .
  • boost chopper In the above boost chopper, all the magnetic energy for boosting is stored in a single reactor, so that there is a problem that the reactor becomes very large in order to prevent magnetic saturation of the core.
  • Patent Document 2 a technique described in Patent Document 2 below has been proposed.
  • a transformer magnetically coupled to a magnetic component constituting a voltage conversion circuit is used, and magnetic saturation of the core is prevented while canceling out DC magnetization caused by DC current. The size is reduced.
  • Japanese Unexamined Patent Publication No. 2003-111390 5th page, FIG. 2
  • Japanese Patent No. 4098299 page 20, FIG. 2
  • the current ripple of the smoothing capacitor (hereinafter simply referred to as the capacitor current ripple) is equal to the current ripple of the reactor.
  • the reactor current ripple is uniquely determined, and therefore the capacitor current ripple is also determined.
  • the inductance of the reactor is determined due to restrictions on the capacitor current ripple, and there is a problem that the design of the reactor is restricted.
  • the present invention has been made to solve the above-described problems, and while reducing the magnetic saturation of the reactor, it is possible to increase the degree of freedom in designing the reactor and the transformer and to reduce the size of the device.
  • An object is to provide a voltage conversion circuit.
  • the voltage conversion circuit according to the present invention has a low voltage terminal, a high voltage terminal, and a reference terminal, a DC voltage between the low voltage terminal and the reference terminal, and between the high voltage terminal and the reference terminal.
  • a magnetic cancellation type transformer in which a primary winding and a secondary winding are magnetically coupled via a core and are reversely wound at a turns ratio of 1: 1.
  • a first reactor for energy storage that is connected to a first end of the primary winding of the transformer and is not shared as a winding of the primary winding; and a first of the secondary winding of the transformer
  • a second reactor for energy storage that is connected to the end and not shared as the winding of the secondary winding, a first switch element that controls energization from the primary winding to the reference terminal, and the primary Second switch element for controlling energization from the winding to the high voltage terminal
  • a third switch element for controlling energization from the secondary winding to the reference terminal, and a fourth switch element for controlling energization from the secondary winding to the high voltage terminal
  • Each inductance of the primary winding and the secondary winding of the transformer is set in a range of 1 to 10 times the inductance of the first reactor and the second reactor.
  • the reactor current ripple is determined by the combination of the inductance of the reactor and the transformer, and the inductance of the reactor is selected without being restricted by the reactor current ripple. can do.
  • the magnetic saturation of the reactor can be alleviated and the design freedom of the reactor and the transformer can be expanded, and each inductance is selected and designed so that the volume of the reactor and the transformer in the device is minimized. This makes it possible to reduce the size and cost of the device.
  • FIG. 9 is a circuit diagram showing a configuration of a voltage conversion circuit as a reference example of the present invention.
  • This voltage conversion circuit includes smoothing capacitors 5 and 6, a reactor 7, a transformer 8, and four switch elements 12, 14, 16 and 18.
  • a smoothing capacitor 5 is connected between the low voltage terminal 2 and the reference terminal (GND) 4, and a smoothing capacitor 6 is connected between the high voltage terminal 3 and the reference terminal 4.
  • a first end of a reactor 7 is connected to the low voltage terminal 2, and a pair of third and fourth T-type circuits connected in parallel to each other are connected between the second end of the reactor 7 and the high voltage terminal 3. Is provided.
  • the third T-type circuit includes the primary winding 9 of the transformer 8 and the two switch elements 12 and 14.
  • the fourth T-type circuit includes the secondary winding 10 of the transformer 8 and the two switch elements 16 and 18.
  • the reactor 7 is for accumulating magnetic energy for boosting.
  • the first ends of the primary winding 9 and the secondary winding 10 of the transformer 8 are connected to the reactor 7 in common.
  • the transformer 8 is of a magnetic canceling type in which the primary winding 9 and the secondary winding 10 are magnetically coupled via the core 11 and are reversely wound with each other at a turn ratio of 1: 1.
  • the collector and the emitter of the switch element 12 are connected between the primary winding 9 and the reference terminal 4, and the switch element 14 is connected between the primary winding 9 and the high voltage terminal 3.
  • the emitter and collector are connected.
  • the collector and the emitter of the switch element 16 are connected between the secondary winding 10 and the reference terminal 4, and between the secondary winding 10 and the high voltage terminal 3.
  • the emitter and collector of the switch element 18 are connected to each other.
  • diodes 13, 15, 17, and 19 are individually connected in parallel to the switch elements 12, 14, 16, and 18, respectively.
  • a gate signal for on / off control is applied to the gate of each switch element 12, 14, 16, 18 from a control device (not shown).
  • FIG. 10 shows the flow of current in each part of the voltage conversion circuit when only the switch element 12 of the third T-type circuit is turned on and the primary winding 9 of the transformer 8 is energized.
  • FIG. 12 shows the current flow in each part of the voltage conversion circuit when only the switch element 16 of the fourth T-type circuit is turned on and the secondary winding 10 of the transformer 8 is energized.
  • a low-level gate signal is input to each of the gates of the switch elements 14 and 18 and the switch element 16 and is turned off.
  • An on / off gate signal G12 is input to the gate of the switch element 12.
  • the excitation current I2 is generated in the secondary winding 10 based on the mutual induction action.
  • This excitation current I2 flows to the high voltage terminal 3 via the diode 19.
  • the excitation current I2 of the secondary winding 10 is substantially the same shape as the excitation currents I1 and I1 ′ as shown in FIG. And have substantially the same value based on the turns ratio (1: 1).
  • the smoothing capacitor 6 is charged by the excitation current I2 and the excitation current I1 '(broken line). As a result, the boosted DC voltage Vo is output to the high voltage terminal 3.
  • a low level gate signal is input to each of the gates of the switch elements 14 and 18 and the switch element 12 and is turned off.
  • An on / off gate signal G16 is input to the gate of the switch element 16.
  • the excitation current I4 is generated in the primary winding 9 based on the mutual induction action.
  • This excitation current I4 flows to the high voltage terminal 3 via the diode 15.
  • the excitation current I4 of the primary winding 9 is substantially the same shape as the excitation currents I3 and I3 ′. It has changing characteristics and occurs at substantially the same value based on the turns ratio (1: 1).
  • the smoothing capacitor 6 is charged by the excitation current I4 and the excitation current I3 '(broken line), and as a result, the boosted DC voltage Vo is output to the high voltage terminal 3.
  • the switching elements 12 and 16 are alternately turned on and off in a time-sharing manner by the gate signals G12 and G16 given from the control device (not shown), so that the high voltage terminal 3 is boosted, A stabilized DC voltage Vo is output.
  • the respective currents I1, I1 ′, I4 flowing through the primary winding 9 of the transformer 8 are collectively referred to as ic1, and the respective I2, I3, I3 ′ flowing through the secondary winding 10 are also described.
  • Is collectively represented as ic2 the reactor current ib flowing through the reactor 7 is the sum of the primary winding current ic1 and the secondary winding current ic2. Since the reactor current ib changes in the period Ton during which the switch elements 12 and 16 are on, assuming that the reactor current ripple generated in the reactor 7 is Ib, Ib is given by the following formula (1).
  • the following equation (2) is derived from the voltage equation of the path through which the primary winding current ic1 (I1) flows and the voltage equation of the path through which the secondary winding current ic2 (I2) flows. Is obtained.
  • the magnetic coupling degree of the transformer 8 is 1
  • the inductance of the primary winding 9 and the inductance of the secondary winding 10 are both equal
  • the inductance of the reactor 7 is Lb.
  • the reactor current ripple Ib is given by the following formula (4).
  • the reactor current ripple Ib represented by the equation (4) is equal to the capacitor current ripple of the smoothing capacitor 5.
  • the current directions of the primary winding 9 and the secondary winding 10 of the transformer 8 are opposite to each other. Since the core 11 is less likely to be magnetically saturated, a small winding (coil) can be employed, and the voltage conversion circuit can be downsized.
  • the inductance of the reactor 7 is determined when the step-up ratio is determined as shown in Equation (4).
  • the reactor current ripple Ib is uniquely determined by Lb, and therefore the capacitor current ripple is also determined.
  • FIG. 1 is a circuit diagram showing a configuration of a voltage conversion circuit according to Embodiment 1 of the present invention. Components corresponding to or corresponding to those of the voltage conversion circuit shown as the reference example in FIG. 9 are denoted by the same reference numerals.
  • the voltage conversion circuit of the first embodiment includes smoothing capacitors 5 and 6, two first and second reactors 21 and 22, a transformer 8, and four switch elements 12, 14, 16, and 18.
  • a smoothing capacitor 5 is connected between the low voltage terminal 2 and the reference terminal 4 (GND), and a smoothing capacitor 6 is connected between the high voltage terminal 3 and the reference terminal 4.
  • the first T-type circuit includes a first reactor 21, a primary winding 9 of the transformer 8, and two switch elements 12 and 14.
  • the second T-type circuit includes a second reactor 22, a secondary winding 10 of the transformer 8, and two switch elements 16 and 18.
  • the first and second reactors 21 and 22 are for accumulating magnetic energy for boosting, and the first ends of the first and second reactors 21 and 22 are common to the low voltage terminal 2. It is connected.
  • the transformer 8 is of a magnetic canceling type in which the primary winding 9 and the secondary winding 10 are magnetically coupled via the core 11 and are reversely wound with each other at a turn ratio of 1: 1.
  • each of the switch elements 12, 14, 16, and 18 is an IGBT (Insulated Gate Bipolar Transistor) here.
  • the second end of the first reactor 21 is connected to the connection terminal 28 on the first end side of the primary winding 9 of the transformer 8.
  • the collector and the emitter of the switch element 12 that controls energization from the primary winding 9 to the reference terminal 4 are connected.
  • the emitter-collector of the switch element 14 that controls energization from the primary winding 9 to the high voltage terminal 3 is connected. ing.
  • the second end of the second reactor 22 is connected to the connection terminal 29 on the first end side of the secondary winding 10 of the transformer 8.
  • the collector-emitter of the switch element 16 that controls energization from the secondary winding 10 to the reference terminal 4 is connected.
  • each switch element 12, 14, 16, 18 is individually connected to each diode 13, 15, 17, 19 in parallel thereto.
  • a gate signal for on / off control is given to a gate of each switch element 12, 14, 16, 18 from a control device (not shown).
  • Reference numeral 41 denotes a common connection point of the switch elements 12 and 14 of the first T-type circuit
  • reference numeral 42 denotes a common connection point of the switch elements 16 and 18 of the second T-type circuit.
  • the first reactor 21 is connected via the connection terminal 28 of the primary winding 9 of the transformer 8, and the second reactor 22 is connected to the secondary winding of the transformer 8.
  • 10 connection terminals 29 are connected.
  • each of the reactors 21 and 22 is not shared as a part of the primary winding 9 or the secondary winding 10 of the transformer 8, and is physically connected to each of the windings 9 and 10 of the transformer 8. In addition, it is divided into an independent structure.
  • the first switch element is the switch element 12
  • the second switch element is the switch element 14
  • the third switch element is the switch element 16
  • the fourth switch element is the switch element 18.
  • FIG. 2 shows the flow of current in each part of the voltage conversion circuit when only the switch element 12 of the first T-type circuit is turned on and the primary winding 9 of the transformer 8 is energized.
  • FIG. 3 shows a current flow in each part of the voltage conversion circuit when only the switch element 16 of the second T-type circuit is turned on and the secondary winding 10 of the transformer 8 is energized.
  • a low-level gate signal is input to each of the gates of the switch elements 14 and 18 and the switch element 16 and is turned off.
  • An on / off gate signal is input to the gate of the switch element 12.
  • the transformer 8 is turned on.
  • the exciting current I5 flows through the primary winding 9 of the first coil 9.
  • This exciting current I5 flows through the low voltage terminal 2, the first reactor 21, the primary winding 9, the switch element 12, and the reference terminal 4. While the gate signal of the switch element 12 is at the high level, the exciting current I5 gradually increases.
  • the excitation current I5 ' (indicated by a broken line in FIG. 2) decreases and finally becomes zero.
  • This exciting current I ⁇ b> 5 ′ flows to the high voltage terminal 3 through the first reactor 21, the primary winding 9, and the diode 15.
  • an excitation current I6 is generated in the secondary winding 10 based on the mutual induction action.
  • This excitation current I6 flows to the high voltage terminal 3 via the diode 19.
  • the excitation current I6 of the secondary winding 10 is substantially equal to the excitation currents I5 and I5 ′ as in the case shown in FIG. And have substantially the same value based on the turn ratio (1: 1).
  • the smoothing capacitor 6 is charged by the excitation current I6 and the excitation current I5 '. As a result, the boosted DC voltage Vo is output to the high voltage terminal 3.
  • a low-level gate signal is input to each of the gates of the switch elements 14 and 18 and the switch element 12 and is turned off.
  • An on / off gate signal is input to the gate of the switch element 16.
  • the excitation current I8 is generated in the primary winding 9 based on the mutual induction action.
  • This excitation current I8 flows to the high voltage terminal 3 via the diode 15.
  • the excitation current I8 of the primary winding 9 is substantially equal to the excitation currents I7 and I7 ′ as in the case shown in FIG. And have substantially the same value based on the turns ratio (1: 1).
  • the smoothing capacitor 6 is charged by the excitation current I8 and the excitation current I7 ', and as a result, the boosted DC voltage Vo is output to the high voltage terminal 3.
  • the switch elements 12 and 16 are alternately turned on and off in a time-sharing manner by the gate signal supplied from the control device (not shown), so that the high voltage terminal 3 is boosted and stabilized. DC voltage Vo is output.
  • the currents I5, I5 ′, I8 flowing through the primary winding 9 of the transformer 8 are collectively referred to as ic3, and the currents I6, I7, I7 ′ flowing through the secondary winding 10 are also described.
  • ic4 the current flowing through the first reactor 21 is equal to ic3
  • the current flowing through the second reactor 22 is equal to ic4.
  • the input current ie is divided into a current ic3 flowing through the primary winding 9 and a current ic4 flowing through the secondary winding 10.
  • the following equation (6) is derived from the voltage equation of the path through which the primary winding current ic3 (I5) flows and the voltage equation of the path through which the secondary winding current ic4 (I6) flows. Is obtained.
  • the magnetic coupling degree of the transformer 8 is 1
  • the inductance of the primary winding 9 and the inductance of the secondary winding 10 are both equal to Lc
  • the inductances of both reactors 21 and 22 are both equal to Ld.
  • Equation (6) when (dic3 / dt) and (dic4 / dt) are solved, the following Equation (7) is obtained.
  • Equation (8) the input current ripple Ie expressed by Equation (8) is equal to the capacitor current ripple of the smoothing capacitor 5.
  • Equation (8) shows that the input current ripple Ie according to the first embodiment, that is, the capacitor current ripple Ie, is the inductance Ld of the first and second reactors 21 and 22, the primary winding 9 and the secondary winding of the transformer 8. It is determined by the inductance Lc of the line 10.
  • FIG. 5 shows the result of examining how the volume of the entire device changes when the transformer 8 having the predetermined inductance Lc is provided from the state with reference to the volume.
  • the reactor volume the total volume of the first and second reactors 21 and 22 (hereinafter referred to as the reactor volume) is Vd
  • the volume of the transformer 8 (hereinafter referred to as the transformer volume) is Vc
  • the relationship of each volume of Vd, Vc, and Vl when the reactor volume Vd at the time is normalized as 10 is shown.
  • the device volume Vl increases.
  • the inductance ratio P when the inductance ratio P is increased, the device volume Vl takes a minimum value and then starts to increase. This is due to the fact that the decrease in the reactor volume Vd is slowed and the increase in the transformer volume Vc is increased.
  • the inductance ratio P was 10 when the device volume Vl reached the initial value of 10 again.
  • the apparatus volume Vl can be reduced to a minimum level of about 6 with respect to the initial value of 10, and thus is a more preferable selection range.
  • FIG. 5 shows the relationship between the device volume Vl and the inductance ratio P. Therefore, the inductance Ld of the first and second reactors 21 and 22 that provides the required capacitor current ripple Ie of the smoothing capacitor 5, the primary winding 9 of the transformer 8, while minimizing the device volume Vl as much as possible.
  • the value of the inductance Lc of the secondary winding 10 can be specifically determined. Thereby, since it becomes possible to perform optimal structure design with respect to the 1st, 2nd reactors 21 and 22 and the transformer 8, the effect that size reduction and cost reduction of a power converter device can be achieved compared with the past. Is obtained.
  • the first and second reactors 21 and 22 divided into two and the transformer 8 are arranged in combination, and the primary winding of the transformer 8 is arranged.
  • the inductance Lc of the wire 9 and the secondary winding 10 in the range of 1 to 10 times the inductance Ld of each reactor 21, 22, each reactor 21 and 22 can be relaxed while alleviating the magnetic saturation.
  • 22 and the design of the transformer 8 can be expanded, and the apparatus can be reduced in size and cost.
  • the present invention is not limited to the circuit configuration of the first embodiment shown in FIG. 1, and for example, as shown in FIG. 6, the primary winding 9 and both switch elements 12, It is good also as a structure which has arrange
  • FIG. Although not shown, the same effect as described above can be obtained even if the second reactor 22 is arranged between the secondary winding 10 of the transformer 8 and the common connection point 42 of both switch elements 16 and 18. It is done.
  • FIG. FIG. 7 is a circuit diagram showing a configuration of the voltage conversion circuit according to the second embodiment, and components corresponding to or corresponding to those in the circuit diagram of the first embodiment shown in FIG. 1 are denoted by the same reference numerals.
  • the features of the second embodiment are as follows. That is, the first ends of the primary winding 9 and the secondary winding 10 of the transformer 8 are made common and connected to the low voltage terminal 2 as one connection terminal 31, and the second end of the primary winding 9 is connected.
  • the first reactor 21 is disposed and connected between the end connection terminal 32 and the common connection point 41 of both switch elements 12, 14, the second end connection terminal 33 of the secondary winding 10 and both switches
  • the second reactor 22 is arranged and connected between the common connection points 42 of the elements 16 and 18. Other configurations are the same as those of the first embodiment shown in FIG.
  • Fig. 8 shows the structure of the transformer 8 in such a configuration.
  • a winding 34 is wound around a toroidal core 11, and a first end of a wire 35 is connected to the middle of the winding 34 via a tap 30.
  • Two ends serve as connection terminals 31 for connection to the low voltage terminal 2.
  • both ends of the winding 34 are a connection terminal 32 on the primary winding 9 side and a connection terminal 33 on the secondary winding 10 side, respectively.
  • the portion of the winding 34 from one connection terminal 32 to the intermediate tap 30 in FIG. 8 is the primary winding 9 in FIG. 7, and the portion of the winding 34 from the other connection terminal 33 to the intermediate tap 30 is It becomes the secondary winding 10 of FIG.
  • the connection terminal 31 is connected to the low voltage terminal 2 of FIG. 7, the connection terminal 32 on the primary winding 9 side is connected to the first end of the first reactor 21, and the connection terminal on the secondary winding 10 side. 33 is connected to the first end of the second reactor 22.
  • the primary winding 9 and the secondary winding 10 can be integrated and configured simply by winding the winding 34 around the core 11 of the transformer 8. Therefore, wiring connection points can be reduced, and the effect of simplifying the assembly process and improving production efficiency can be obtained. Moreover, since the primary winding 9 and the secondary winding 10 of the transformer 8 can be formed in one step, an effect of reducing the manufacturing cost can be obtained.
  • the operation as the voltage conversion circuit and the accompanying effects are all the same as in the first embodiment.
  • the shape of the core 11 of the transformer 8 in this Embodiment 2 is not limited to the toroidal, and it is needless to say that it can be applied to any shape as long as it has the same function in operation. Yes.
  • the IGBT is described as the switching elements 12, 14, 16, and 18 of the circuit configuration.
  • the present invention is not limited to this, and switching elements such as MOSFETs are used. It goes without saying that it can be done.
  • the coupling degree of the transformer 8 is described as 1.
  • the present invention is not limited to this, and the same effect can be obtained even in a circuit configuration having a coupling degree of 1 or less. Needless to say.
  • the case where the DC power source is connected between the low voltage terminal 2 and the reference terminal 4 to perform the step-up operation has been described as an example, but the step-down operation can be performed.
  • a DC power source is connected between the high voltage terminal 3 and the reference terminal 4, and the switch elements 12 and 16 are both turned off by a gate signal given from a control device (not shown).
  • the switch elements 14 and 18 are alternately turned on and off in a time division manner, whereby a stabilized DC voltage Vi stepped down to the low voltage terminal 2 is obtained.
  • the switch elements 12, 14, 16, 18 and the diodes 13, 15, 17, 19 of the circuit configuration are mainly composed of silicon (Si) such as IGBT and MOSFET. did.
  • the material of the wide band gap semiconductor can be composed of, for example, silicon carbide (SiC), a gallium nitride-based material, or diamond.
  • switch elements and diode elements formed of such wide band gap semiconductors have high voltage resistance and high allowable current density
  • the switch elements and diodes can be miniaturized.
  • a diode or a diode By using a diode or a diode, a semiconductor module incorporating these elements can be miniaturized.
  • silicon carbide (SiC) is applied as a material for the switch elements 12, 14, 16, 18 in particular.
  • Other configurations are the same as those of the first embodiment shown in FIG.
  • a switching element made of silicon carbide can suppress a switching loss smaller than a switching element made of silicon such as IGBT.
  • the switching frequency of the element can be increased.
  • the iron cores used in the reactors 21 and 22 and the transformer 8 generate a loss (iron loss) due to the ripple of current flowing through the windings, and the iron loss is higher as the ripple frequency is higher even with the same ripple amount. growing.
  • the frequency characteristics of iron cores differ depending on the material, and the iron loss that occurs even when the same ripple is applied differs. Furthermore, since the iron loss has a dependency relationship with the inductance, the relationship between the reactors 21 and 22, the iron core material of the transformer 8, and the inductances Lc and Ld is a factor that greatly affects the miniaturization of the voltage conversion circuit.
  • the first and second reactors 21 and 22 divided into two and the transformer 8 are arranged in combination, and the primary winding 9 and two of the transformer 8 are arranged.
  • the inductance Lc of the secondary winding 10 in the range of 1 to 10 times the inductance Ld of each of the reactors 21 and 22, in addition to being able to realize downsizing and cost reduction, silicon carbide
  • the switch elements 12, 14, 16, and 18 configured as described above at a high frequency, heat generation can be suppressed and the cooler can be made smaller. Therefore, the voltage conversion circuit can be further downsized than the case of the first embodiment. Cost reduction is possible. Since other operations and effects are the same as those of the first embodiment, detailed description thereof is omitted here.
  • the present invention is not limited to the configurations of the first to third embodiments described above, and the first to third embodiments can be freely combined or the embodiments can be implemented without departing from the spirit of the present invention.
  • the configurations of the first to third embodiments can be appropriately changed or omitted.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

La présente invention concerne un circuit de conversion de tension qui convertit la tension d'une alimentation électrique à courant continu connectée à une borne basse tension (2) ou à une borne haute tension (3), et qui comporte un transformateur de compensation magnétique (8) ayant un enroulement primaire (9) et un enroulement secondaire (10) qui sont reliés magnétiquement via un noyau (11) et qui sont bobinés en inverse selon un rapport de tours de 1 sur 1. Un premier et un second réacteur (21, 22) sont connectés individuellement à l'enroulement primaire (9) et à l'enroulement secondaire (10), mais ne sont pas partagés comme enroulements pour ceux-là. Le circuit de conversion de tension comprend en outre : un premier et un deuxième élément de commutation (12, 14) qui commandent l'alimentation électrique à partir de l'enroulement primaire (9) vers à la fois une borne de référence (4) et la borne haute tension (3) ; et un troisième et un quatrième élément de commutation (16, 18) qui commandent l'alimentation électrique à partir de l'enroulement secondaire (10) vers à la fois la borne de référence (4) et la borne haute tension (3). L'inductance (Lc) de l'enroulement primaire (9) et de l'enroulement secondaire (10) est établie dans une gamme faisant de 1 à 10 fois l'inductance (Ld) du premier et du second réacteur (21, 22).
PCT/JP2013/056706 2013-03-12 2013-03-12 Circuit de conversion de tension WO2014141371A1 (fr)

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JP2015505112A JP6038282B2 (ja) 2013-03-12 2013-03-12 電圧変換回路
PCT/JP2013/056706 WO2014141371A1 (fr) 2013-03-12 2013-03-12 Circuit de conversion de tension

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PCT/JP2013/056706 WO2014141371A1 (fr) 2013-03-12 2013-03-12 Circuit de conversion de tension

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WO2017212843A1 (fr) * 2016-06-10 2017-12-14 Ntn株式会社 Convertisseur continu-continu
EP3425783A4 (fr) * 2016-03-04 2019-04-03 Mitsubishi Electric Corporation Dispositif de conversion de puissance
US10541600B2 (en) 2016-06-10 2020-01-21 Ntn Corporation Power factor improvement device

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JP2005124302A (ja) * 2003-10-16 2005-05-12 Sumitomo Electric Ind Ltd 車載用電力変換装置
JP2006149054A (ja) * 2004-11-18 2006-06-08 Honda Motor Co Ltd Ｄｃ／ｄｃコンバータ
JP2008192931A (ja) * 2007-02-06 2008-08-21 Honda Motor Co Ltd 複合型トランスおよびそれを用いた昇降圧回路
JP2009273280A (ja) * 2008-05-09 2009-11-19 Hitachi Ltd Ｄｃ−ｄｃコンバータ
JP2011036086A (ja) * 2009-08-05 2011-02-17 Honda Motor Co Ltd Ｄｃ／ｄｃコンバータ及びそのｄｃ／ｄｃコンバータを備えた電力供給システム

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JP2005124302A (ja) * 2003-10-16 2005-05-12 Sumitomo Electric Ind Ltd 車載用電力変換装置
JP2006149054A (ja) * 2004-11-18 2006-06-08 Honda Motor Co Ltd Ｄｃ／ｄｃコンバータ
JP2008192931A (ja) * 2007-02-06 2008-08-21 Honda Motor Co Ltd 複合型トランスおよびそれを用いた昇降圧回路
JP2009273280A (ja) * 2008-05-09 2009-11-19 Hitachi Ltd Ｄｃ−ｄｃコンバータ
JP2011036086A (ja) * 2009-08-05 2011-02-17 Honda Motor Co Ltd Ｄｃ／ｄｃコンバータ及びそのｄｃ／ｄｃコンバータを備えた電力供給システム

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* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP3425783A4 (fr) * 2016-03-04 2019-04-03 Mitsubishi Electric Corporation Dispositif de conversion de puissance
US11245333B2 (en) 2016-03-04 2022-02-08 Mitsubishi Electric Corporation Power conversion device
WO2017212843A1 (fr) * 2016-06-10 2017-12-14 Ntn株式会社 Convertisseur continu-continu
CN109196765A (zh) * 2016-06-10 2019-01-11 Ntn株式会社 Dc/dc转换器
KR20190016479A (ko) * 2016-06-10 2019-02-18 엔티엔 가부시키가이샤 Dc/dc 컨버터
US10541600B2 (en) 2016-06-10 2020-01-21 Ntn Corporation Power factor improvement device
US10778095B2 (en) 2016-06-10 2020-09-15 Ntn Corporation Switching DC/DC converter having power output during on and off periods
CN109196765B (zh) * 2016-06-10 2021-08-24 Ntn株式会社 Dc/dc转换器
KR102399320B1 (ko) * 2016-06-10 2022-05-18 엔티엔 가부시키가이샤 Dc/dc 컨버터

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JP6038282B2 (ja) 2016-12-07

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