WO2014106488A1 - 一种自适应射频干扰抵消装置、方法以及接收机 - Google Patents

一种自适应射频干扰抵消装置、方法以及接收机 Download PDF

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Publication number
WO2014106488A1
WO2014106488A1 PCT/CN2014/070181 CN2014070181W WO2014106488A1 WO 2014106488 A1 WO2014106488 A1 WO 2014106488A1 CN 2014070181 W CN2014070181 W CN 2014070181W WO 2014106488 A1 WO2014106488 A1 WO 2014106488A1
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Prior art keywords
signal
radio frequency
amplitude
baseband
reference signal
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PCT/CN2014/070181
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English (en)
French (fr)
Inventor
陈特彦
杜颖钢
刘晟
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华为技术有限公司
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Priority to KR1020157021155A priority Critical patent/KR101690120B1/ko
Priority to EP14735172.0A priority patent/EP2933927B1/en
Publication of WO2014106488A1 publication Critical patent/WO2014106488A1/zh
Priority to US14/790,958 priority patent/US9270308B2/en

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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/06—Receivers
    • H04B1/10—Means associated with receiver for limiting or suppressing noise or interference
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/06—Receivers
    • H04B1/10—Means associated with receiver for limiting or suppressing noise or interference
    • H04B1/109—Means associated with receiver for limiting or suppressing noise or interference by improving strong signal performance of the receiver when strong unwanted signals are present at the receiver input
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/38—Transceivers, i.e. devices in which transmitter and receiver form a structural unit and in which at least one part is used for functions of transmitting and receiving
    • H04B1/40—Circuits
    • H04B1/50—Circuits using different frequencies for the two directions of communication
    • H04B1/52—Hybrid arrangements, i.e. arrangements for transition from single-path two-direction transmission to single-direction transmission on each of two paths or vice versa
    • H04B1/525—Hybrid arrangements, i.e. arrangements for transition from single-path two-direction transmission to single-direction transmission on each of two paths or vice versa with means for reducing leakage of transmitter signal into the receiver

Definitions

  • the present invention belongs to the technical field of wireless full duplex systems, and in particular, to an adaptive radio frequency interference canceling apparatus, method and receiver. Background technique
  • a wireless local area network such as a mobile cellular communication system
  • a wireless local area network such as a mobile cellular communication system
  • FWA fixed wireless access
  • BS base station
  • AP access point
  • Communication nodes such as Relay Station (RS) and User Equipment (UE) usually have the ability to transmit their own signals and receive signals from other communication nodes. Since the attenuation of the wireless signal in the wireless channel is very large, the signal from the communication peer arrives at the receiving end is very weak compared to its own transmitted signal. For example, the power difference between the transmitting and receiving signals of one communication node in the mobile cellular communication system is reached.
  • the transmission and reception of the wireless signal are usually distinguished by different frequency bands or time periods.
  • Frequency Division Duplex FDD
  • transmission and reception use different frequency bands separated by a certain guard band for communication.
  • Time Division Duplex TDD
  • transmission and reception are separated by a certain distance.
  • the different time periods of the protection interval are communicated, wherein the protection band in the FDD system and the protection time interval in the TDD system are both to ensure sufficient isolation between reception and transmission, and to avoid interference caused by transmission.
  • Wireless full-duplex technology differs from existing FDD or TDD technologies in that it can perform both receive and transmit operations on the same wireless channel.
  • the theoretical full-duplex wireless technology is twice as efficient as FDD or TDD.
  • the premise of implementing wireless full-duplex is to avoid, reduce and eliminate the strong interference of the transmitted signal of the same transceiver to the received signal as much as possible (called self-interference, Self-interference ) so that it does not affect the correct reception of useful signals.
  • the transmitter including a transmitting digital processor, an analog to digital converter, an upconverter, a power amplifier, and a transmitting antenna.
  • the receiver includes a receiving antenna, a radio frequency interference canceling device, a low noise amplifier (LNA), a down converter, an analog to digital converter, a digital interference canceling device, and a receiving digital processor, and the receiver receives
  • the radio frequency receiving signal includes a self-interference signal and a useful signal, and the strength of the self-interference signal is much greater than the strength of the useful signal, so the self-interference signal in the radio frequency receiving signal needs to be cancelled here, otherwise the receiver front end LNA is caused. Blocking of other modules.
  • the radio frequency interference cancellation device uses the radio frequency signal coupled after the transmitter power amplifier is amplified as a reference signal, and estimates the channel parameters of the local transmitting antenna to the receiving antenna, such as amplitude and phase, etc.
  • the reference signal is made as close as possible to the self-interfering signal component of the received signal, thereby canceling the local self-interfering signal received by the receiving antenna in the analog domain.
  • the radio frequency interference cancellation device in the existing receiver is mainly based on the method of Received S i gna l Strength Indica tor (RS I ), and correspondingly adjusts the radio frequency reference signal, including amplitude and phase, Then, the phase cancellation operation is performed with the RF receiving signal. As shown in FIG.
  • the structure of the existing RF interference canceling device based on RSSI detection is given, including amplitude phase adjustment module, subtractor, RSS I detection module, and amplitude and phase search processing.
  • the module, the RF reference signal is adjusted by the amplitude phase adjustment module, and the RF received signal is cancelled.
  • the cancelled RF residual signal is detected by the RSSI detection module, and the amplitude and phase search processing module processes the feedback RSSI by using the amplitude and phase search algorithm.
  • the detection result generates an amplitude phase control signal, adjusts the search step, and updates the amplitude and phase of the next adjustment.
  • the RSSI detection module can only obtain the absolute value of the adjustment search path, and the amplitude and phase search processing module also needs to search for the adjustment direction to determine the existing amplitude.
  • the phase is based on increasing or decreasing the corresponding step value.
  • the amplitude phase search algorithm has a slower convergence rate and is only applicable to the parameters to be adjusted. In less cases, due to slow convergence, it does not cause It can track the changes of parameters in time and affect the accuracy of their estimation. Summary of the invention
  • an object of the present invention is to provide an adaptive radio frequency interference canceling apparatus, method, receiver, and wireless full duplex communication system, aiming at solving the convergence speed of the existing self-interference cancellation search method based on RSSI detection. Slow, technical problem of inaccurate estimation of the amplitude and phase of the self-interfering signal relative to the RF reference signal.
  • the adaptive radio frequency interference device includes:
  • the amplitude phase adjustment module is configured to adjust the amplitude and phase of the RF reference signal, output the RF adjustment signal to the subtractor, so that the RF adjustment signal converges to the self-interference signal in the RF reception signal; and the subtracter is configured to receive the RF reception signal and the amplitude a radio frequency adjustment signal outputted by the phase adjustment module (1), and outputting a radio frequency residual signal, where the radio frequency residual signal is a difference signal between the radio frequency receiving signal and the radio frequency adjustment signal;
  • the baseband extraction filtering module is configured to receive the RF reference signal and the output RF residual signal of the subtractor, and extract the baseband signal, and the baseband signal is subjected to minimum mean square adaptive filtering to obtain an amplitude phase control signal and output to the amplitude phase adjustment.
  • the module, the amplitude phase control signal is used to control the amplitude phase adjustment module to adjust the amplitude and phase of the radio frequency reference signal.
  • the baseband extraction filtering module includes a first multiplier, a first low pass filter, a phase shifter, a second multiplier, a second low pass filter, and a minimum average
  • the square adaptive filtering processing module, the radio frequency reference signal is divided into two paths, wherein one of the channels and the radio frequency residual signal are mixed by the first multiplier, and the first baseband product signal is obtained through the first low pass filter, and the other radio frequency is obtained.
  • the RF residual signal is mixed by the second multiplier, and filtered by the second low pass filter to obtain a second baseband product signal, the first baseband product signal and After the second baseband product signal is connected to the minimum mean square adaptive filtering processing module, an amplitude phase control signal for controlling the amplitude phase adjustment module is generated.
  • the amplitude phase control signal is an adjustment coefficient signal
  • the amplitude phase adjustment module adjusts the amplitude and phase of the radio frequency reference signal according to the received adjustment coefficient signal.
  • the adaptive radio frequency interference cancellation method includes:
  • the radio frequency residual signal is a difference signal between the radio frequency receiving signal and the radio frequency adjustment signal
  • the receiving the radio frequency residual signal and the radio frequency reference signal and extracting a baseband signal, and performing the amplitude phase control by using the minimum mean square adaptive filtering process on the baseband signal specifically include:
  • the RF residual signal is mixed and low-pass filtered to obtain a second baseband product signal
  • an amplitude phase control signal is generated, and the amplitude phase control signal is used to control the amplitude and phase of the RF reference signal.
  • the receiver includes a receiving antenna, a low noise amplifier, a down converter, an analog to digital converter, a digital interference cancellation module, and a receiving digital signal processor, and the receiver further includes an adaptive radio frequency interference canceling device, a receiving antenna, an adaptive RF interference cancellation device, a low noise amplifier, a down converter, an analog to digital converter, a digital interference cancellation module, and a receiving digital signal processor are sequentially connected, and the adaptive RF interference cancellation device is further connected with The digital interference cancellation module is further connected to the digital reference signal from the transmitter.
  • the wireless full duplex communication system includes a transmitter and a receiver, and the transmitter includes a serially connected transmit digital processor, a digital to analog converter, an upconverter, a power amplifier, and a transmit antenna.
  • the power amplifier outputs a radio frequency reference signal to the adaptive radio frequency interference cancellation device of the receiver, and the digital reference signal output by the transmitting digital signal processor is coupled to the digital interference cancellation module of the receiver.
  • the invention adopts a radio frequency interference cancellation scheme based on Least t Mean Squares (LMS) adaptive filtering algorithm. Since the LMS adaptive filtering algorithm operates in the radio frequency simulation domain, direct sampling of high frequency radio frequency signals cannot be performed.
  • the algorithm can only be implemented on a digital baseband.
  • the baseband extraction filter module directly extracts the baseband signal from the radio frequency reference signal and the radio frequency residual signal, and then estimates the self-interference signal by the LMS adaptive filtering algorithm.
  • the amplitude and phase of the reference signal are generated to generate the amplitude phase control signal for the purpose of adjusting the amplitude and phase of the RF reference signal, so that it converges to the self-interference signal in the RF received signal, and the LMS adaptive filtering algorithm and the existing RSS I detection Compared with the algorithm, the convergence speed is faster and the estimation result is more accurate.
  • FIG. 1 is a structural diagram of a conventional wireless full duplex communication system
  • FIG. 2 is a structural diagram of an existing radio frequency interference canceling apparatus based on RSS I detection
  • FIG. 3 is a structural diagram of an adaptive radio frequency interference cancellation apparatus according to a first embodiment of the present invention
  • FIG. 4 is a structural diagram of an adaptive radio frequency interference cancellation apparatus according to a second embodiment of the present invention
  • FIG. 5 is an LMS adaptive filtering algorithm. Comparison of MSE performance with amplitude and phase search algorithm based on RSS I detection;
  • FIG. 6 is a flowchart of an adaptive radio frequency interference cancellation method according to a third embodiment of the present invention.
  • FIG. 7 is a flowchart of an adaptive radio frequency interference cancellation method according to a fourth embodiment of the present invention;
  • FIG. 8 is a fifth embodiment of the present invention. a structural diagram of a receiver provided by the example;
  • FIG. 9 is a structural diagram of a wireless full duplex communication system according to a sixth embodiment of the present invention. detailed description
  • Embodiment 1
  • FIG. 3 shows the structure of the adaptive radio frequency interference canceling apparatus provided by the first embodiment of the present invention, and only parts related to the embodiment of the present invention are shown for convenience of explanation.
  • the amplitude phase adjustment module 1 is configured to adjust the amplitude and phase of the radio frequency reference signal, output the radio frequency adjustment signal to the subtractor 2, so that the radio frequency adjustment signal converges to the self-interference signal in the radio frequency receiving signal; and the subtractor 2 is configured to receive the radio frequency receiving
  • the signal and the amplitude adjustment circuit 1 output the radio frequency adjustment signal, and output a radio frequency residual signal, where the radio frequency residual signal is a difference signal between the radio frequency receiving signal and the radio frequency adjustment signal;
  • the baseband extraction filtering module 3 is configured to receive the radio frequency reference signal and the output radio frequency residual signal of the subtractor 2, and extract the baseband signal, and the baseband signal is subjected to minimum mean square adaptive filtering to obtain an amplitude phase control signal and output to the amplitude.
  • the phase adjustment module 1 is configured to control the amplitude phase adjustment module 1 to adjust the amplitude and phase of the radio frequency reference signal.
  • the baseband extraction filtering module 3 receives the radio frequency reference signal and the radio frequency residual signal.
  • the baseband signal is extracted, and after the baseband signal is processed by the LMS adaptive filtering algorithm, an amplitude phase control signal is obtained, and then the amplitude phase control module 1 is controlled to complete the amplitude of the radio frequency reference signal according to the amplitude phase control signal.
  • the phase is gradually adjusted. After continuous iterative control, the RF reference signal converges to the self-interference signal in the RF received signal.
  • the LMS adaptive filtering algorithm has a faster convergence rate than the existing RSS I detection based algorithm. more acurrate.
  • FIG. 4 shows the structure of an adaptive radio frequency interference canceling apparatus according to a second embodiment of the present invention, and only parts related to the embodiment of the present invention are shown for convenience of explanation.
  • the adaptive radio frequency interference cancellation apparatus includes the amplitude phase adjustment module 1, the subtractor 2, and the baseband extraction and filtering module 3 as described in the first embodiment, as shown in FIG. 4, wherein the baseband extraction and filtering module 3 includes a first multiplier 31, a first low pass filter 32, a phase shifter 33, a second multiplier 34, a second low pass filter 35, and a minimum mean square adaptive filtering processing module 36, wherein the radio frequency reference signal is divided into two a path, wherein one of the channels and the radio frequency residual signal are mixed by the first multiplier 31, the first baseband product signal is obtained through the first low pass filter 32, and the other radio frequency reference signal is shifted to the 90 degree by the phase shifter 33.
  • radio frequency residual signal is mixed by the second multiplier 34, filtered by the second low pass filter 35 to obtain a second baseband product signal, and the first baseband product signal and the second baseband product signal are connected to the After the minimum mean square adaptive filtering processing module 36, an amplitude phase control signal for controlling the amplitude phase adjustment module 1 is generated.
  • This embodiment discloses a specific preferred structure of the baseband extraction and filtering module 3 on the basis of the first embodiment.
  • the product of the radio frequency reference signal X and the radio frequency residual signal ⁇ is used as the basis for amplitude and phase adjustment.
  • the RF reference signal X is divided into two paths, one of which is phase-shifted by 90°, and the two RF reference signals X are mixed with the RF residual signal ⁇ , and the baseband product of the two signals is obtained through a low-pass filter.
  • the LMS adaptive filtering algorithm is used to estimate the amplitude and phase of the self-interference signal relative to the reference signal, that is, the amplitude and phase adjustment coefficient W, and the corresponding amplitude phase adjustment of the RF reference signal X is completed, and the adjusted RF signal is again
  • the RF received signal d cancels out and obtains a new RF residual signal ⁇ .
  • X k U ref cos( «t) + Q ref ⁇ ) , - I ref ⁇ ) + Q ref cos( «t)] r , ( 1 ) where and / are respectively in-phase/orthogonal of baseband Signal (ie I / Q signal), "for carrier frequency Rate, T represents matrix transposition, / ⁇ cos ⁇ O + a ⁇ sin ⁇ O is the original signal of the RF reference signal, - / ⁇ sin O + O ⁇ cos O is phase shifted 90. RF reference signal.
  • RF receiving signal ⁇ can be expressed as
  • d k al ref cos( ⁇ yt + ⁇ ) + aQ ref ⁇ + ⁇ ) + n ⁇ t) ( ⁇ )
  • ⁇ and ⁇ are the estimated values of the amplitude and the phase at the kth sampling moment.
  • the equations (1), ( 2 ) and (3) are used to know the radio frequency residual signal.
  • the embodiment provides a specific baseband extraction mode.
  • the baseband signal on the transmitter side is known, considering that the nonlinear factor of the transmitter power amplifier affects the self-interference cancellation effect,
  • the amplified RF signal is usually used as the reference signal, that is, the RF reference signal described in this embodiment.
  • the RF residual signal and the RF reference signal need to be down-converted separately. Processing, however, this method needs to generate the local oscillator signal, which is complicated to implement, and introduces nonlinear factors such as I/Q imbalance, which affects the convergence speed of the algorithm and the accuracy of the estimation, but this embodiment does not need to perform down-conversion.
  • the minimum mean square adaptive filtering processing module can be performed at the baseband during the iterative process. It is beneficial to digital calculation and control, and achieves the purpose of controlling the convergence of RF reference signals. Since the embodiment does not need to perform down-conversion processing, the complexity of the implementation is reduced, and the influence of non-linear factors such as I/Q imbalance on the algorithm is also avoided.
  • Embodiment 3 is a diagrammatic representation of Embodiment 3
  • FIG. 6 shows a flow of an adaptive radio frequency interference cancellation method according to a third embodiment of the present invention, and only parts related to the embodiment of the present invention are shown for convenience of description.
  • the adaptive radio frequency interference cancellation method provided in this embodiment includes: Step S601, adjusting the amplitude and phase of the radio frequency reference signal, and outputting the radio frequency adjustment signal, so that the radio frequency adjustment signal converges to the self-interference signal in the radio frequency receiving signal;
  • Step S6G2 acquiring a radio frequency residual signal, where the radio frequency residual signal is a difference signal between the radio frequency receiving signal and the radio frequency adjustment signal;
  • Step S603 receiving the radio frequency residual signal and the radio frequency reference signal and extracting a baseband signal, and performing the minimum mean square adaptive filtering process to obtain an amplitude phase control signal, where the amplitude phase control signal is used to control and adjust the radio frequency.
  • the amplitude and phase of the reference signal are used to control and adjust the radio frequency.
  • the steps S 601 - S 603 described in this embodiment are implemented by the amplitude phase adjustment module 1, the subtractor 2 and the baseband extraction filter module 3 in the first embodiment.
  • the method of the embodiment constitutes a feedback loop, and the step is performed in step S603.
  • the baseband signal is extracted from the radio frequency residual signal and the radio frequency reference signal, and the amplitude phase control signal is obtained according to the LMS adaptive filtering algorithm to control and adjust the amplitude and phase of the radio frequency reference signal described in step S601, and then the next iteration is performed.
  • the radio frequency reference signal converges on the self-interference signal of the radio frequency received signal.
  • the LMS adaptive filtering algorithm is adopted, and the convergence speed is faster and the estimation result is more accurate than the existing RSSI detection-based algorithm.
  • FIG. 7 shows a flow of an adaptive radio frequency interference cancellation method according to a fourth embodiment of the present invention, and only parts related to the embodiment of the present invention are shown for convenience of description.
  • Step S701 adjusting the amplitude and phase of the radio frequency reference signal, and outputting the radio frequency adjustment signal, so that the radio frequency adjustment signal converges to the self-interference signal in the radio frequency receiving signal;
  • Step S702 Acquire a radio frequency residual signal, where the radio frequency residual signal is a difference signal between the radio frequency receiving signal and the radio frequency adjustment signal;
  • Step S703 dividing the radio frequency reference signal into two paths, wherein one of the channels and the radio frequency residual signal are mixed and low-pass filtered to obtain a first baseband product signal;
  • Step S704 after another radio frequency reference signal is moved by 90 degrees, and the radio frequency residual signal After mixing and low-pass filtering, a second baseband product signal is obtained;
  • Step S705 after the first baseband product signal and the second baseband product signal are subjected to minimum mean square adaptive filtering processing, generating an amplitude phase control signal, wherein the amplitude phase control signal is used to control and adjust the amplitude and phase of the radio frequency reference signal.
  • the above steps S703-S705 are a specific preferred step of the step S603 in the third embodiment.
  • the product of the radio frequency reference signal and the radio frequency residual signal is used as the basis for the amplitude and phase adjustment.
  • the radio frequency reference signal is divided into Two paths, one of which is phase-shifted by 90°, the two RF reference signals are mixed with the RF residual signal, and the baseband product of the two signals is obtained through a low-pass filter, and then the self-interference signal is estimated by the LMS adaptive filtering algorithm.
  • the amplitude and phase adjustment coefficients Relative to the amplitude and phase of the reference signal, that is, the amplitude and phase adjustment coefficients, the corresponding amplitude phase adjustment of the RF reference signal X is completed, and the adjusted RF signal is again cancelled by the RF receiving signal, and a new RF residual is obtained. Signal, go to the next iteration.
  • the RF residual signal and the RF reference signal need to be down-converted separately.
  • this method needs to generate the local oscillator signal, which is complicated to implement and introduces nonlinear factors such as I/Q imbalance.
  • the convergence speed and the accuracy of the estimation are affected, and the embodiment does not need to perform down-conversion processing, and directly divides the RF reference signal into two paths, one of which is phase shifted by 90.
  • the two RF reference signals are mixed with the RF residual signal, and then the harmonic components are all filtered out by low-pass filtering to obtain a baseband signal, so the minimum mean square adaptive filtering processing module can be performed at the baseband in the iterative process.
  • Embodiment 5 It is beneficial to digital calculation and control, and achieves the purpose of controlling the convergence of RF reference signals. Since the embodiment does not need to perform down-conversion processing, the complexity of the implementation is reduced, and the influence of nonlinear factors such as I/Q imbalance on the algorithm is also avoided. Embodiment 5:
  • Fig. 8 shows the structure of a receiver provided by a fifth embodiment of the present invention, and only parts related to the embodiment of the present invention are shown for convenience of explanation.
  • the receiver provided in this example includes a receiving antenna 41, a low noise amplifier 43, a down converter 44, An analog-to-digital converter 45, a digital interference cancellation module 46, and a receiving digital signal processor 47, and an adaptive radio frequency interference cancellation device 42 according to the first or second embodiment, the receiving antenna 41, and an adaptive radio frequency interference canceling device 42.
  • the low noise amplifier 43, the down converter 44, the analog to digital converter 45), the digital interference cancellation module 46, and the receiving digital signal processor 47 are sequentially connected, and the adaptive radio frequency interference cancellation device 42 is also connected to The radio frequency reference signal of the transmitter, the digital interference cancellation module 46 is also connected with a digital reference signal from the transmitter.
  • the radio frequency receiving signal received by the receiver of the embodiment includes the self-interference signal and the useful signal.
  • the adaptive radio frequency interference cancellation device 42 in this embodiment adopts the LMS adaptive filtering algorithm to implement the adjustment radio frequency reference.
  • the amplitude and phase of the signal cause the RF reference signal to converge to the self-interference signal in the RF received signal. Therefore, after convergence, the adaptive RF interference canceling device 42 outputs a useful signal to complete the self-interference cancellation operation.
  • the adaptive radio frequency interference cancellation device 42 adopts the LMS adaptive filtering algorithm, and the amplitude and phase search algorithm based on the RSSI detection used by the existing radio frequency interference cancellation module is Ratio, convergence is faster, and the estimation result is more accurate.
  • Example 6 Example 6:
  • Fig. 9 shows the structure of a wireless full duplex communication system according to a sixth embodiment of the present invention, and only parts related to the embodiment of the present invention are shown for convenience of explanation.
  • the wireless full duplex communication system includes a transmitter 50 and a receiver 40 as described in Embodiment 5, the transmitter including a serially connected transmit digital processor 51, a digital to analog converter 52, and upconversion.
  • the power amplifier 54 outputs a radio frequency reference signal to the adaptive radio frequency interference canceling device 42 of the receiver, and the digital reference signal output by the transmitting digital signal processor 51 is connected.
  • the digital interference cancellation module 46 is input to the receiver.
  • the wireless full duplex communication system provided by this embodiment is composed of a transmitter 50 and a receiver 40, wherein the adaptive radio frequency interference cancellation device 42 in the receiver 40 adopts an LMS adaptive filtering algorithm, but in the existing receiver
  • the amplitude and phase search algorithm based on RSSI detection used by the RF interference cancellation module The receiver in this embodiment converges faster and the estimation result is more accurate.
  • all or part of the steps of the foregoing embodiments may be implemented by a program to instruct related hardware, and the program may be stored in a computer readable storage medium. Storage media, such as ROM/RAM, disk, CD, etc.

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Abstract

本发明适用于移动通信技术领域，提供一种自适应射频干扰抵消装置、方法、接收机以及无线全双工通信系统，所述装置包括：幅度相位调整模块，用于调整射频参考信号的幅度和相位，输出射频调整信号，使得射频调整信号收敛于射频接收信号中的自干扰信号；减法器，用于输出射频残余信号，所述射频残余信号为射频接收信号与射频参考信号的差值信号；基带提取滤波模块，用于接收射频参考信号以及减法器输出射频残余信号，并提取出基带信号，将所述基带信号经最小均方自适应滤波处理后得到幅度相位控制信号并输出至幅度相位调整模块。本发明采用了LMS自适应滤波算法，收敛速度更快，估算结果更准确。

Description

一种自适应射频干扰抵消装置、 方法以及接收机
技术领域
本发明属于无线全双工系统技术领域， 尤其涉及一种自适应射频干扰抵 消装置、 方法以及接收机。 背景技术
在移动蜂窝通信系统、无线局域网（Wireless Local Area Network, WLAN ), 固定无线接入（Fixed Wireless Access, FWA )等无线通信系统中，基站（Base Station, BS )或接入点 ( Access Point, AP ) 、 中继站（ Relay Station, RS ) 以及用户设备 (User Equipment, UE )等通信节点通常具有发射自身信号和 接收其它通信节点信号的能力。 由于无线信号在无线信道中的衰减非常大， 与自身的发射信号相比， 来自通信对端的信号到达接收端时信号已非常微弱， 例如， 移动蜂窝通信系统中一个通信节点的收发信号功率差达到 80dB_140dB 甚至更大， 因此， 为了避免同一收发信机的发射信号对接收信号的干扰， 无 线信号的发送和接收通常采用不同的频段或时间段加以区分。 例如， 在频分 双工 ( Frequency Division Duplex, FDD ) 中， 发送和接收使用相隔一定保 护频带的不同频段进行通信， 在时分双工（ Time Division Duplex, TDD )中， 发送和接收则使用相隔一定保护时间间隔的不同时间段进行通信， 其中， FDD 系统中的保护频带和 TDD 系统中的保护时间间隔都是为了保证接收和发送之 间充分地隔离， 避免发送对接收造成干扰。
无线全双工技术不同于现有的 FDD或 TDD技术， 可以在相同无线信道 上同时进行接收与发送操作， 这样， 理论上无线全双工技术的频谱效率是 FDD 或 TDD技术的两倍。 显然， 实现无线全双工的前提在于尽可能地避免、 降低 与消除同一收发信机的发射信号对接收信号的强干扰 （称为自干扰， Self-interference ) , 使之不对有用信号的正确接收造成影响。
图 1 示出了现有的无线全双工通信系统的结构， 包括发送机和接收机， 所述发送机包括发射数字处理器、 模数转换器、 上变频器、 功率放大器以及 发送天线，所述接收机包括接收天线、射频干扰抵消装置、低噪声放大器（Low Noi se Ampl if ier , LNA ) 、 下变频器、 模数转换器、 数字干扰抵消装置以及 接收数字处理器， 接收机接收到的射频接收信号中包括有自干扰信号和有用 信号， 且所述自干扰信号的强度远大于所述有用信号的强度， 因此这里需要 抵消射频接收信号中的自干扰信号， 否则会造成接收机前端 LNA等模块的阻 塞。 因此， 在现有技术中， 在 LNA之前， 射频干扰抵消装置将从发送机功率 放大器放大之后耦合的射频信号作为参考信号， 估计本地发射天线到接收天 线的信道参数， 如幅度与相位等， 调节参考信号使之尽可能地接近接收信号 中的自干扰信号成份， 从而在模拟域抵消接收天线收到的本地自干扰信号。 具体的， 现有接收机中的射频干扰抵消装置主要是基于接收信号强度检测 ( Received S i gna l Strength Indica tor , RSS I ) 的方法， 对射频参考信号 进行相应调整， 包括幅度和相位等， 然后和射频接收信号进行相抵消操作， 如图 2所示， 给出了现有基于 RSSI检测的射频干扰抵消装置的结构， 包括幅 度相位调整模块、 减法器、 RSS I检测模块、 幅相搜索处理模块， 射频参考信 号在经过幅度相位调整模块调整后， 会与射频接收信号进行抵消， 抵消后的 射频残余信号将通过 RSSI检测模块检测， 幅相搜索处理模块利用幅相搜索算 法处理反馈回来的 RSSI检测结果， 生成幅度相位控制信号， 对搜索的步径进 行调整， 并更新下一次调整的幅度和相位。
但是现有的这种基于 RSSI检测的自干扰抵消方法， RSSI检测模块只能得 到调整搜索步径的绝度值， 幅相搜索处理模块还需要对调整的方向进行搜索， 确定出在现有幅度和相位的基础上是增加还是减小相应步径值， 在这里需要 同时搜索确定出幅度和相位的方向， 因而这种幅度相位搜索算法的收敛速度 较慢， 而且只适用于需调整的参数较少的情况， 由于收敛速度慢， 导致其不 能及时跟踪参数的变化， 影响其估算的精确度。 发明内容
鉴于上述问题， 本发明的目的在于提供一种自适应射频干扰抵消装置、 方法、 接收机以及无线全双工通信系统， 旨在解决现有基于 RSSI检测的自干 扰抵消搜索方法中存在着收敛速度慢、 对自干扰信号相对于射频参考信号的 幅度和相位估算不精确的技术问题。
第一方面， 所述自适应射频干扰 ·!氏消装置包括：
幅度相位调整模块， 用于调整射频参考信号的幅度和相位， 输出射频调 整信号至减法器， 使得射频调整信号收敛于射频接收信号中的自干扰信号； 减法器， 用于接收射频接收信号以及幅度相位调整模块 ( 1 )输出的射频 调整信号， 并输出射频残余信号， 所述射频残余信号为所述射频接收信号与 射频调整信号的差值信号；
基带提取滤波模块， 用于接收射频参考信号以及减法器输出射频残余信 号， 并提取出基带信号， 将所述基带信号经最小均方自适应滤波处理后得到 幅度相位控制信号并输出至幅度相位调整模块， 所述幅度相位控制信号用于 控制幅度相位调整模块调整射频参考信号的幅度和相位。
在第一方面的第一种可能的实现方式， 所述基带提取滤波模块包括第一 乘法器、 第一低通滤波器、 移相器、 第二乘法器、 第二低通滤波器以及最小 均方自适应滤波处理模块， 所述射频参考信号分成两路， 其中一路与所述射 频残余信号通过第一乘法器混频后， 经过第一低通滤波器得到第一基带乘积 信号， 另一路射频参考信号经过移相器移向 90度后， 与所述射频残余信号通 过第二乘法器混频， 经过第二低通滤波器滤波后得到第二基带乘积信号， 所 述第一基带乘积信号和第二基带乘积信号接入到所述最小均方自适应滤波处 理模块后， 生成用于控制幅度相位调整模块的幅度相位控制信号。
结合第一方面的第一种可能的实现方式， 在第二种可能的实现方式中， 所述幅度相位控制信号为调整系数信号， 所述幅度相位调整模块根据接收到 的调整系数信号调整所述射频参考信号的幅度和相位
第二方面， 所述自适应射频干扰 ·!氏消方法包括：
调整射频参考信号的幅度和相位， 输出射频调整信号， 使得射频调整信 号收敛于射频接收信号中的自干扰信号；
获取射频残余信号 , 所述射频残余信号为射频接收信号与射频调整信号 的差值信号；
接收所述射频残余信号和射频参考信号并提取出基带信号， 将所述基带 信号经最小均方自适应滤波处理后得到幅度相位控制信号， 所述幅度相位控 制信号用于控制调整射频参考信号的幅度和相位。
在第二方面的第一种可能的实现方式中， 所述接收所述射频残余信号和 射频参考信号并提取出基带信号， 将所述基带信号经最小均方自适应滤波处 理后得到幅度相位控制信号步骤， 具体包括：
将所述射频参考信号分成两路， 其中一路与所述射频残余信号经过混频、 低通滤波后得到第一基带乘积信号；
另一路射频参考信号经过 90度移向后， 与所述射频残余信号经过混频、 低通滤波后得到第二基带乘积信号；
将所述第一基带乘积信号和第二基带乘积信号经过最小均方自适应滤波 处理后， 生成幅度相位控制信号， 所述幅度相位控制信号用于控制调整射频 参考信号的幅度和相位。
第三方面， 所述接收机包括接收天线、 低噪声放大器、 下变频器、 模数 转换器、 数字干扰抵消模块以及接收数字信号处理器， 所述接收机还自适应 射频干扰抵消装置， 所述接收天线、 自适应射频干扰抵消装置、 低噪声放大 器、 下变频器、 模数转换器、 数字干扰抵消模块以及接收数字信号处理器顺 次连接， 所述自适应射频干扰抵消装置还接入有来自于发送机的射频参考信 号， 所述数字干扰抵消模块还接入有来自于发送机的数字参考信号。 第四方面， 所述无线全双工通信系统包括发送机和上述接收机， 所述发 送机包括顺次连接的发射数字处理器、 数模转换器、 上变频器、 功率放大器 以及发射天线， 所述功率放大器输出射频参考信号接入到所述接收机的自适 应射频干扰抵消装置， 所述发射数字信号处理器输出的数字参考信号接入到 所述接收机的数字干扰抵消模块。
本发明采用的是基于最小均方 （Leas t Mean Squares , LMS ) 自适应滤波 算法的射频干扰抵消方案， 由于 LMS 自适应滤波算法是在射频模拟域操作， 无法对高频率的射频信号进行直接采样， 该算法一般只能在数字基带上实现， 为此本发明中， 基带提取滤波模块直接从射频参考信号和射频残余信号中提 取出基带信号， 再通过 LMS 自适应滤波算法估算出自干扰信号相对于参考信 号的幅度和相位， 生成幅度相位控制信号到达调整射频参考信号的幅度和相 位的目的，使之收敛于射频接收信号中的自干扰信号， LMS自适应滤波算法与 现有的基于 RSS I检测的算法相比， 收敛速度更快， 估算结果更准确。 附图说明
图 1是现有无线全双工通信系统的结构图；
图 2是现有基于 RSS I检测的射频干扰抵消装置的结构图；
图 3是本发明第一实施例提供的自适应射频干扰抵消装置的结构图； 图 4是本发明第二实施例提供的自适应射频干扰抵消装置的结构图； 图 5是 LMS 自适应滤波算法与基于 RSS I检测的幅相搜索算法的 MSE性能 对比图；
图 6是本发明第三实施例提供的自适应射频干扰抵消方法的流程图； 图 7是本发明第四实施例提供的自适应射频干扰抵消方法的流程图； 图 8是本发明第五实施例提供的接收机的结构图；
图 9是本发明第六实施例提供的无线全双工通信系统的结构图。 具体实施方式
为了使本发明的目的、 技术方案及优点更加清楚明白， 以下结合附图及 实施例， 对本发明进行进一步详细说明。 应当理解， 此处所描述的具体实施 例仅仅用以解释本发明， 并不用于限定本发明。
为了说明本发明所述的技术方案， 下面通过具体实施例来进行说明。 实施例一：
图 3 示出了本发明第一实施例提供的自适应射频干扰抵消装置的结构， 为了便于说明仅示出了与本发明实施例相关的部分。
本实施例提供的自适应射频干扰抵消装置包括：
幅度相位调整模块 1 , 用于调整射频参考信号的幅度和相位，输出射频调 整信号至减法器 2 , 使得射频调整信号收敛于射频接收信号中的自干扰信号； 减法器 2 ,用于接收射频接收信号以及幅度相位调整模块 1输出的射频调 整信号， 并输出射频残余信号， 所述射频残余信号为所述射频接收信号与射 频调整信号的差值信号；
基带提取滤波模块 3 ,用于接收射频参考信号以及减法器 2输出射频残余 信号， 并提取出基带信号， 将所述基带信号经最小均方自适应滤波处理后得 到幅度相位控制信号并输出至幅度相位调整模块 1 ,所述幅度相位控制信号用 于控制幅度相位调整模块 1调整射频参考信号的幅度和相位。
为了能够将 LMS 自适应滤波算法应用到本实施例中， 由于 LMS 自适应滤 波算法无法对高频率的射频信号进行直接采样， 因此本实施中， 基带提取滤 波模块 3从射频参考信号和射频残余信号中， 提取出基带信号， 在对所述基 带信号经 LMS 自适应滤波算法处理后， 得到幅度相位控制信号， 再根据所述 幅度相位控制信号控制幅度相位调整模块 1 完成对射频参考信号的幅度和相 位进行逐步调整， 经过不断迭代控制， 使得射频参考信号收敛于射频接收信 号中的自干扰信号， LMS自适应滤波算法与现有的基于 RSS I检测的算法相比， 收敛速度更快， 估算结果更准确。 实施例二：
图 4 示出了本发明第二实施例提供的自适应射频干扰抵消装置的结构， 为了便于说明仅示出了与本发明实施例相关的部分。
本实施例提供的自适应射频干扰抵消装置包括如实施例一所述的幅度相 位调整模块 1、 减法器 2和基带提取滤波模块 3 , 如图 4所示， 其中所述基带 提取滤波模块 3包括第一乘法器 31、 第一低通滤波器 32、 移相器 33、 第二乘 法器 34、 第二低通滤波器 35以及最小均方自适应滤波处理模块 36 , 所述射 频参考信号分成两路， 其中一路与所述射频残余信号通过第一乘法器 31混频 后， 经过第一低通滤波器 32得到第一基带乘积信号， 另一路射频参考信号经 过移相器 33移向 90度后， 与所述射频残余信号通过第二乘法器 34混频， 经 过第二低通滤波器 35滤波后得到第二基带乘积信号， 所述第一基带乘积信号 和第二基带乘积信号接入到所述最小均方自适应滤波处理模块 36后， 生成用 于控制幅度相位调整模块 1的幅度相位控制信号。
本实施例在实施例一的基础上公开了基带提取滤波模块 3 的一种具体优 选的结构， 在本实施例中， 以射频参考信号 X和射频残余信号 ε的乘积作为 幅相调整的依据，具体的，将射频参考信号 X分成两路，其中一路移相 90° , 两路射频参考信号 X再与射频残余信号 ε进行混频， 并通过低通滤波器得到 这两个信号的基带乘积， 然后利用 LMS 自适应滤波算法估算出自干扰信号相 对于参考信号的幅度和相位， 即幅度和相位的调整系数 W, 完成对射频参考信 号 X进行相应的幅度相位调整，经过调整后的射频信号再次与射频接收信号 d 相抵消， 并获得新的射频残余信号 ε 。
在上述技术方案中， 假设当前准备进行第 k次迭代， 即在第 k个采样时 刻， 这里用 来表示射频参考信号向量， 即
Xk = Uref cos(«t) + Qref ύη{ωί) , - Iref ήη{ωί) + Qref cos(«t)]r , ( 1 ) 其中 和 /分别为基带的同相 /正交信号 （即 I /Q信号） ， 《为载波频 率， T 表示矩阵转置， /^cos^O + a^sin^O为射频参考信号的原信号， - /^sin O + O^cos O为经移相 90。 的射频参考信号。
射频接收信号 ^可以表达为
dk = alref cos(<yt + φ) + aQref ύη{ωί + φ) + n{t) ( ^ )
=acosO)[/re cosOt) + Qref sin(<yt)] + sin(^)[-/re/ sin(<yt) + Qref cosOt)] + n(t), 其中"和 ^分别为射频接收信号的幅度和相位变化， 0为白噪声。
在本实施例中， 假设最小均方自适应滤波处理模块 36的滤波系数为
Figure imgf000010_0001
其中 ^和^分别为在第 k个采样时刻对幅度"和相位 的估算值。由 公式（ 1 ) 、 （ 2 )和（ 3 ) , 可知射频残余信号
sk =dk -(WkfXk
= [ cos(^) - ak cos(^k )][Iref cos(ot) + Qref sin(ot)] +
[ sin(^) - ak m(pk )][-Iref sin(ot) + Qref cos(ot)] + n t)
= el [Iref cosOt) + Qref sin(wt)] + e2 [-Iref sin(wt) + Qref cos(»t)] + n(t), 其中 ex - acos( )-ak cos( k ) , e2 -a sin(^) -ak sin(^* )。 将射频残余信号^和射频参考信号 相混频， 可以注意到， 其乘积项中 没有了本振对应的频率 除了基带信号， 就只有 2«这样的二次谐波项， 因 此将该乘积项对应的信号进行低通滤波， 获得基带信号
{ekXk}LPF =[Prefe 2, Prefe2/2f, ( 4 ) 其中 ^=/re 2 +0re 2。 基于 LMS 自适应滤波算法， 可以通过第 k次迭代的 系数，以及基带信号 kXk、LPF ,得到第 k+1次迭代的系数 +1 =^ + {skXk)LPF , 其中 ^为 LMS自适应滤波算法中的步长参数。 将公式（4 )代入， 最终得到
Wk+l =Wk + MPref[ei, e2]T/2. 可以看出， 即为 的线性迭代，随着 中的 ^和 ^分别逼近。和 的迭代表达式中的向量 f会逐渐减小， 也收敛于 因此选取 合适的 ^， 即可以估计出自干扰信号相对于参考信号的幅度调整"和相位调整 并据此对最小均方自适应滤波处理模块的滤波系数进行调整， 达到对参考 信号调整的目的， 以最小化^。
为了更直观的看到 LMS自适应滤波算法相对于基于 RSSI检测的幅相搜索 算法的优越性， 参照图 5 , 示出了这两种算法的 MSE ( Mean Squared Error , 均方误差）的性能对比， 本图中， 信噪比 SNR=85dB, ^选取 0. 6 , 最小均方自 适应滤波处理模块的滤波系数经过 12bi t量化， 从图 5 中可以看到， 相对于 基于 RSSI检测的幅相搜索算法， 本实施例中最小均方自适应滤波处理模块采 用的 LMS 自适应滤波算法收敛速度更快， 估算结果更精确。
与实施二相比， 本实施例提供了一种具体的基带提取方式， 虽然在发送 机侧基带信号是已知的， 但是考虑到发送机功放的非线性因素会影响自干扰 消除的效果， 因此在模拟干扰消除中， 通常会采用经过放大后的射频信号作 为参考信号， 即本实施例中所述的射频参考信号， 通常为了得到基带信号 ， 需要对射频残余信号和射频参考信号分别做下变频处理， 然而这种方式需要 产生本振信号， 实现起来比较复杂，而且会引入如 I/Q不平衡等非线性因素， 影响算法的收敛速度及估算的精确度， 而本实施例无需进行下变频处理， 直 接将射频参考信号分成两路， 其中一路移相 90° , 再将这两路射频参考信号 与射频残余信号进行混频， 再经过低通滤波将谐波分量全部滤除得到基带信 号， 因此最小均方自适应滤波处理模块在迭代过程可以在基带进行， 有利于 进行数字化计算和控制， 实现了控制射频参考信号收敛的目的。 由于本实施 例无需进行下变频处理， 降低了实现的复杂度， 也避免了 I/Q 不平衡等非线 性因素对算法的影响。
实施例三：
图 6 示出了本发明第三实施例提供的自适应射频干扰抵消方法的流程, 为了便于说明仅示出了与本发明实施例相关的部分。
本实施例提供的自适应射频干扰抵消方法包括： 步骤 S601、 调整射频参考信号的幅度和相位， 输出射频调整信号， 使得 射频调整信号收敛于射频接收信号中的自干扰信号；
步骤 S6G2、 获取射频残余信号， 所述射频残余信号为所述射频接收信号 与射频调整信号的差值信号；
步骤 S603、 接收所述射频残余信号和射频参考信号并提取出基带信号， 将所述基带信号经最小均方自适应滤波处理后得到幅度相位控制信号， 所述 幅度相位控制信号用于控制调整射频参考信号的幅度和相位。
本实施例所述的步骤 S 601 -S 603对应由实施例一中的幅度相位调整模块 1、 减法器 2和基带提取滤波模块 3实现， 本实施例方法构成了一个反馈循环， 在步骤 S603从射频残余信号和射频参考信号中提取出基带信号， 并按照 LMS 自适应滤波算法得到幅度相位控制信号来控制并调整步骤 S 601中所述的射频 参考信号的幅度和相位， 再进行下一次迭代直至射频参考信号收敛于射频接 收信号的自干扰信号， 本实施例采用了 LMS 自适应滤波算法， 与现有的基于 RSSI检测的算法相比， 收敛速度更快， 估算结果更准确。 实施例四：
图 7 示出了本发明第四实施例提供的自适应射频干扰抵消方法的流程， 为了便于说明仅示出了与本发明实施例相关的部分。
本实施例提供的自适应射频干扰抵消方法包括：
步骤 S701、 调整射频参考信号的幅度和相位， 输出射频调整信号， 使得 射频调整信号收敛于射频接收信号中的自干扰信号；
步骤 S702、 获取射频残余信号， 所述射频残余信号为所述射频接收信号 与射频调整信号的差值信号；
步骤 S703、 将所述射频参考信号分成两路， 其中一路与所述射频残余信 号经过混频、 低通滤波后得到第一基带乘积信号；
步骤 S704、 另一路射频参考信号经过 90度移向后， 与所述射频残余信号 经过混频、 低通滤波后得到第二基带乘积信号；
步骤 S705、 将所述第一基带乘积信号和第二基带乘积信号经过最小均方 自适应滤波处理后， 生成幅度相位控制信号， 所述幅度相位控制信号用于控 制调整射频参考信号的幅度和相位。
上述步骤 S703-S705为实施例三中步骤 S603的一种具体优选步骤， 在本 实施例中， 以射频参考信号和射频残余信号的乘积作为幅相调整的依据， 具 体的， 将射频参考信号分成两路， 其中一路移相 90° , 两路射频参考信号再 与射频残余信号进行混频， 并通过低通滤波器得到这两个信号的基带乘积， 然后利用 LMS 自适应滤波算法估算出自干扰信号相对于参考信号的幅度和相 位， 即幅度和相位的调整系数， 完成对射频参考信号 X进行相应的幅度相位 调整， 经过调整后的射频信号再次与射频接收信号相抵消， 并获得新的射频 残余信号， 进行下一次迭代。
通常为了得到基带信号 ， 需要对射频残余信号和射频参考信号分别做下 变频处理， 然而这种方式需要产生本振信号， 实现起来比较复杂， 而且会引 入如 I/Q 不平衡等非线性因素， 影响算法的收敛速度及估算的精确度， 而本 实施例无需进行下变频处理， 直接将射频参考信号分成两路， 其中一路移相 90。 ， 再将这两路射频参考信号与射频残余信号进行混频， 再经过低通滤波 将谐波分量全部滤除得到基带信号， 因此最小均方自适应滤波处理模块在迭 代过程可以在基带进行， 有利于进行数字化计算和控制， 实现了控制射频参 考信号收敛的目的。 由于本实施例无需进行下变频处理， 降低了实现的复杂 度， 也避免了 I/Q不平衡等非线性因素对算法的影响。 实施例五：
图 8 示出了本发明第五实施例提供的接收机的结构， 为了便于说明仅示 出了与本发明实施例相关的部分。
本实例提供的接收机包括接收天线 41、 低噪声放大器 43、 下变频器 44、 模数转换器 45、 数字干扰抵消模块 46 以及接收数字信号处理器 47 , 以及如 实施例一或二所述的自适应射频干扰氏消装置 42 , 所述接收天线 41、 自适应 射频干扰抵消装置 42、 低噪声放大器 43、 下变频器 44、 模数转换器 45 ) 、 数字干扰抵消模块 46 以及接收数字信号处理器 47顺次连接， 所述自适应射 频干扰抵消装置 42还接入有来自于发送机的射频参考信号， 所述数字干扰抵 消模块 46还接入有来自于发送机的数字参考信号。
本实施例的接收机通过天线接收到的射频接收信号包括自干扰信号和有 用信号， 本实施例中的自适应射频干扰 ·!氏消装置 42采用了 LMS 自适应滤波算 法， 实现了调整射频参考信号的幅度和相位， 使得射频参考信号收敛于射频 接收信号中的自干扰信号， 因此收敛后， 自适应射频干扰抵消装置 42输出的 就是有用信号， 完成了自干扰消除操作。 本实施例与现有的接收机相比， 自 适应射频干扰 ·!氏消装置 42采用了 LMS 自适应滤波算法， 与现有的射频干扰氐 消模块采用的基于 RSSI检测的幅相搜索算法相比， 收敛速度更快， 估算结果 更精确。 实施例六：
图 9 示出了本发明第六实施例提供的无线全双工通信系统的结构， 为了 便于说明仅示出了与本发明实施例相关的部分。
本实施例提供的无线全双工通信系统包括发送机 50以及如实施例五所述 的接收机 40,所述发送机包括顺次连接的发射数字处理器 51、数模转换器 52、 上变频器 53、 功率放大器 54以及发射天线 55 , 所述功率放大器 54输出射频 参考信号接入到所述接收机的自适应射频干扰抵消装置 42 , 所述发射数字信 号处理器 51输出的数字参考信号接入到所述接收机的数字干扰抵消模块 46。
本实施例提供的无线全双工通信系统由发送机 50和接收机 40组成， 其 中接收机 40中的自适应射频干扰抵消装置 42采用了 LMS 自适应滤波算法， 而现有的接收机中的射频干扰抵消模块采用的基于 RSSI检测的幅相搜索算法, 本实施例中的接收机收敛速度更快， 估算结果更精确。 本领域普通技术人员可以理解， 实现上述实施例方法中的全部或部分步 骤是可以通过程序来指令相关的硬件来完成， 所述的程序可以在存储于一计 算机可读取存储介质中， 所述的存储介质， 如 R0M/RAM、 磁盘、 光盘等。 以上所述仅为本发明的较佳实施例而已， 并不用以限制本发明， 凡在本发明 的精神和原则之内所作的任何修改、 等同替换和改进等， 均应包含在本发明 的保护范围之内。

Claims

权利 要求 书
1、 一种自适应射频干扰氏消装置， 其特征在于， 所述装置包括：
幅度相位调整模块（1 ) , 用于调整射频参考信号的幅度和相位， 输出射频 调整信号至减法器（2 ) , 使得射频调整信号收敛于射频接收信号中的自干扰信 号；
减法器（2 ) , 用于接收射频接收信号以及幅度相位调整模块（1 )输出的 射频调整信号， 并输出射频残余信号， 所述射频残余信号为所述射频接收信号 与射频调整信号的差值信号；
基带提取滤波模块（3 ) , 用于接收射频参考信号以及减法器（2 )输出射 频残余信号， 并提取出基带信号， 将所述基带信号经最小均方自适应滤波处理 后得到幅度相位控制信号并输出至幅度相位调整模块（1 ) , 所述幅度相位控制 信号用于控制幅度相位调整模块（1 )调整射频参考信号的幅度和相位。
2、 如权利要求 1 所述装置， 其特征在于， 所述基带提取滤波模块（3 ) 包 括第一乘法器（ 31 )、第一低通滤波器（ 32 )、移相器（ 33 )、第二乘法器（ 34 ) 、 第二低通滤波器（35 ) 以及最小均方自适应滤波处理模块（36 ) , 所述射频参 考信号分成两路， 其中一路与所述射频残余信号通过第一乘法器 ( 31 )混频后， 经过第一低通滤波器（32 )得到第一基带乘积信号， 另一路射频参考信号经过 移相器（33 )移向 90度后， 与所述射频残余信号通过第二乘法器（34 ) 混频， 经过第二低通滤波器（35 ) 滤波后得到第二基带乘积信号， 所述第一基带乘积 信号和第二基带乘积信号接入到所述最小均方自适应滤波处理模块（36 )后， 生成用于控制幅度相位调整模块（1 ) 的幅度相位控制信号。
3、 如权利要求 2所述装置， 其特征在于， 所述幅度相位控制信号为调整系 数信号， 所述幅度相位调整模块（1 )根据接收到的调整系数信号调整所述射频 参考信号的幅度和相位。
4、 一种自适应射频干扰 ·!氏消方法， 其特征在于， 所述方法包括下述步骤： 调整射频参考信号的幅度和相位， 输出射频调整信号， 使得射频调整信号 收敛于射频接收信号中的自干扰信号；
获取射频残余信号， 所述射频残余信号为所述射频接收信号与射频调整信 号的差值信号；
接收所述射频残余信号和射频参考信号并提取出基带信号， 将所述基带信 号经最小均方自适应滤波处理后得到幅度相位控制信号， 所述幅度相位控制信 号用于控制调整射频参考信号的幅度和相位。
5、 如权利要求 4所述方法， 其特征在于， 所述接收所述射频残余信号和射 频参考信号并提取出基带信号， 将所述基带信号经最小均方自适应滤波处理后 得到幅度相位控制信号步骤， 具体包括：
将所述射频参考信号分成两路， 其中一路与所述射频残余信号经过混频、 低通滤波后得到第一基带乘积信号；
另一路射频参考信号经过 90度移向后， 与所述射频残余信号经过混频、 低 通滤波后得到第二基带乘积信号；
将所述第一基带乘积信号和第二基带乘积信号经过最小均方自适应滤波处 理后， 生成幅度相位控制信号， 所述幅度相位控制信号用于控制调整射频参考 信号的幅度和相位。
6、一种接收机，包括接收天线（41 )、低噪声放大器（43 )、下变频器（44 )、 模数转换器（ 45 )、 数字干扰抵消模块 ( 46 ) 以及接收数字信号处理器（ 47 ) , 其特征在于， 所述接收机还包括如权利要求 1-3任一项所述的自适应射频干扰 抵消装置 （42 ) , 所述接收天线 （41 ) 、 自适应射频干扰抵消装置 （42 ) 、 低 噪声放大器（43 ) 、 下变频器（44 ) 、 模数转换器（45 ) 、 数字干扰抵消模块
( 46 ) 以及接收数字信号处理器（47 )顺次连接， 所述自适应射频干扰抵消装 置（ 42 )还接入有来自于发送机的射频参考信号， 所述数字干扰抵消模块（ 46 ) 还接入有来自于发送机的数字参考信号。
7、 一种无线全双工通信系统， 包括发送机（50 ) , 所述发送机包括顺次连 接的发射数字处理器（51 ) 、 数模转换器（52 ) 、 上变频器（53 ) 、 功率放大 器（54) 以及发射天线（55) , 其特征在于， 所述系统还包括如权利要求 6 所 述的接收机（40) , 所述功率放大器（54)输出射频参考信号接入到所述接收 机的自适应射频干扰抵消装置 （42) , 所述发射数字信号处理器（51)输出的 数字参考信号接入到所述接收机的数字干扰抵消模块（46) 。
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