WO2011131021A1 - 磁性变速组成及其分段相位驱动马达 - Google Patents

磁性变速组成及其分段相位驱动马达 Download PDF

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Publication number
WO2011131021A1
WO2011131021A1 PCT/CN2011/000454 CN2011000454W WO2011131021A1 WO 2011131021 A1 WO2011131021 A1 WO 2011131021A1 CN 2011000454 W CN2011000454 W CN 2011000454W WO 2011131021 A1 WO2011131021 A1 WO 2011131021A1
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WO
WIPO (PCT)
Prior art keywords
ring
magnetic
blocks
stator
sub
Prior art date
Application number
PCT/CN2011/000454
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English (en)
French (fr)
Inventor
彭明燦
郑丽茹
Original Assignee
财团法人工业技术研究院
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Priority claimed from US12/763,751 external-priority patent/US8188629B2/en
Application filed by 财团法人工业技术研究院 filed Critical 财团法人工业技术研究院
Priority to DE112011101381T priority Critical patent/DE112011101381T5/de
Publication of WO2011131021A1 publication Critical patent/WO2011131021A1/zh
Priority to GB1213724.6A priority patent/GB2492259A/en

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02K—DYNAMO-ELECTRIC MACHINES
    • H02K49/00—Dynamo-electric clutches; Dynamo-electric brakes
    • H02K49/10—Dynamo-electric clutches; Dynamo-electric brakes of the permanent-magnet type
    • H02K49/102—Magnetic gearings, i.e. assembly of gears, linear or rotary, by which motion is magnetically transferred without physical contact
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02K—DYNAMO-ELECTRIC MACHINES
    • H02K51/00—Dynamo-electric gears, i.e. dynamo-electric means for transmitting mechanical power from a driving shaft to a driven shaft and comprising structurally interrelated motor and generator parts
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02K—DYNAMO-ELECTRIC MACHINES
    • H02K21/00—Synchronous motors having permanent magnets; Synchronous generators having permanent magnets
    • H02K21/02—Details
    • H02K21/021—Means for mechanical adjustment of the excitation flux
    • H02K21/028—Means for mechanical adjustment of the excitation flux by modifying the magnetic circuit within the field or the armature, e.g. by using shunts, by adjusting the magnets position, by vectorial combination of field or armature sections

Definitions

  • the present invention is a transmission assembly, and more particularly a magnetic shifting composition. Background technique
  • the transmission is used for power transmission. In addition to relaying and transmitting power, it also has the function of decelerating or increasing the speed of the power source. Variable speeds for conventional automotive engines include mechanical gearboxes and hydraulic gearboxes. For electric vehicles or hybrid vehicles, there are magnetic transmissions.
  • variable speed motor The technology of the variable speed motor can be found in the US Patent No. 3,980,937 (Fractional Horsepower Gear Motor) announced on September 14, 1976, which passes the power outputted by the motor through the mechanical gear set to achieve torque conversion and shifting effects.
  • the aforementioned mechanical transmission has the disadvantages of high noise and heavy weight, while the general magnetic transmission can reduce vibration and noise, but it cannot reduce the weight.
  • the electric motor in the application of electric vehicles, the electric motor must meet the requirements of different driving torque and driving speed. It must also meet the requirements of high-efficiency operation. Therefore, the motor and the transmission are often matched. In this mode, the motor and the transmission are integrated. The drive power density is usually not easily increased (due to the total weight of the motor and the transmission).
  • the proposed magnetic shifting composition is easily integrated with an electric motor (e.g., an electric motor) or a generator to have a light weight characteristic, so that the driving power density can be improved.
  • a magnetic shifting composition includes a rotor, a stator, and a magnetically permeable assembly.
  • Rotor and stator The sub-coaxial sleeve has a plurality of magnetic poles and has R pole pairs.
  • the stator has a plurality of magnetic poles and STI pole pairs.
  • the magnetically conductive component is located between the rotor and the stator and has a plurality of conductors. When the magnetically permeable component is actuated, the magnetically permeable component selectively causes PN1 or PN2 of the conductive magnets to correspond between the rotor and the stator, wherein PN1-3 ⁇ R+ST1 ⁇ PN1+3 , PN2-3 ⁇ +ST1 ⁇ PN2+3.
  • the magnetic conductive component comprises a first ring and a second ring, the first ring is axially connected to the second ring, the first ring has PN1 magnetic conductive sub-blocks, and the second ring has PN2 A magnetically permeable sub-block that selectively moves the first or second ring between the rotor and the stator when the magnetically permeable assembly is axially actuated.
  • the magnetic conductive component includes a first ring and a second ring, the first ring is located radially outward of the second ring, and the first ring and the second ring are disposed between the stator and the rotor.
  • the magnetically permeable component is actuated, the first ring and the second ring are relatively displaced between the first position and the second position, and when the first ring and the second ring are in the first position, the magnetic conductive component has PN1
  • the magnetizer when the first ring and the second ring are in the second position, the magnetic conductive component has PN2 of the magnetizers.
  • the stator includes a plurality of induction coils and a pole number modulation circuit, wherein the induction coil is electrically formed to form a magnetic pole, and the pole number modulation circuit selectively switches the induction coil to the ST1 pole pairs and one ST2 Between the pole pairs.
  • PN2-3 R+ST2 ⁇ ⁇ 2 ⁇ .
  • the magnetic shifting composition includes a rotor, a stator, and a magnetically permeable assembly.
  • the rotor has a plurality of magnetic poles, and the magnetic poles of the rotor have R pole pairs.
  • the stator and the rotor are coaxially sleeved, and the stator has a plurality of magnetic poles, and the magnetic poles of the stator have ST1 pole pairs.
  • the magnetic conductive component is disposed between the rotor and the stator and has PN1 magnetic conductive sub-blocks, and the PN1 magnetic conductive sub-blocks are disposed between the rotor and the stator, wherein PN1-3 ⁇ R+ST1 ⁇ ⁇ 1+3.
  • the magnetic conductive component is disposed between the stator and the rotor, and the design of the magnetic flux component can selectively change the number of the magnetic conductors (that is, the number of magnetic gaps also changes), so that different speed ratios can be generated between the stator and the rotor. (The stator speed is higher than the rotor speed).
  • the magnetic logarithm of the stator also has a switchable design, so that the purpose of generating different gear ratios can be achieved by using the magnetic conductive component and the rotor.
  • the foregoing magnetic conductive component, stator and rotor can all have a hollow annular design, so that the entire magnetic shifting composition has a relatively small volume and weight, and can be easily integrated with the electric motor to obtain a higher driving power density (Watt/ Kg, W/Kg or watt/volume, W/m 3 ) 0
  • FIG. 1 is a perspective view of a first embodiment of a magnetic shifting composition according to a first embodiment of the present invention
  • FIG. 2 is a perspective exploded view of a first embodiment of a magnetic shifting composition according to the present invention
  • 4A is a schematic cross-sectional view of a magnetically permeable component of the first embodiment of the present invention
  • FIG. 4B is a partially enlarged cross-sectional view of the first embodiment of the magnetically permeable component of FIG. 4A;
  • FIG. 4C is another partially enlarged cross-sectional view of the first embodiment of the magnetically permeable assembly of FIG. 4A;
  • FIG. 5A is a schematic view of a winding of another embodiment of the stator of the magnetic shifting composition according to the present invention;
  • FIG. 5B is a schematic view of the stator of FIG. A schematic diagram of the action of another embodiment;
  • Figure 6 is a schematic diagram of the pole-to-number switching of Figures 5A and 5B;
  • FIG. 7A, 7B and 7C are schematic views showing a second embodiment of a magnetically permeable component of the magnetic shifting composition according to the present invention.
  • Figure 8 is a perspective view of a third embodiment of a magnetically permeable component of a magnetic shifting assembly in accordance with the present invention
  • Figure 9 is a perspective exploded view of a second embodiment of a magnetic shifting composition in accordance with the present invention
  • FIG. 10B and FIG. 10C are respectively a partial cross-sectional view and a state diagram of FIG. 10A at positions 10B-10B;
  • FIG. 11A is a schematic view showing a fourth embodiment of a magnetically permeable component of a magnetic shifting assembly according to the present invention
  • FIGS. 11B and 11C are respectively a partial cross-sectional view and a state diagram of FIG. 11A at positions 11B-11B;
  • Figure 1 1D is another schematic view of Figure 11B;
  • Figure 12 is a schematic view showing the structure of a segmented phase drive motor according to the present invention.
  • the magnetic shifting composition includes a rotor 20, a stator 30 and a magnetically permeable component 40 (also referred to as a magnetically variable shifting assembly).
  • the magnetic shifting composition can be adapted to be integrated with an electric motor (such as an electric motor) or a generator.
  • the drive power density here can be, but is not limited to, output power divided by volume, or output power divided by weight (i.e., (output torque X speed) / volume, or (output torque X speed) / weight).
  • the rotor 20 can receive the rotational power, and the coil of the stator 30 (detailed later) can output the electric power generated by the magnetic field cutting. This power can be passed through The output is output after the current and voltage regulator circuits. Since the magnetic shifting composition can generate the shift ratio via control, when the input rotary power has a large variation, or a better system conversion efficiency is desired, the controller can adjust the shift ratio of the magnetic shifting composition. '
  • the stator 30 may be a fixed magnet or an induction magnet (or an electromagnet).
  • an induction magnet is taken as an example.
  • the inner side of the stator 30 is annularly arranged with a plurality of bumps 32a, 32b.
  • Each of the bumps 32a, 32b is wound with an induction coil (described in detail later), and when the induction coil is energized, a magnetic pole can be formed.
  • the stator 30 has 48 bumps 32a, 32b, and each of the bumps 32a, 32b is electrically connected to form a pair of magnetic poles. In this example, there are four phases (4 phases), and each phase has 12 pole pairs.
  • FIG. 3 is a schematic diagram of the magnetic logarithm of the stator 30 according to an embodiment of the present invention.
  • the adjacent magnetic poles have opposite polarities (magnetic north pole N and magnetic south pole S).
  • Two adjacent magnetic poles of opposite polarity are a magnetic pair (for example, Sl of the drawing, N1 is a magnetic pair).
  • N1 is a magnetic pair.
  • the pole logarithm is only one embodiment.
  • the present invention is not limited to this magnetic logarithm, and is represented by ST1 pole pairs.
  • the rotor 20 may be a fixed magnet or an induction magnet. In the present embodiment, the rotor 20 will be described by taking a fixed magnet as an example.
  • the rotor 20 has a plurality of magnetic poles and has R pole pairs. In the present embodiment, the rotor 20 has 20 pole pairs as an example.
  • the stator 30 is disposed coaxially with the rotor 20 (coaxially sleeved), and in this embodiment, the rotor 20 is disposed radially inward of the stator 30, but is not limited thereto. It is also possible to arrange the stator 30 on the radially inner side of the rotor 20 to achieve the object of the present invention. Next, the direction of the magnetic pole (magnetic force line) of the rotor 20 is directed toward the magnetic pole (magnetic field line) of the stator 30.
  • the magnetic conductive component 40 may be laminated steel, and the material thereof may be soft magnetic material (Soft
  • the magnetically permeable component 40 includes a first ring 42 and a second ring 44.
  • the first ring 42 is located radially outward of the second ring 44, and the first ring 42 and the second ring 44 are disposed between the stator 30 and the rotor 20.
  • the first ring 42 and the second ring 44 may be in contact with each other or at a distance (the pattern is implemented by a gap).
  • the first ring 42 has a plurality of magnetically permeable sub-blocks 420, 422.
  • the second ring 44 also has a plurality of magnetically permeable sub-blocks 440, 442.
  • the magnetically permeable sub-blocks 420, 422, 440, 442 can form a plurality of magnetizers (described in detail later).
  • the two can be relatively moved (relatively rotated) between the first position and the second position, and the number of the magnetizers will also change accordingly. As explained below.
  • FIG. 4A is a cross section of a first embodiment of a magnetically permeable assembly in accordance with an embodiment of the present invention.
  • the cross-sectional view is a schematic cross-sectional view of the first ring 42 of FIG. 2 after being placed radially outward of the second ring 44, and having a plane perpendicular to the axial direction.
  • the arcs labeled 429 and 449 in Figure 4A are again enlarged in Figure 4B.
  • the arc angles of the arc segments 429, 449 are 45 degrees, so that the entire first ring 42 and the second ring 44 have 8 arc segments 429, 449.
  • 4B is a partially enlarged cross-sectional view showing a state in which the first ring 42 and the second ring 44 are at the first position.
  • 4C is a partially enlarged cross-sectional view showing a state in which the first ring 42 and the second ring 44 are at the second position.
  • the magnetically permeable sub-block 420 of the first ring 42 is connected (or overlapped) with the magnetically permeable sub-block 440 of the second ring 44 and forms a magnetizer 46a.
  • the magnetic permeable sub-block 422 of the first ring 42 is connected to the magnetic permeable sub-block 442 of the second ring 44 and forms a magnetizer 46b.
  • FIG. 4C a partial enlarged cross-sectional view of the state in which the first ring 42 and the second ring 44 are in the second position is continued.
  • the magnetically permeable sub-block 420 of the first ring 42 is connected to the magnetically permeable sub-block 440 of the second ring 44 and forms a magnetizer 46a.
  • the magnetic permeable sub-block 422 of the first ring 42 is connected to the magnetic permeable sub-block 442 of the second ring 44 and forms a magnetizer 46b.
  • there are four magnetic gaps 48a, 48b, 48c, 48d in the arc segments 429, 449, which also have four magnetizers 46a, 46b. Therefore, there will be 32 (4 X 8 32) magnetic gaps 48a, 48b, 48c, 48d throughout the first ring 42 and the second ring 44.
  • the foregoing magnetically conductive sub-blocks 420, 440 are in a connected state, and the distances are similar, and not only in the state of contact, and the distances may be similar to the magnetically conductive sub-blocks 420, 440 which are not in contact but overlap in the radial direction, or The magnetic sub-blocks 420, 440 are not in contact and have a spacing in the radial or circumferential direction. It is claimed that if the magnetic sub-blocks 420, 440 are not in contact, there are two distances between the magnetic sub-blocks 420, 440, one of which is a radial distance and the other is a distance in the circumferential direction.
  • the radial distance of the former As far as the radial distance of the former is concerned, it has been experimentally possible to achieve the effect of forming a single magnetizer 46a if the radial distance is within 5 millimeters (mm). Of course, this distance is also related to the strength of the magnetic field lines of the stator 30. If the strength of the magnetic lines is stronger, the distance can be larger. That is to say, this radial distance can be changed depending on the size of the magnetic shifting composition itself and the strength of the magnetic field lines.
  • the distance (arc length) in the circumferential direction of the latter can also be expressed as the angle between the boundary of the magnetic sub-block 420 and the 440 corresponding to the center of the circle (the center of the stator), for example, as shown in FIG. 4B, the left side of the magnetic sub-block 420 The angle between the side and the right side of the magnetic sub-block 440.
  • the magnetic sub-block 420 will be The space formed by the distance between the left side of the magnet and the right side of the magnetic sub-block 440 is defined as an air gap. Since the magnetic shifting composition is in operation, each magnetic gap 48a, 48b, 48c (Fig.
  • the 4B generates a magnetic pole (hereinafter referred to as a magnetic gap magnetic pole), and when the magnetic conductive sub-blocks 420, 440 have an air gap, the gas The slit also has a magnetic pole (hereinafter referred to as an air gap magnetic pole), which is an effect of allowing the magnetic conductive sub-blocks 420, 440 to form the lead magnet 46a.
  • the magnetic field strength of the air gap magnetic pole is preferably less than the magnetic field strength of the air gap magnetic pole. Twenty (20%) of the points.
  • the arc length or the angle obtained by retracting the magnetic field strength of the air gap magnetic pole is a preferred circumferential direction pitch.
  • the material of the magnetic sub-blocks 420, 422, 440, 442 may be any magnetically permeable material such as an iron-based material or soft iron.
  • the relative motion of the first ring 42 and the second ring 44 can be driven in a mechanical or electromagnetic manner. While driving, the first ring 42 or the second ring 44 may be driven separately, or the first ring 42 and the second ring 44 may be driven at the same time, as long as the relative positions of the first ring 42 and the second ring 44 can be displaced. It can be between a position and a second position.
  • the magnetic conductive component 40 when the magnetic conductive component 40 is actuated, the first ring 42 and the second ring 44 are relatively moved in the first position (as shown in FIG. 4B) and the second position (as shown in FIG. 4C). Between the positions), when the first ring 42 and the second ring 44 are in the first position, the magnetic conductive component 40 has 24 (hereinafter referred to as PN1) magnets 46a, 46b, when the first ring 42 and the second ring When the 44 is in the second position, the magnetically permeable assembly 40 has 32 (hereinafter referred to as PN2) magnets 46a, 46b.
  • the magnetically permeable component 40 is designed such that the first ring 42 and the second ring 44 are relatively movable.
  • the magnetically permeable component 40 can selectively cause the PN1 or PN2 magnetizers 46a, 46b to correspond between the rotor 20 and the stator 30.
  • the PN1 or PN2 magnets 46a, 46b matching the magnetic field of the rotor 20 and the magnetic field of the stator 30, an effect of increasing and decreasing (shifting) can be produced.
  • This increase/deceleration ratio can be obtained by the following formula (1):
  • the rotational speed of the stator 30 is 1.6:1 than the rotational speed of the upper rotor 20.
  • the magnetic shifting composition has the effect of shifting by proper arrangement and design of the magnetic conductive component 40, the stator 30 and the rotor 20.
  • the magnetic conductive component 40 when the magnetic conductive component 40 is located at the second position, it satisfies the formula (3) PN2-3 ⁇ R+ST1 ⁇ PN2+3.
  • the magnetic conductive component 40 when the magnetic conductive component 40 is in the first position, although it does not satisfy the formula (2) PN1-3 ⁇ R+ST1 ⁇ PN1+3, it is still a variable speed requirement.
  • the design of the magnetic permeable sub-blocks 420, 422, 440, 442 of the magnetic conductive component 40 can be modified to satisfy the formula (2). For example, if ST1 is 12, and PN1 and PN2 are 35 and 29, respectively, the above equations (2) and (3) are satisfied.
  • FIG. 5A can be used.
  • Figure 5A is a schematic view of a winding of another embodiment of a stator 30 of magnetic shifting composition in accordance with the present invention.
  • Figure 5B is a schematic illustration of the operation of another embodiment of the stator 30 of Figure 5A.
  • another embodiment of the stator 30 includes a plurality of inductive coils 34a, 34b, 34c, 34d and a pole number modulation circuit 36.
  • the induction coils 34a, 34b, 34c, 34d are wound around the bumps 32a, 32b, respectively.
  • FIG. 5A and FIG. 5B only the induction coils 34a, 34b, 34c, 34d of three magnetic pole pairs (1, N2, N3, SI, S2, S3) are drawn, but it does not mean that the stator 30 only includes the induction coils 34a, 34b. , 34c, 34d.
  • the pole number modulation circuit 36 includes two switchers 360, 362. When the changeover switches 360, 362 are in the state of FIG.
  • the magnetic poles formed by the respective induction coils 34a, 34b, 34c, 34d are the polarities as shown in FIG. 3, that is, the stator 30 has a total of 12 poles. logarithm.
  • the changeover switches 360, 362 are in the state of FIG. 5B and the power is supplied, the induction coils 34c, 34d which originally formed N1, S3 are turned into the power supply in the opposite direction, so that the magnetic poles formed are opposite (ie, N1 becomes magnetic south pole). , S3 becomes magnetic north pole), please refer to FIG. 6, which is a schematic diagram of the pole-to-number switching of FIG. 5A and FIG. 5B.
  • the dashed box shows the polarity of the magnetic pole formed when the switch 360, 362 is located in Fig. 5B.
  • Nl, N4, N7, and N10 are magnetic north poles, S3, S6, and S9 in Fig. 5A.
  • S12 is a magnetic south pole in FIG. 5A.
  • the stator 30 has a total of 12 (hereinafter referred to as ST1) pole pairs (ie, N1, S1, N2, S3...N12, S12), but in FIG.
  • each coil set 35a, 35b includes three sequentially adjacent induction coils 34a, 34b, 34c, 34d.
  • the adjacent neighbors are connected, for example, SI, Nl, S2 in Fig. 5B are sequentially adjacent induction coils 34a, 34b, 34c, 34d.
  • the stator 30 can selectively switch the induction coils 34a, 34b, 34c, 34d to 12 (ST1) pole pairs and 4 (ST2) pole pairs by the pole number modulation circuit 36. between.
  • the gear ratio (stator revolution number: rotor rotational speed) of the following table can be obtained, and the above formula (2) and the following formula (4) are satisfied. ).
  • the pole number modulation circuit 36 is only one of the embodiments in FIG. 5A, but is not limited thereto. With proper circuit and switch design, the number of pole pairs of the stator 30 can be increased or decreased in different proportions.
  • the winding method of the stator 30 can also be used in a more complicated and diverse design, for example, by using a winding chart to obtain more extreme pole-log requirements. This can be, but is not limited to, LRK (Lucas, Retzbach and Ktihf ss) winding, or D-LRK (distributed LRK) winding, or ABC winding, for this application, as detailed later.
  • FIGS 7A, 7B, and 7C Other embodiments of the aforementioned magnetically permeable assembly 40 of Figure 4A can be seen in Figures 7A, 7B, and 7C.
  • the magnetic conductive component 50 (second embodiment) of Figures 7A and 7B, and 7C is similar to the schematic of Figure 4B. Style.
  • the magnetically permeable assembly 50 includes a first ring 52, a second ring 54, a third ring 56, and a fourth ring 58.
  • the first ring 52, the second ring 54, the third ring 56 and the fourth ring 58 are radially stacked and respectively have magnetic conductive sub-blocks 53, 55, 57, 59 (also referred to as first, second, third respectively) , the fourth magnetic sub-block:).
  • the magnetic conductive sub-blocks 53, 55, 57, 59 are connected to each other such that there are two magnetisms 51a, 51b and Two magnetic gaps (magnetic gaps are the gaps in which the magnetizers are separated in the circumferential direction).
  • the magnetic conductive component 50 is in the position of FIG. 7B (second position)
  • the magnetic sub-blocks 53, 55, 57, 59 are separated from each other such that there are four magnetizers 51a, 51b, 51c in this arc segment. , 51d and four magnetic gaps.
  • the magnetic conductive component 50 is located at a position as shown in FIG.
  • the magnetic conductive sub-blocks 53, 55, 57, 59 are completely overlapped in the radial direction, at this time,
  • the magnetic conductive component 50 has two magnetizers 51a, 51b and two magnetic gaps.
  • the magnetic conductive component 50 is in the position of FIGS. 7A and 7C, although the number of the obtained magnetisms 51a, 51b is the same, the magnetic flux is Differently, therefore, the torque that can be transmitted also changes. Therefore, the magnetic permeability component 50 can change its gear ratio and change the torque transmitted by the appropriate design and control.
  • a plurality of annular (cylindrical) magnetically conductive rings i.e., the aforementioned first rings 42, 52, etc.
  • the number can vary according to the actual design requirements, which means that there can be a combination of three or five magnetically conductive rings, but it is not limited to this number.
  • the size, arrangement and number of the magnetically permeable sub-blocks in the magnetically permeable ring can also be appropriately designed to produce a different number of magnetic gaps, thereby obtaining the desired ratio of variables.
  • FIG. 8 is a schematic illustration of a third embodiment of a magnetically permeable assembly of magnetic shifting in accordance with the present invention.
  • the magnetically permeable assembly 60 includes a first ring 62 and a second ring 64.
  • the first ring 62 is axially coupled to the second ring 64.
  • the magnetic conductive component 60 is disposed between the stator 30 and the rotor 20.
  • the first ring 62 and the second ring 64 are axially movable between the stator 30 and the rotor 20 such that only one of the first ring 62 and the second ring 64 is sandwiched between the stator 30 and the rotor at the same time. 20 inside.
  • the magnetically permeable assembly 60 when the magnetically permeable assembly 60 is axially actuated, the magnetically permeable assembly 60 selectively moves the first ring 62 or the second ring 64 between the rotor 20 and the stator 30.
  • the sandwiched first ring 62 or the second ring 64 can interact with the magnetic field of the stator 30 and the rotor 20 to have a specific gear ratio.
  • the number of the first ring 62 of the conductive sub-blocks 63 (for example, PN1 magneto-optical sub-blocks) is different from the number of the second ring 64-conducting sub-blocks 65 (for example, PN2 magneto-optical sub-blocks).
  • PN1 magneto-optical sub-blocks for example, PN1 magneto-optical sub-blocks
  • the number of the first ring 62 of the conductive sub-blocks 63 is 32, and the number of the second ring 64 of the conductive sub-blocks 65 is 24, which is suitable for replacing the magnetically conductive components in the embodiment of FIG. 40.
  • Each of the conductive sub-blocks 63, 65 in this embodiment is formed separately and equivalent to the magnetizers 46a, 46b 0 in FIGS. 4B and 4C, respectively.
  • the first ring 62 and the second ring 64 are coaxially connected.
  • the first ring 62 and the second ring 64 are coaxially connected by an electrically insulating component 66a.
  • the two outer ends of the first ring 62 and the second ring 64 respectively have electrical insulation components 66b, 66c 0 electrically insulating components 66a, 66b, 66c for fixing the magnetic permeable sub-blocks 65 of the second ring 64 and the first The magnetically permeable sub-block 63 of the ring 62.
  • FIG. 9 is a perspective view of a second embodiment of the magnetic shifting composition according to the present invention.
  • the magnetic shifting composition comprises a rotor 20, a stator 30 and a magnetically permeable component 70.
  • the rotor 20 has a plurality of magnetic poles, and the magnetic poles of the rotor 20 have R pole pairs.
  • the stator 30 is coaxially sleeved with the rotor 20.
  • the stator 30 has a plurality of magnetic poles, and the magnetic poles of the stator 30 have ST1 pole pairs.
  • the magnetic conductive component 70 is disposed between the rotor 20 and the stator 30 and has PN1 magnetic conductive sub-blocks 72 (also called magnetizers).
  • the PN1 magnetic conductive sub-blocks 72 are correspondingly disposed between the rotor 20 and the stator 30, wherein , PN1-3 ⁇ R+ST1 ⁇ ⁇ 1+3. Therefore, when R is 20, PN1 is 32, and ST1 is 12, the acceleration/deceleration ratio of this magnetic shifting ratio is 1.6:1 (according to the above formula (1)).
  • both ends of the magnetic permeable sub-block 72 are fixed by the electrically insulating components 74a, 74b, and therefore, the current induced by the magnetic permeable sub-block 72 due to the magnetic field of the stator 30 and the rotor 20 will be limited. Within each of the magnetically permeable sub-blocks 72, no leakage occurs.
  • each of the magnetic conductive component 70, the stator 30 and the rotor 20 has a hollow annular design, so that the entire magnetic shifting composition has a relatively small volume and weight, and can be easily integrated with the electric motor.
  • Higher drive power density Watt/kg, W/Kg or watt/volume, W/m 3 .
  • the magnetic shifting composition can be switched between different shift ratios via different embodiments of the magnetic conductive assemblies 40, 50, 60. Then, if the number of the magnets 46a, 46b, 51a, 51b, 51c, 51d that can be switched by the magnetic conductive components 40, 50, 60 fails to conform to the formulas (2) and (3), a map can also be used.
  • the embodiment of the stator 30 of 5A (according to equations (2) and (4)) can improve the stability in different speed ratio states.
  • beta 1 J can be obtained by the following relationship:
  • ST1, and ST2' are the pole pairs of the high-order magnetic permeability of the stator 30, respectively.
  • the number of pole pairs of the main harmonic of the stator 30 is 4, then the third permeance harmonics The pole-logarithm is 12, and therefore, there is a greater elastic selection space when designing the pole-number R of the rotor 20 and the number of the magnetizers 46a, 46b of the magnetic conductive assembly 40, PN1, PN2.
  • the magnetic field generated by the stator 30 can be asynchronously designed in addition to the pole pair R of the rotor 20 and the magnetic permeability 46a, 46b of the magnetic conductive member 40.
  • switching between synchronous and asynchronous can also be achieved by controlling the number of pole pairs and/or the magnetically permeable component 40 of the stator 30.
  • FIG. 10A, FIG. 10B, and FIG. 10C are respectively a schematic view of a fourth embodiment of a magnetically permeable component according to the magnetic shifting composition of the present invention, and a partial cross-sectional view and an operation diagram of FIG. 10A at a position of 10B-10B. .
  • the magnetically permeable assembly 80 includes a first ring 82 and a second ring 84.
  • the first ring 82 has a plurality of magnetically conductive sub-blocks 820 (also referred to as first magnetically conductive sub-blocks) that are parallel to each other, are strip-shaped, and are arranged in a ring shape.
  • the second ring 84 also includes a plurality of magnetically conductive sub-blocks 840 (also referred to as second magnetically conductive sub-blocks) that are parallel to each other, are strip-shaped, and are arranged in a ring shape.
  • the magnetically permeable sub-block 820 of the first ring 82 and the magnetically permeable sub-block 840 of the second ring 84 are radially interposed and sandwiched between the stator 30 and the rotor 20 (see Fig. 1). That is, the magnetic permeable sub-block 820 of the first ring 82 and the magnetic permeable sub-block 840 of the second ring 84 are located at the same or close radial position, as can be seen from FIG. 10B.
  • Fig. 10B is a partial cross-sectional view of Fig. 10A at the position 10B-I0B, which is similar to the cross-sectional relationship of Fig. 4B and Fig. 2 and Fig. 4A. That is, Fig. 10B is only a cross-sectional view of a portion of the arc of Fig. 10A.
  • Figure 10B illustrates the state in which the first ring 82 and the second ring 84 of the magnetically permeable component 80 are in the first position.
  • the magnetically permeable sub-blocks 820, 840 have a distance from each other, and each magnetically conductive Sub-blocks 820, 840 are self-contained as a magnetizer.
  • the distances described herein are in an equidistant state in the drawings, but are not limited thereto, as long as the aforementioned air gaps are formed between the two magnetically conductive sub-blocks 820, 840, so that adjacent magnetically conductive sub-blocks are formed.
  • the distance between the magnetic sub-blocks 820 and 840 may be non-equal.
  • the first ring 82 and the second ring 84 of the magnetic conductive component 80 are in a second position.
  • the two adjacent magnetic conductive sub-blocks 820, 840 are close to each other, so that two The two closely spaced magnetically permeable sub-blocks 820, 840 form a magnetizer.
  • the close-up referred to herein means that the distance between two adjacent magnetically permeable sub-blocks 820, 840 is sufficiently small that the two adjacent magnetically permeable sub-blocks 820, 840 form a single magnetizer.
  • the number of magnetrons formed in FIG. 10B is the guide of FIG. 10C. Double the number of magnets. Therefore, the magnetic permeability component 80 can change the number of its magnetizers via control.
  • actuating assembly 88 that controls the amount of magnetism of the magnetically permeable component 80
  • components such as an electric motor or a pneumatic valve may be employed.
  • This actuation assembly 88 can also be applied to the embodiment of Figures 1, 7A, 8, and 11A. Of course, if the actuating assembly 88 is changed to a fixed type, it can be controlled by manual dialing.
  • FIG. 11A, FIG. 11B, and FIG. 11C are respectively a schematic view of a fourth embodiment of a magnetically permeable assembly of the magnetic shifting assembly according to the present invention, and a partial cross-sectional view and an operation diagram of FIG. 11A at a position of 11B-11B.
  • the schematic representation is similar to that of Figs. 10A, 10B, and 10C, and therefore will not be described again.
  • the fourth embodiment of the magnetically permeable assembly 80 includes a first ring 92, a second ring 94, and a third ring 96.
  • the first ring 92, the second ring 94 and the third ring 96 respectively have a plurality of magnetic permeable sub-blocks 920, 940, 960 (also referred to as first, second, and third magnetically permeable sub-blocks, respectively), the first guide
  • the magnetic sub-block 920, the second magnetically conductive sub-block 940, and the third magnetically conductive sub-block 960 are arranged in a radial direction and sandwiched between the stator 30 and the rotor 20, and each of the magnetically conductive sub-blocks 920, 940 , 960 are located at the same or close to the radial position (ie, the radius from the center of the circle), so when the first ring 92, the second ring 94 and the third ring 96 are in the first position as shown in FIG.
  • each guide The magnet blocks 920, 940, 960 each become a separate magnetizer, such that the magnetic component 90 has PN1 magnets, and the first ring 92, the second ring 94 and the third ring 96 are located as shown in FIG.
  • the adjacent three magnetically conductive sub-blocks 920, 940, 960 are close together and form a magnetizer, so that the magnetic conductive component 90 has PN2 magnetizers, and therefore, the magnetic conductive component located at the first position
  • the number PN1 of the magnetizers formed by 90 is three times the number PN2 of the magnetizers located at the second position.
  • FIG. 11D is a schematic diagram of the first ring 92 , the second ring 94 and the third ring 96 in the third position.
  • the magneto-optical block 960 and the third ring 96 are visible.
  • the magnetically permeable sub-blocks 940 of the second ring 94 are close together, and the magnetically permeable sub-blocks 920 of the first ring 92 are not close (or close to or in contact with) the (second, third) magnetically conductive sub-blocks 940, 960, thus
  • the magnetically conductive sub-blocks 940, 960 are formed to form a magnetizer, and the (first:) magnetically conductive sub-block 920 is independently formed with a magnetizer, so that the magnetic conductive component 90 has PN3 magnetizers, which is formed by FIG. 11D.
  • the number of magnetizers PN3 is twice the number of magnetizers PN2 formed in Fig. 11C. Where PN3 can satisfy the following formula (5) :
  • first ring 92, the second ring 94 and the third ring 96 may also be arranged in a non-equidistant manner, so that the arc length occupied by the magnetizer and the arc gap of the magnetic gap are not equal, and Reaching the power Purpose, only the torque it transmits will also change.
  • the relation between the logarithm 1, and the number of the magnetic conductors 46a, 46b of the magnetic conductive component 40, PN1, PN2, must be adjusted, wherein when the pole pair number R of the rotor 20 is greater than the pole pair number ST1 of the stator 30, the relationship
  • the formula is as follows:
  • pole pairs ST1, ST2 of the stator 30 in the above formulas (9) to (14) may also replace the aforementioned pole pairs ST1' or ST2' of the higher-order magnetism, respectively (that is, the equations (5) to (7) ST1, ST2 in the middle are replaced by SI, ST2') o
  • the above-described manner of applying the magnetic shifting composition of the present invention to a segmented phase drive (Split phase) or electromagnetic shifting motor will be described below.
  • the gear ratio obtained by the segmented phase drive is greater than one, and the gear ratio of the electromagnetic shift mode may be greater or less than one.
  • the stator 30 is located radially inward of the rotor 20 and the magnetically permeable assembly 99 is located between the stator 30 and the rotor 20.
  • the stator 30 has a winding arm 300.
  • the stator 30 has a total of twelve winding arms 300.
  • a winding chart or segmented phase winding table. As shown in the table below, this winding table is not used. To limit the scope of the invention.
  • this winding table When this winding table is applied to the structure without the magnetic conductive component 99 of the present invention (that is, the structure in which the magnetic conductive component 99 is removed in FIG. 12), it can be used to know the respective winding arms 300 of the stator 30. The way the winding is required and the available reduction ratio.
  • A, B, and C shown in the figure indicate the first phase winding mode and the second phase, respectively.
  • a winding method, a third phase winding method, and a, b, c respectively indicate a winding manner in which the first phase is inverted, a winding method in which the second phase is inverted, and an inversion with the third phase. Winding method.
  • the magnetic conductive component 99 When the structure of the magnetic conductive component 99 is not employed, if the magnetic number of the rotor 20 is 4 and the number of the winding arms 300 of the stator 30 is 9, and the winding is performed by the ABaCAcBCb method, a reduction ratio of 2:1 can be obtained.
  • each letter of ABaCAcBCb represents the winding mode of a winding arm 300
  • the winding arm 300 of 30 is disposed clockwise or counterclockwise.
  • the first winding arm 300 adopts a first phase winding method (A)
  • the second winding arm 300 adopts a second method.
  • the third winding arm 300 adopts a winding method (a) opposite to the first phase
  • the fourth winding arm 300 adopts a third phase winding method (C), and so on.
  • the first, second, third, and fourth winding arms 300 are sequentially adjacent to the winding arms 300 on the stator 30 in a clockwise manner.
  • the stator 30 has twelve winding arms 300. If each winding arm 300 independently winds a coil and the adjacent winding arm 300 winds a coil of a different phase, the stator 30 There will be 12 pole numbers, that is, the pole pair number ST1 of the stator 30 is 6 (the number of poles is twice the number of pole pairs).
  • the pole number R of the rotor 20 is 10 (i.e., the number of poles is 20).
  • the number of magnetic conductors PN1 of the magnetic conductive component 99 is 8, and therefore, it can be known that the number of stator side poles R2 in the gap 990 between the magnetic conductive component 99 and the stator 30 is 2 according to the following formula (15). Therefore, the number of magnetic poles on the stator side is four.
  • the winding table is checked by the stator-side magnetic pole number 4 and the number of magnetic poles 12 of the winding arm 300 of the stator, and the winding method is AcBaCbAcBaCb, which is a deceleration that can be obtained between the magnetic conductive component 99 and the stator 30.
  • the ratio is 2:1.
  • stator 30 will have 6 magnetic pole numbers to increase the variability.
  • the number of its magnetizers changes to 6 (PN2), and the number of stator-side pole pairs at this time is 4 (the formula (15), therefore, the winding table is used. At that time, the magnetic number is 8, and can produce different reduction ratios.
  • equation (15) for calculating the number of pairs of stator side poles can also be changed to the following equation (16).
  • the driving mode (or excitation mode) of the motor stator coil can be AC current mode (AC) Current) drive (such as synchronous motor drive), square wave or sine wave generated by Pulse Width Modulation (PWM) (such as the drive mode of brushless DC motor).
  • AC AC current mode
  • PWM Pulse Width Modulation
  • the magnetic shifting composition in the embodiment includes the design of the stator and the rotor of the electric motor or the generator, and has a shifting structural design, it can be easily connected to the motor driver of the electric motor or the power take-off circuit of the generator ( If the circuit such as rectification voltage regulator is integrated to form a variable speed electric motor or a variable speed generator, the integrated variable speed electric motor has the functions of generating rotational power and shifting, but the volume and weight are only about The volume and weight of the original electric motor achieve a high driving power density.
  • the magnetic shifting component uses electromagnetic shifting, which reduces vibration and noise.
  • the variable speed electric motor can meet different driving torque requirements and driving speed requirements, and can maintain high efficiency operation.
  • the magnetic shifting composition of the present invention comprises the design of the stator and the rotor of the electric motor or the generator, and has a variable-speed structural design, which can be easily connected to the motor driver of the electric motor or the power take-off circuit of the generator (such as the rectifier voltage regulator circuit M) Therefore, it integrates to form a variable speed electric motor or a variable speed generator.
  • the integrated variable speed electric motor also has the function of generating rotary power and shifting, but the volume and weight are only about the volume and weight of the original electric motor.
  • the magnetic shifting component uses electromagnetic shifting, which can reduce vibration and noise.
  • the variable speed electric motor can match different driving torques. Demand and driving speed requirements, and can maintain high efficiency operation.

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Abstract

一种磁性变速组成系适于与电动机或发电机整合。磁性变速组成具有转子、定子及导磁组件。转子与定子系同轴套设并分别具有R个及ST1个极对数。导磁组件位于转子与定子之间并具有导磁体。当导磁组件被致动时，导磁组件系选择性地使PN1个或PN2个导磁体对应于转子与定子之间。与转子及定子对应的导磁体即与R个及ST1个极对数的磁场作用而产生预定变速比。磁性变速组成与电动马达作内部整合，即可提升驱动功率密度。

Description

磁性变速组成及其分段相位驱动马达 技术领域
本发明为一种变速组成 (transmission assembly), 特别是一种磁性变速组成。 背景技术
变速器应用于动力传输， 除了能将动力进行中继与传送外， 另具有将动力 源的转速减速或增速的功能。 应用于传统汽车引擎的变速组成有机械式的变速 箱及油压式变速箱。 应用于电动车或油电混合车的则有磁性变速器。
变速马达的技术可见于公元 1976年 9月 14日公告的美国第 3,980,937号专 利（Fractional Horsepower Gear Motor》 ， 其将马达所输出的动力经过机械式齿 轮组以达到扭力转换及变速效果。
另于公元 1998年 10月 20日公告的美国第 5,825,111号专利 {(Single-phase induction motot 4/6 pole common winding connection with magnetic motive force symmetrically distributed))及公元 2009年 10月 6日公告的美国第 7，598，648号 专禾!] 《2/6 pole single-phase induction motor having shared windings》 ， 公开禾 ij用 改变感应马达定子的极数的方式来达成变速的目的。
磁性变速器的相关技术亦可见于由 K. Atallah及 D. Howe于国际电机电子 工程师学会期刊在公元 200〖 年 7 月发表的文章《A Novel High-Performance Magnetic Gear》 (IEEE Transactions on Magnetics, Vol. 37， No. 4, July, 2001)。
前述机械式变速器有噪音大与重量重的缺点， 而一般磁性变速器虽可减少 振动与噪音， 但亦不能减少重量。 此外， 在电动车的应用上， 电动马达须配合 不同的行车扭力及行驶速度的需求， 亦须兼顾高效率运转的要求， 故常将马达 与变速器搭配， 在此种搭配模式下， 马达与变速器整体的驱动功率密度通常不 易提高 (因马达与变速器的总重量重)。 发明公开
基于上述问题，所提出的磁性变速组成易与电动机 (如电动马达)或发电机做 内部整合而具有重量轻的特色， 故能提高驱动功率密度。
依据一实施例， 一种磁性变速组成包含转子、 定子及导磁组件。 转子与定 子同轴套设， 转子具有多个磁极并具有 R个极对数。 定子具有多个磁极及 STI 个极对数。 导磁组件位于转子与定子之间并具有多个导^体。 当导磁组件被致 动时,导磁组件选择性地使 PN1个或 PN2个该些导磁体对应于转子与定子之间， 其中， PN1-3 ≤ R+ST1 ≤ PN1+3 , PN2-3 ≤ +ST1 ≤ PN2+3。
依据导磁组件的一实施例， 前述导磁组件包含第一环及第二环， 第一环与 第二环轴向连接， 第一环具有 PN1个导磁子块， 第二环具有 PN2个导磁子块， 当导磁组件被轴向致动时， 导磁组件选择性地使第一环或第二环被移至转子与 定子之间。
依据导磁组件的第二实施例， 前述导磁组件包含第一环及第二环， 第一环 位于第二环的径向外侧且第一环与第二环配置于定子与转子之间， 当导磁组件 被致动时， 第一环与第二环相对位移于第一位置与第二位置之间， 当第一环与 第二环位于第一位置时， 导磁组件具有 PN1个该导磁体， 当第一环与第二环位 于第二位置时， 导磁组件具有 PN2个该导磁体。
依据另一实施例， 定子包含多个感应线圈及极数调变电路， 感应线圈被导 电时形成磁极， 而极数调变电路选择性地切换感应线圈于前述 ST1个极对数及 一 ST2个极对数之间。 其中， PN2-3 ≤ R+ST2 ≤ ΡΝ2· 。
依据又一实施例， 磁性变速组成包含转子、 定子及导磁组件。 转子具有多 个磁极， 转子的磁极具有 R个极对数。 定子与转子同轴套设， 定子并具有多个 磁极， 定子的磁极具有 ST1个极对数。 导磁组件被配置于转子与定子之间并具 有 PN1个导磁子块， PN1个导磁子块对应配置于转子与定子之间，其中， PN1-3 ≤ R+ST1 ≤ ΡΝ1+3。
前述导磁组件配置于定子与转子之间， 藉由导磁组件可选择性地变动导磁 体数量 (意即其磁隙数量亦变动)的设计，即可在定子与转子间产生不同的变速比 (定子转速比转子转速)。其次， 在另一实施例中， 定子的磁对数亦具有可变换的 设计， 如此一来， 搭配导磁组件与转子， 亦能达到产生不同变速比的目的。 前 述的导磁组件、 定子及转子均可为中空环形的设计， 使得整个磁性变速组成的 体积及重量都相当小， 并能够易于与电动马达做内部整合， 得到较高的驱动功 率密度 (瓦 /公斤， W/Kg或瓦 /体积, W/m3)0
有关本发明的特征与实施例， 兹配合附图及实施例说明如下。 附图简要说明 图 1为依据本发明磁性变速组成第一实施例的立体结构示意图； 图 2为依据本发明磁性变速组成第一实施例的立体分解示意图； 图 3为依据本发明磁性变速组成第一实施例的定子的磁对数示意图； 图 4A为依据本发明磁性变速组成第一实施例的导磁组件的剖面示意图； 图 4B为图 4A的导磁组件第一实施例的局部放大剖面示意图；
图 4C为图 4A的导磁组件的第一实施例另一局部放大剖面示意图； 图 5A为依据本发明磁性变速组成的定子的另一实施例的绕线示意图； 图 5B为图 5A的定子的另一实施例的动作示意图；
图 6为图 5A及图 5B极对数切换的示意图；
图 7A、 图 7B及图 7C为依据本发明磁性变速组成的导磁组件的第二实施 例示意图；
图 8为依据本发明磁性变速组成的导磁组件的第三实施例示意图； 图 9为依据本发明磁性变速组成第二实施例的立体分解示意图； 图 10A为依据本发明磁性变速组成的导磁组件的第四实施例示意图； 图 10B及图 10C分别为图 10A在 10B-10B位置的局部剖面示意图及状态 示意图；
图 11A为依据本发明磁性变速组成的导磁组件的第四实施例示意图； 图 11B及图 11C分别为图 11A在 11B-11B位置的局部剖面示意图及状态 示意图；
图 1 1D为图 11B的另一状态示意图；
图 12为依据本发明应用于分段相位驱动马达的结构示意图。
其中， 附图标记-
20转子
30定子
300 绕线臂
32a, 32b 凸块
34a, 34b, 34c, 34d 感应线圈
35a, 35b 线圈组
36极数调变电路
360, 362 切换开关 40， 50, 60, 70， 80， 90， 99 导磁组件
42, 52， 62, 82， 92 第一环
420， 422， 440， 442 导磁子块
429, 449 弧段
44， 54， 64， 84， 94 第二环
46a, 46b 导磁体
48a, 48b, 48c, 48d 磁隙
53， 55, 57, 59 导磁子块
51a, 51b, 51c, 51d 导磁体
56, 96 第三环
58第四环
63, 65, 72 导磁子块
66a, 66b, 66c, 74a, 74b 电绝缘组件
820, 840, 920， 940, 960导磁子块
88致动组件
990 空隙 实现本发明的最佳方式
首先， 请同时参阅图 1及图 2, 其分别为依据本发明一实施例的立体结构 示意图及立体分解图。 图中可以见悉， 磁性变速组成包含转子 20、 定子 30及 导磁组件 40(亦可称为导磁变速组件)。 磁性变速组成可适于与电动机 (如电动马 达)或发电机进行整合。 例如若与电动车的电动马达进行整合， 由马达驱动器输 出电力予磁性变速组成， 则磁性变速组成即能从转子处产生旋转动力， 同时， 由马达驱动器适当地控制磁性变速组成的变速比， 磁性变速组成即能输出不同 的功率 (功率 =驱出扭力 X转速)。 由于此磁性变速组成同时包含了电动机与变速 器的功能， 整体体积及重量较低， 因而能得到较高的驱动功率密度。 此处的驱 动功率密度可以是但不限于输出功率除以体积，或者是输出功率除以重量 (即 (输 出扭力 X转速) /体积、 或 (输出扭力 X转速) /重量)。
其次，若是将磁性变速组成应用于电动机中，则可由转子 20承接旋转动力， 定子 30的线圈 (容后详述)即可输出经磁场切割所产生的电力。 此电力可经过整 流及稳压电路后输出。 由于磁性变速组成可以经由控制而产生变速比， 故当输 入的旋转动力有较大的变动， 或者欲得到较佳的系统转换效率， 可以由控制器 调整磁性变速组成的变速比来达成。 '
请续参阅图 1及图 2， 定子 30可为固定磁铁或感应磁铁 (或称电磁铁)， 在 本实施例中以感应磁铁为例。 定子 30的内侧环形配置有多个凸块 32a，32b。 各 凸块 32a， 32b缠绕有感应线圈 (容后详述)， 感应线圈被通电时， 即可形成磁极。 以图式的实施例为例，定子 30具有 48个凸块 32a， 32b，每个凸块 32a， 32b被通 电后即可形成一磁极对。在此例中， 共有四相 (4 phases), 每一相即有 12个极对 数 (20 Pole Pairs) 请同时参照图 3， 其为依据本发明一实施例的定子 30的磁对 数示意图。 图中可以看出，相邻的磁极为相反极性 (磁北极 N与磁南极 S)。二个 相邻相反极性的磁极为一磁对 (例如图式的 Sl， N1为一磁对)。 从图中可以看出 共有 12个极对数， 此极对数仅为一实施态样， 本发明并不限于此磁对数， 以下 以 ST1个极对数表示。
转子 20可为固定磁铁或感应磁铁， 在本实施例中， 转子 20以固定磁铁为 例进行说明。 转子 20具有多个磁极并具有 R个极对数， 在本实施例中， 转子 20以具有 20个极对数为例。定子 30与转子 20同轴配置 (同轴套设)， 且在此实 施例中， 转子 20配置于定子 30的径向内侧， 但并不以此为限。 亦可将定子 30 配置于转子 20的径向内侧， 仍能达到本发明的目的。 其次， 转子 20的磁极 (磁 力线)的方向朝向定子 30的磁极 (磁力线)的方向。
导磁组件 40 可以是薄片钢 (laminated steel), 其材料可以是软磁材料 (Soft
Magnetic Composite, SMC)， 以减少涡电流 (Eddy Current)及铁损。
请再参阅图 1及图 2， 导磁组件 40包含第一环 42及第二环 44。 第一环 42 位于第二环 44的径向外侧， 且第一环 42与第二环 44配置于定子 30与转子 20 之间。第一环 42与第二环 44可相互接触或相距一间隙 (图系采相距一间隙方式 实施)。 第一环 42具有多个导磁子块 420， 422。 第二环 44亦具有多个导磁子块 440, 442。当第一环 42位于第二环 44的径向外侧时，导磁子块 420, 422, 440, 442 即可形成多个导磁体 (容后详述)。 当第一环 42或 /与第二环 44被致动时， 两者 可相对运动 (相对转动)于第一位置及第二位置之间，此时，导磁体的数量亦会随 之变化， 如下说明。
请参考图 4A。 图 4A为依据本发明一实施例的导磁组件第一实施例的剖面 示意图。 此剖面示意图为图 2中的第一环 42套于第二环 44径向外侧后， 依垂 直于轴向的平面为切面所为的剖面示意图。 为了便于说明第一环 42 与第二环 44的相对转动的动作，兹再将图 4A中标示为 429及 449的弧段于图 4B进行放 大。 弧段 429， 449所夹的弧角为 45度， 故整个第一环 42与第二环 44则共有 8 个弧段 429, 449。图 4B为第一环 42与第二环 44位于第一位置的状态的局部放 大剖面示意图。图 4C则为第一环 42与第二环 44位于第二位置的状态的局部放 大剖面示意图。
从图 4B中可以见悉， 第一环 42的导磁子块 420与第二环 44的导磁子块 440呈相连状态 (或重迭)并形成导磁体 46a。 同样地， 第一环 42的导磁子块 422 与第二环 44的导磁子块 442呈相连状态并形成导磁体 46b。而在导磁体 46a, 46b 之间即具有三个磁隙 48a， 48b, 48c。由于整个第一环 42与第二环 44具有相同的 8个弧段 429, 449,故整个第一环 42与第二环 44则会有 24个磁隙 48a, 48b, 48c(3 X 8=24, 亦即具有 24个导磁体 46a, 46b)。
续请参阅图 4C，此为第一环 42与第二环 44位于第二位置的状态的局部放 大剖面示意图。 第一环 42的导磁子块 420与第二环 44的导磁子块 440呈相连 状态并形成导磁体 46a。同样地，第一环 42的导磁子块 422与第二环 44的导磁 子块 442呈相连状态并形成导磁体 46b。 从图中可以看出， 弧段 429， 449内有 四个磁隙 48a，48b, 48c，48d， 亦具有四个导磁体 46a, 46b。是以， 整个第一环 42 与第二环 44则会有 32个 (4 X 8=32)磁隙 48a, 48b, 48c, 48d。
前述导磁子块 420, 440呈相连状态系指距离相近，而非仅指相接触的状态， 距离相近亦可为导磁子块 420， 440两者不相接触但在径向上重迭， 或者导磁子 块 420， 440不相接触且径向上或圆周方向上有一间距。申言之，若导磁子块 420， 440未相接触， 则导磁子块 420， 440之间有二个距离， 其一为径向距离， 其二 为沿圆周方向的距离。 就前者的径向距离而言， 经实验， 若该径向距离在 5毫 米 (mm)以内， 均能达到形成单一导磁体 46a 的效果。 当然此距离亦与定子 30 磁力线的强度有关， 若磁力线强度愈强， 此距离可以愈大。 也就是说， 此径向 距离可视磁性变速组成本身的大小及磁力线强度做改变。
就前述后者的圆周方向的距离 (弧长)亦可表述为导磁子块 420， 440边界对 应到圆心 (定子圆心)的夹角， 例如以图 4B为例， 导磁子块 420的左侧边与导磁 子块 440的右侧边的夹角。 为能进一步定义此夹角或弧长， 兹将导磁子块 420 的左侧边与导磁子块 440的右侧边的距离所形成的空间定义为气缝。 由于磁性 变速组成在运作时， 每个磁隙 48a， 48b, 48c (图 4B)会产生一个磁极 (；以下称磁隙 磁极)，当导磁子块 420， 440间具有气缝时，此气缝亦会具有磁极 (以下称气缝磁 极)， 为能让导磁子块 420, 440形成前导磁体 46a的效果， 此气缝磁极的磁场强 度较佳者为小于气隙磁极的磁场强度的百分的二十 (20%)。再经由此气缝磁极的 磁场强度所回推而得的该弧长或该夹角则为较佳的圆周方向的间距。
导磁子块 420， 422, 440， 442的材料可选用任何可导磁的材料， 例如铁基的 材料或软铁。 前述第一环 42与第二环 44的相对运动的驱动方式可釆用机械式 或电磁式方式驱动。 而驱动时， 可单独驱动第一环 42或第二环 44， 或者是第 一环 42与第二环 44同时驱动， 只要能使得第一环 42与第二环 44的相对位置 能位移于第一位置与第二位置之间即可。
综合图 4B与图 4C的说明可知， 当导磁组件 40被致动时， 第一环 42与第 二环 44相对运动于第一位置 (如图 4B的位置)与第二位置 (如图 4C的位置)之间， 当第一环 42与第二环 44位于第一位置时， 导磁组件 40具有 24个 (以下称 PN1 个)导磁体 46a， 46b, 当第一环 42与第二环 44位于第二位置时， 导磁组件 40具 有 32个（以下称 PN2个)导磁体 46a， 46b。
导磁组件 40藉由第一环 42与第二环 44可相对运动的设计， 导磁组件 40 可选择性地使 PN1个或 PN2个导磁体 46a， 46b对应于转子 20与定子 30之间。 藉由 PN1个或 PN2个导磁体 46a， 46b配合转子 20的磁场与定子 30的磁场，即 可产生一个增减速 (变速)的效果。 此增减速比可由下述计算公式 (1)而得：
G = ΜΡ ,
mP + kn\ 式 (i) 其中， G为变速比 (即增减速比)， m，k为简谐波 (harmonics)级数， p为转子 20的极对数 (pole pairs) n为导磁体 46a, 46b的数目 (number of steel pieces)。 于 主简谐波 (fundamental harmonics)状态下， m=-k=l， 而本实施例中， 转子 20的 极对数为 20, 以第一环 42与第二环 44位于第一位置为例， 导磁体 46a， 46b的 数量为 24， 套入上列公式， 可得 G=(1 X 20)/(1 X 24-1 X 20)=5， 即定子的转速比 上转子的转速为 5:1。 若以第一环 42与第二环 44位于第二位置为例， 导磁体 46a， 46b的数量为 32, 套入上列公式， 可得 G=(l X20)/(l X 32-1 X 20)=1.6， 即 定子 30的转速比上转子 20的转速为 1.6:1。
由此可知， 藉由导磁组件 40、 定子 30与转子 20的适当配置与设计， 即可 使得磁性变速组成具有变速的效果。
其次， 为了能进一步提升变速比的稳定性， 经实验可得定子 30 的极对数 ST1、 转子 20的极对数 R、 及导磁组件 40的导磁体 46a， 46b的数量 PN1, PN2 维持在下述关系， 将可得到稳定的变速比与驱动力：
PN1-3 ≤ R+ST1 ≤ PN1+3 式 (2)
PN2-3 ≤ R+ST1 ≤ PN2+3 式 (3)
以本实施例为例， 导磁组件 40位于第二位置时， 恰满足式 (3) PN2-3 ≤ R+ST1 ≤ PN2+3。 而导磁组件 40位于第一位置时， 则虽未能满足式 (2) PN1-3 ≤ R+ST1 ≤ PN1+3 , 但仍属能变速的要求。 而在本实施例中， 若欲同时满足 式 (2)与式 (3)， 则可以利用修改导磁组件 40的导磁子块 420， 422, 440, 442的设 计， 使得能满足式 (2)即可， 例如， 若 ST1为 12， 而 PN1与 PN2分别为 35及 29即同时满足上式 (2)与 (3)。
在本实施例中， 若不变更导磁组件 40的设计， 欲同时满足式 (2)与式 (3) (但 式 (3)须做些微变动， 容后详述)， 则可使用图 5A及图 5B的定子 30的实施例。 图 5A为依据本发明磁性变速组成的定子 30的另一实施例的绕线示意图。图 5B 为图 5A的定子 30的另一实施例的动作示意图。
从图中可以见悉， 定子 30的另一实施例包含多个感应线圈 34a, 34b, 34c, 34d及极数调变电路 36。感应线圈 34a， 34b, 34c, 34d分别绕于凸块 32a， 32b。在 图 5A及图 5B中仅绘制三个磁极对 ( l， N2, N3, SI, S2， S3)的感应线圈 34a, 34b, 34c, 34d,但并不表示定子 30仅包含感应线圈 34a, 34b, 34c, 34d。极数调变电路 36包含二个切换开关 360， 362。 当切换开关 360， 362位于图 5A的状态并通入 电源时， 各感应线圈 34a, 34b, 34c, 34d所形成的磁极即如图 3所示的极性， 意 即定子 30共具有 12个极对数。当切换开关 360, 362位于图 5B的状态并通入电 源时， 原形成 N1, S3的感应线圈 34c, 34d因反向通入电源， 故所形成的磁极即 会相反 (即 N1变为磁南极， S3变为磁北极)， 请参阅图 6， 其为图 5A及图 5B 极对数切换的示意图。
图中可以见悉，虚线框中所表示的即为切换开关 360， 362位于图 5B时，所 形成的磁极极性的示意图。图中 Nl, N4， N7， N10在图 5A中为磁北极， S3, S6, S9, S12在图 5A中为磁南极， 此时定子 30共具有 12个 (以下称 ST1个)极对数 (即 Nl, S1, N2, S3...N12, S12), 但是在图 5B中， 因为切换开关 360, 362及电路的 巧妙设置， 使得 N1，N4，N7，N10通电后变为磁南极， 而 S3， S6， S9， S12则变为 磁北极，其余维持不变，是以定子 30共具有 4个 (以下称 ST2个)极对数 (如虚线 框 ΝΓ, S1', N2'，S2'，N3'， S3', N4'， S4'所示)。 换句话说， 当感应线圈 34a， 34b， 34c, 34d被切换至 STl个极对数时，相邻的感应线圈 34a, 34b, 34c, 34d的极性 (磁 极性)系相反， 当感应线圈 34a，34b，34c，34d被切换至 ST2个极对数时， 感应线 圈 34a, 34b, 34c, 34d被群组为多个线圈组 35a， 35b,且相邻的线圈组 35a, 35b的 极性相反。 在此实施例中， 每一线圈组 35a， 35b包含三个依序相邻的感应线圈 34a, 34b, 34c, 34d。 此处的依序相邻系为相连接的， 例如图 5B中的 SI, Nl, S2 即属依序相邻的感应线圈 34a, 34b, 34c, 34d。
综上说明， 定子 30藉由极数调变电路 36而能选择性地切换感应线圈 34a, 34b, 34c, 34d于 12个 (STl个)极对数及 4个 (ST2个)极对数之间。 将图 5A的定 子 30实施例与导磁组件 40导磁体数量的切换整合后， 即可得到如下表的变速 比 (定子转数： 转子转速)， 并满足上述式 (2)与下式 (4)。
PN2-3 ≤ R+ST2 ≤ PN2+3 式 (4)
Figure imgf000011_0001
极数调变电路 36虽仅以图 5A为实施例之一， 但并不以此为限。 经过适当 电路及开关设计， 可以使定子 30的极对数有不同比例的增减。 除此之外， 定子 30 的绕线方式亦可以用更为复杂且多样的设计， 例如采用一个绕线表 (winding chart)的方式， 以得到更多样的极对数需求， 此绕线方式可以是但不限于 LRK (Lucas, Retzbach and Ktihf ss)绕线方式、 或 D-LRK (distributed LRK)绕线方式、 或 ABC绕线方式， 关于此应用， 容后详述。
关于前述图 4A导磁组件 40的其它实施方式， 可见于图 7A、 图 7B、 及图 7C。图 7A及图 7B、及图 7C的导磁组件 50(第二实施例)为类似图 4B的示意方 式。 图中可以见悉， 导磁组件 50包含第一环 52、 第二环 54、 第三环 56及第四 环 58。 第一环 52、 第二环 54、 第三环 56及第四环 58径向迭置并分别具有导 磁子块 53， 55, 57， 59(亦可分别称第一、 第二、 第三、 第四导磁子块：)。 当导磁组 件 50位于图 7A的位置时 (第一位置)，导磁子块 53， 55, 57, 59间有相连接关系， 使得在此弧段中即具有二个导磁体 51a， 51b及二个磁隙 (磁隙即为导磁体在圆周 方向上所分隔出来的空隙)。 当导磁组件 50位于图 7B的位置时 (第二位置)， 导 磁子块 53， 55, 57, 59间则相互分离，使得在此弧段中即具有四个导磁体 51a, 51b, 51c，51d及四个磁隙。 此外， 当导磁组件 50位于如图 7C所示位置时 (亦可称为 第三位置)， 其导磁子块 53， 55, 57, 59呈在径向完全重迭的状态， 此时， 导磁组 件 50即具有二个导磁体 51a, 51b及二个磁隙， 所导磁组件 50在图 7A及图 7C 的位置时， 虽然所得到的导磁体 51a， 51b的数量相同， 但其磁通量不同， 因此， 所能传递的扭力亦随之变化， 因此， 导磁组件 50可以经由适当的设计及控制， 即可改变其变速比， 亦可改变其所传递的扭力。
从上述图 4A与图 7A的导磁组件 40， 50同样采用多个环状 (圆筒状)的导磁 环 (即前述第一环 42， 52等:)径向迭置， 导磁环的数量可依实际设计的需求而变 动， 意即可以有三个或五个导磁环的结合设计， 但并不限于此数量。 导磁环中 的导磁子块的尺寸、排列及数量亦可经由适当地设计而能产生不同数量的磁隙， 藉以得到所需的变数比。 '
续参阅图 8， 其为依据本发明磁性变速组成的导磁组件的第三实施例示意 图。 此导磁组件 60包含第一环 62与第二环 64。 第一环 62与第二环 64轴向连 接。导磁组件 60配置于前述定子 30与转子 20之间。第一环 62与第二环 64可 在定子 30与转子 20间轴向移动， 使得在同一时间内， 仅会有第一环 62及第二 环 64其中之一被夹置于定子 30与转子 20内。 易言之， 当导磁组件 60被轴向 致动时， 导磁组件 60选择性地使第一环 62或第二环 64移至转子 20与定子 30 之间。 前述被夹置的第一环 62或第二环 64方能与定子 30与转子 20的磁场产 生作用，而具有特定变速比。前述第一环 62导磁子块 63的数量 (例如 PN1个导 磁子块)相异于第二环 64导磁子块 65的数量 (例如 PN2个导磁子块)。 在图 8实 施例中， 第一环 62导磁子块 63的数量为 32， 而第二环 64导磁子块 65的数量 为 24， 即为适于置换图 1实施例中的导磁组件 40。在本实施例中的每一导磁子 块 63， 65即分别形成并等效于图 4B与图 4C中的导磁体 46a, 46b 0 如上所述， 第一环 62及第二环 64同轴连接， 请再参阅图 8， 第一环 62及 第二环 64藉由一电绝缘组件 66a而同轴连接。同时在第一环 62与第二环 64的 二个外侧端亦分别具有电绝缘组件 66b, 66c0电绝缘组件 66a， 66b, 66c用以固定 第二环 64的导磁子块 65及第一环 62的导磁子块 63。
再者， 请续参阅图 9， 其为依据本发明磁性变速组成第二实施例的立体分 解示意图。 从图中可以得知， 磁性变速组成包含转子 20、 定子 30及导磁组件 70。 转子 20具有多个磁极， 转子 20的磁极具有 R个极对数。 定子 30与转子 20同轴套设， 定子 30并具有多个磁极， 定子 30的磁极具有 ST1个极对数。 导 磁组件 70被配置于转子 20与定子 30之间并具有 PN1个导磁子块 72(亦可称导 磁体 )， PN1个导磁子块 72对应配置于转子 20与定子 30之间，其中， PN1-3 ≤ R+ST1 ≤ ΡΝ1+3。 因此， 当 R为 20、 PN1为 32而 ST1为 12时， 此磁性变速 组成的加减速比即为 1.6: 1(依据上述式 (1))。
其次，从图 9可以见悉，导磁子块 72的两端由电绝缘组件 74a, 74b而固定， 因此，导磁子块 72因切割定子 30与转子 20磁场而感应的电流将会被限制于每 个导磁子块 72内而不致泄漏。
依据图 9的实施例， 每一导磁组件 70、 定子 30及转子 20均为中空环形的 设计， 使得整个磁性变速组成的体积及重量都相当小， 并能够易于与电动马达 做内部整合， 得到较高的驱动功率密度 (瓦 /公斤， W/Kg或瓦 /体积, W/m3)。 依据 前述实施例， 经由导磁组件 40， 50， 60的不同实施态样， 即可使得磁性变速组成 能切换于不同的变速比之间。接着， 若在导磁组件 40， 50, 60所能切换的导磁体 46a, 46b, 51a, 51b, 51c, 51d的数量未能符合式 (2)及式 (3)时，则亦可采用图 5A的 定子 30的实施态样 (符合式 (2)与式 (4))， 而能提高不同变速比状态下的稳定性。
再者， 关于前述式 (2)、 式 (3)、 及式 (4)， 其以定子 30的主简谐波为基础所 列的关系式， 而若将该些关系式中的定子 30 的极对数以高阶导磁性简谐波 (higher-order permeance harmonics)进行设计， 贝1 J可得下述关系式：
PN1-3 ≤ R+ST1 ' ≤ PN1+3 式 (5)
PN2-3 ≤ R+ST1 ' ≤ PN2+3 式 (6)
PN2-3 ≤ R+ST2' ≤ PN2+3 式 (7)
其中， ST1，及 ST2'分别为定子 30的高阶导磁的极对数。 举例而言， 若定 子 30的主简谐波的极对数为 4， 则其三阶导磁 (the third permeance harmonics)的 极对数即为 12，因此，在设计转子 20的极对数 R、及导磁组件 40的导磁体 46a， 46b的数量 PN1， PN2时则有更大的弹性选择空间。
此外， 在上述关系式中， 定子 30所产生的磁场除了采用与转子 20的极对 数 R及导磁组件 40的导磁 46a， 46b同步方式之外，亦可采用异步的设计。当然， 亦可藉由控制定子 30的极对数及 /或导磁组件 40而在同步与异步之间做切换。
接着， 请续参考图 10A、 图 10B、 及图 10C：， 其分别为依据本发明磁性变 速组成的导磁组件的第四实施例示意图、图 10A在 10B-10B位置的局部剖面示 意图及动作示意图。
图中可以见悉， 导磁组件 80包含有第一环 82及第二环 84。 第一环 82具 有多个相互平行、 呈条状并以环形方式排列的导磁子块 820(亦可称第一导磁子 块)。 第二环 84 亦包含多个相互平行、 呈条状并以环形方式排列的导磁子块 840(亦可称第二导磁子块)。 第一环 82的导磁子块 820与第二环 84的导磁子块 840在径向交互列置并夹置于于定子 30与转子 20(请参阅图 1)之间。 意即第一 环 82的导磁子块 820与第二环 84的导磁子块 840位于相同或相接近的半径位 置， 此点可以从图 10B中看出。
图 10B为图 I0A在 10B-I0B位置的局部剖面图，此局部剖面的方式类似于 图 4B与图 2及图 4A的剖面关系。 意即， 图 10B所示意的仅为图 10A部分弧 段的剖面图。
图 10B示意导磁组件 80的第一环 82与第二环 84位于第一位置的状态，在 此第一位置时，导磁子块 820, 840相互之间均具有一个距离，且各导磁子块 820, 840 自成一个导磁体。 此处所述的距离在附图中虽呈等距状态， 但并不以此为 限，只要两两导磁子块 820， 840间形成前述的气隙，而使得相邻的导磁子块 820, 840不形成前述的导磁体作用时， 即可， 即使导磁子块 820, 840间的距离非等 距亦可。
而在图 10C中则示意导磁组件 80的第一环 82与第二环 84位于第二位置的 状态， 在第二位置时， 二相邻的导磁子块 820, 840相互靠拢， 使得两两靠拢的 导磁子块 820， 840形成一个导磁体。 此处所述的靠拢指两相邻的导磁子块 820, 840之间的距离足够小到使该两相邻的导磁子块 820， 840形成单一导磁体的状 态。
从图 10B及图 10C可以得知，在图 10B所形成的导磁体数量为图 10C的导 磁体数量的两倍。 因此， 导磁组件 80可以经由控制而改变其导磁体数量。
关于控制导磁组件 80变化其导磁体数量的致动组件 88(请参阅图 10A)，可 以采用电动马达或气压阀等组件。此致动组件 88亦可应用于图 1、图 7A、图 8、 及图 11A的实施例中。 当然， 若将此致动组件 88改成固定式， 由人工拨动控 制亦可。
续， 请参阅图 11A、 图 11B、 及图 11C， 其分别为依据本发明磁性变速组 成的导磁组件的第四实施例示意图、图 11A在 11B-11B位置的局部剖面示意图 及动作示意图。 其图式表示方式与图 10A、 图 10B、 及图 10C相似， 故不再赘 述。
从图中可以看出导磁组件 80的第四实施例包含第一环 92、 第二环 94、 及 第三环 96。第一环 92、第二环 94及第三环 96分别具有多个导磁子块 920, 940， 960(亦可分别称为第一、 第二、 第三导磁子块)， 第一导磁子块 920、 第二导磁 子块 940、 及第三导磁子块 960在径向依序列置并被夹置于该定子 30与该转子 20之间，各导磁子块 920, 940, 960位于相同或相接近的半径位置 (即距离圆心的 半径相当)， 因此， 当第一环 92、 第二环 94及第三环 96位于如图 11B所示的 第一位置时， 各导磁子块 920, 940, 960各自成为一个独立的导磁体， 使此导磁 组件 90具有 PN1个导磁体，而第一环 92、第二环 94及第三环 96位于如图 1 1C 所示的第二位置时， 相邻的三个导磁子块 920， 940, 960相互靠拢并形成一个导 磁体， 使此导磁组件 90具有 PN2个导磁体， 因此， 位于第一位置的导磁组件 90所形成的导磁体的数量 PN1为位于第二位置的导磁体的数量 PN2的三倍。
除此之外， 请参阅图 11D, 其为第一环 92、 第二环 94及第三环 96位于第 三位置的示意图， 图中可以看见， 第三环 96的导磁子块 960与第二环 94的导 磁子块 940相互靠拢， 而第一环 92的导磁子块 920则未与 (第二、 第三)导磁子 块 940， 960靠拢 (或称接近或接触)，因此,靠拢的导磁子块 940， 960形成导磁体， 而 (第一：)导磁子块 920则独立形成一个导磁体，使导磁组件 90具有 PN3个导磁 体， 是以图 11D所形成的导磁体的数量 PN3为图 11C所形成导磁体数量 PN2 的二倍。 其中 PN3可满足下式 (5):
PN3-3 ≤ R+ST1 ≤ PN3+3 式 (8)
再者， 第一环 92、 第二环 94及第三环 96的相对位置亦可采用非等距的方 式排列， 而使得导磁体所占弧长与磁隙所占弧长不相等， 亦能达到传递动力的 目的， 唯其所传递的扭矩亦将有所变动。
关于前述式 (1)中 m与 k的关系，除了上述的 m=-k=l之外，亦可采用 m=k=l， 如此一来， 定子 30的极对数 ST1、 转子 20的极对数1、 及导磁组件 40的导磁 体 46a, 46b的数量 PN1，PN2的关系式即须进行调整， 其中， 当转子 20的极对 数 R大于定子 30的极对数 ST1时， 其关系式如下：
R-3 ≤ PN1+ST1 ≤ R+3 式 (9)
R-3 ≤ PN2+ST1 ≤ R+3 式（10)
R-3 ≤ PN3+ST1 ≤ R+3 式（11)
PN3-3 ≤ R+ST1 ≤ PN3+3、 或 R- 3 ≤ PN3+ST1 ≤ R+3、 或 ST1-3 ≤ PN3+R ≤ STl+3。
当当转子 20的极对数 R小于定子 30的极对数 ST1时， 其关系式如下：
ST1-3 ≤ PN1+R ≤ ST1+3 式 (12)
ST1-3 ≤ PN2+R ≤ ST1+3 式（13)
ST1-3 ≤ PN3+R ≤ ST1+3 式（14)
上述式 (9)到式 (14)中的定子 30极对数 ST1， ST2亦可分别替换前述的高阶导 磁的极对数 ST1'或 ST2' (即将式 (5)到式 (7)中的 ST1, ST2替换为 SI , ST2')o 最后， 关于前述将本发明的磁性变速组成应用于分段相位驱动 (Split phase) 或电磁变速的马达的方式， 兹说明如下。 其中分段相位驱动所得到的变速比大 于 1 , 而电磁变速方式的变速比则可能大于或小于 1。
请搭配图 12阅览之。 图中可以见悉， 定子 30是位于转子 20的径向内侧， 而导磁组件 99则位于定子 30与转子 20之间。 定子 30具有绕线臂 300， 从图 中可以看出， 定子 30共有 12个绕线臂 300。 在使用传统的分段相位驱动 (Split phase)或电磁变速的马达时， 须参考一绕线表 (winding chart, 或称分段相位绕线 表)， 如下表所示， 此绕线表并非用以限制本发明的范围。
Figure imgf000016_0001
6 无 无 ABCABCABC 无 3:1
8 ABC ABCABC AaABbBCcC ABCABCABCABC 4:1
AabBCcaABbcC
10 ABC AbCaBc AaABbBCcC 5:1
A-b-C-a-B-c
12 无 无 ABCABCABC 无 6:1
AacCBbaACcbB
14 ABC AcBaCb ACaBAbCBc 7:1
A-b-C-a-B-c
16 ABC ABCABC AAbCCaBBc ABCABCABCABC 8:1
18 无 无 无 无 9:1
20 ABC ABCABC AbbCaaBcc AbCaBcAbCaBc 10: 1
Figure imgf000017_0001
当将此绕线表应用于未有本发明的导磁组件 99的结构下 (也就是将图 12中 的导磁组件 99移除的结构)， 可用以得知定子 30的各绕线臂 300所需绕线的方 式及可得的减速比。 图中所示的 A，B, C分别表示第一相位绕线方式、第二相位 绕线方式、 第三相位绕线方式， 而 a, b, c则分别表示与第一相位反相的绕线方 式、 与第二相位反相的绕线方式、 及与第三相位反相的绕线方式。 在未采用导 磁组件 99的结构时， 若转子 20的磁数为 4， 而定子 30绕线臂 300的数量为 9， 且其采用 ABaCAcBCb方式绕线， 则可得到 2:1的减速比。
其中 ABaCAcBCb每个字母均代表一个绕线臂 300的绕线方式， 并依定子
30的绕线臂 300采顺时针或逆时针方式配置， 以上述 ABaCAcBCb绕线方式为 例， 第一绕线臂 300采用第一相位绕线方式 (A)、 第二绕线臂 300采用第二相位 绕线方式、 第三绕线臂 300采用与第一相位相反的绕线方式 (a)、 而第四绕线臂 300则采用第三相位绕线方式 (C)， 以下依此类推。 前述第一、 二、 三、 四绕线 臂 300在定子 30上依顺时针方式依序相邻的绕线臂 300。
请再参考图 12的应用例， 其定子 30具有 12个绕线臂 300， 若每一个绕线 臂 300独立绕设线圈且相邻绕线臂 300绕设不同相位的线圈时，则此定子 30将 具有 12个磁极数，亦即定子 30的极对数 ST1为 6(磁极数为极对数的两倍)。而 转子 20的极对数 R为 10(即磁极数为 20)。 导磁组件 99的导磁体的数量 PN1 为 8， 因此， 依下述式 (15)可以得知在导磁组件 99与定子 30之间的空隙 990中 的定子侧极对数 R2即为 2。 是以该定子侧磁极数为 4。
R2 = |R-PN1| 式 (15)
接着，以该定子侧磁极数 4与定子的绕线臂 300的磁极数 12查上述绕线表， 可得到其绕线方式为 AcBaCbAcBaCb, 是以在导磁组件 99与定子 30间可得到 的减速比为 2:1， 另外， 在转子 20 与导磁组件 99 间的减速比则为 5 (R/R2=10/2=5)，是以图 12的整个分段相位驱动马达的减速比将达到 10:1 (即 2:1 乘上 5:1)。
此外，若将上述定子 30中两两相邻的绕线臂 300视为一绕线臂组并绕有相 同相位的绕线， 则定子 30将具有 6个磁极数， 而增加其变化性。
其次， 上述的导磁组件 99若经由致动后， 其导磁体的数量变化为 6(PN2)， 此时的定子侧极对数即为 4(套用式 (15)， 因此， 使用绕线表时， 磁数即为 8， 而 能够产生不同的减速比。
再者， 用以计算定子侧极对数的式 (15)亦可变化为下式 (16)。
R2 = R+PN1 式 (16)
前述马达定子线圈的驱动方式 (或称激磁方式)可以采用交流电流方式 (AC current)驱动（如同步马达方式驱动）， 亦可采用脉冲宽度调变 (Pulse Width Modulation, PWM)方式所产生的方波或弦波 (如无刷直流马达的驱动方式)。
综上所述， 由于实施例中的磁性变速组成包含了电动马达或发电机的定子 与转子的设计， 并具有变速的结构设计， 能易于与电动马达的马达驱动器或发 电机的取电电路 (如整流稳压等电路)做整合，而形成可变速的电动马达或可变速 的发电机， 此整合后的可变速电动马达同时具有产生旋转动力及变速的功能， 但体积及重量则仅约为原电动马达的体积及重量， 达到较高的驱动功率密度。 同时， 磁性变速组成采用电磁式的变速， 故能降低振动及噪音。 再者， 在电动 车产业的应用中， 此可变速电动马达即能配合不同的行车扭力需求及行驶速度 要求， 且能保持高效率运转。
虽然本发明以前述的较佳实施例公开如上， 然其并非用以限定本发明， 任 何本领域的技术人员， 在不脱离本发明的精神和范围内， 当可作些许的更动与 修改， 因此本发明的专利保护范围须视本说明书所附的专利保护范围所界定者 为准。 工业应用性
本发明的磁性变速组成包含了电动马达或发电机的定子与转子的设计，并 具有变速的结构设计， 能易于与电动马达的马达驱动器或发电机的取电电路 (如 整流稳压等电路 M故整合， 而形成可变速的电动马达或可变速的发电机， 此整合 后的可变速电动马达同时具有产生旋转动力及变速的功能， 但体积及重量则仅 约为原电动马达的体积及重量， 达到较高的驱动功率密度。 同时， 磁性变速组 成采用电磁式的变速， 故能降低振动及噪音。 再者， 在电动车产业的应用中， 此可变速电动马达即能配合不同的行车扭力需求及行驶速度要求， 且能保持高 效率运转。

Claims

权利要求书
1. 一种磁性变速组成， 其特征在于， 包含：
一转子， 具有多个磁极， 该转子的该些磁极具有 R个极对数；
一定子， 与该转子同轴套设， 该定子具有多个磁极， 该定子的该些磁极 具有 ST1个极对数； 以及
一导磁组件， 位于该转子与该定子之间并具有多个导磁体， 当该导磁组 件被致动时，该导磁组件选择性地使 PN1个或 PN2个该些导磁体对应于该转子 与该定子之间， 其中， PN1-3≤ R+ST1 ≤ ΡΝ1+3、 或 R- 3≤ PN1+ST1 ≤ R+3、 或 ST1 - 3 ≤ PN1+R ≤ STl+3。
2. 如权利要求 1所述的磁性变速组成， 其特征在于， PN2- 3≤ R+ST1
≤ PN2+3> 或 R_3 ≤ PN2+ST1 ≤ R+3、 或 ST1- 3 ≤ PN2+R ≤ STl+3。
3. 如权利要求 1 所述的磁性变速组成， 其特征在于， 该导磁组件包 含一第一环及一第二环， 该第一环与该第二环轴向连接， 该第一环具有 PN1 个导磁子块， 该第二环具有 PN2个导磁子块， 当该导磁组件被轴向致动时， 该 导磁组件选择性地使该第一环或该第二环移动至该转子与该定子之间。
4. 如权利要求 1 所述的磁性变速组成， 其特征在于， 该导磁组件包 含一第一环及一第二环，该第一环位于该第二环的径向外侧且该第一环及该第 二环配置于该定子与该转子之间， 当该导磁组件被致动时，该第一环与该第二 环相对运动于一第一位置与一第二位置之间，当该第一环与该第二环位于该第 一位置时，该导磁组件具有 PN1个该导磁体， 当该第一环与该第二环位于该第 二位置时， 该导磁组件具有 PN2个该导磁体。
5. 如权利要求 4所述的磁性变速组成， 其特征在于， 该第一环具有 多个第一导磁子块， 该第二环具有多个第二导磁子块，当该第一环与该第二环 位于该第一位置时， 两相邻的该些第一导磁子块与该些第二导磁子块形成该 PN1个导磁体之一， 当该第一环与该第二环位于该第二位置时， 该些第一导磁 子块与该些第二导磁子块各自形成该 PN2个导磁体之一。
6. 如权利要求 1所述的磁性变速组成， 其特征在于， 该定子包含多 个感应线圈， 该些感应线圈被通电时形成该些磁极。
7. 如权利要求 6所述的磁性变速组成， 其特征在于， 该定子还包含 一极数调变电路，该极数调变电路选择性地切换该些感应线圈于该 ST1个极对 数及一 ST2个极对数之间。
8. 如权利要求 7 所述的磁性变速组成， 其特征在于， 该定子还包含 环形配置的多个凸块， 该些感应线圈分别绕于该些凸块， 当该些感应线圈 ¾切 换至该 ST1个极对数时，相邻的该些感应线圈的极性相反， 当该些感应线圈被 切换至该 ST2个极对数时， 该些感应线圈被群组为多个线圈组， 且相邻的该些 线圈组的极性相反。
9. 如权利要求 8所述的磁性变速组成， 其特征在于， PN2- 3≤ R+ST2 ≤ PN2+3。
10. 如权利要求 8所述的磁性变速组成， 其特征在于， 每一该些线圈 组包含三个依序相邻的该些感应线圈。
11. 如权利要求 8所述的磁性变速组成， 其特征在于， 该导磁组件包 含一第一环及一第二环， 该第一环与该第二环轴向连接， 该第一环具有 PN1 个导磁子块， 该第二环具有 PN2个导磁子块， 当该导磁组件被轴向致动时， 该 导磁组件选择性地使该第一环或该第二环被移至该转子与该定子之间。
12. 如权利要求 8所述的磁性变速组成， 其特征在于， 该导磁组件包 含一第一环及一第二环，该第一环与该第二环径向接触并夹置于该定子与该转 子之间， 当该导磁组件被致动时，该第一环与该第二环相对位移于一第一位置 与一第二位置之间， 当该第一环与该第二环位于该第一位置时，该导磁组件具 有 PN1个该些导磁体， 当该第一环与该第二环位于该第二位置时，该导磁组件 具有 PN2个该些导磁体。
13. 如权利要求 1 所述的磁性变速组成， 其特征在于， 该导磁组件包 含一第一环及一第二环， 该第一环具有多个环状列置的第一导磁子块， 该第二 环具有多个环状列置的第二导磁子块，该些第一导磁子块与该些第二导磁子块 在径向交错列置并被夹置于该定子与该转子之间， 当该导磁组件被致动时， 该 第一环与该第二环相对运动于一第一位置与一第二位置之间，当该第一环与该 第二环位于该第一位置时，两相邻的该些第一导磁子块与该些第二导磁子块形 成该 PN1个导磁体之一， 当该第一环与该第二环位于该第二位置时，该些第一 导磁子块与该些第二导磁子块分别形成该 PN2个导磁体之一。
14. 如权利要求 1 所述的磁性变速组成， 其特征在于， 该导磁组件包 含一第一环、 一第二环、及一第三环， 该第一环具有多个环状列置的第一导磁 子块，该第二环具有多个环状列置的第二导磁子块，该第三环具有多个环状列 置的第三导磁子块， 该些第一导磁子块、该些第二导磁子块、及该些第三导磁 子块在径向依序列置并被夹置于该定子与该转子之间， 当该导磁组件被致动 时， 该第一环、 该第二环及该第三环相对运动于一第一位置、一第二位置及一 第三位置之间， 当该第一环、该第二环及该第三环位于该第一位置时， 三相邻 的该些第一导磁子块、该些第二导磁子块及该些第三导磁子块形成该 PN1个导 磁体之一， 当该第一环与该第二环位于该第二位置时， 该些第一导磁子块、 该 些第二导磁子块及该些第三导磁子块各自形成该 PN2个导磁体之一，当该第一 环与该第二环位于该第三位置时，两相邻的该些第二导磁子块及该些第三导磁 子块形成 PN3个导磁体之一，且该些第一导磁子块各自形成该 PN3个导磁体之 一， 其中 PN3- 3≤ R+ST1 ≤ PN3+3、 或 R- 3≤ PN3+ST1 ≤ R+3、 或 ST1- 3≤ PN3+R ≤ STl+3。
15. 如权利要求 1 所述的磁性变速组成， 其特征在于， 该导磁组件的 材料为软磁材料（Soft Magnetic Composite, SMC)。
16. 一种磁性变速组成， 其特征在于， 包含：
一转子， 具有多个磁极， 该转子的该些磁极具有 R个极对数；
一定子， 与该转子同轴套设， 该定子具有多个磁极， 该定子的该些磁极 具有 ST1个极对数及 ST1 ' 个髙阶导磁的极对数； 以及
一导磁组件， 位于该转子与该定子之间并具有多个导磁体， 当该导磁组 件被致动时，该导磁组件选择性地使 PN1个或 PN2个该些导磁体对应于该转子 与该定子之间， 其中， PN1- 3 ≤ R+ST1 ' ≤ ΡΝ1+3、 或 R- 3 ≤ PN1+ST1 ' ≤ R+3、 或 ST1， -3 ≤ PN1+R ≤ ST1， +3。
17. 如权利要求 16 所述的磁性变速组成， 其特征在于， PN2- 3 ≤ R+ST1， ≤ PN2+3、 或 R— 3 ≤ PN2+ST1 ' ≤ R+3、 或 ST1， —3 ≤ PN2+R ≤ ST1 ' +3。
18. 如权利要求 16所述的磁性变速组成， 其特征在于， 该导磁组件包 含一第一环及一第二环， 该第一环与该第二环轴向连接， 该第一环具有 PN1 个导磁子块， 该第二环具有 PN2个导磁子块， 当该导磁组件被轴向致动时， 该 导磁组件选择性地使该第一环或该第二环移动至该转子与该定子之间。
19. 如权利要求 16所述的磁性变速组成， 其特征在于， 该导磁组件包 含一第一环及一第二环，该第一环位于该第二环的径向外侧且该第一环及该第 二环配置于该定子与该转子之间， 当该导磁组件被致动时，该第一环与该第二 环相对运动于一第一位置与一第二位置之间，当该第一环与该第二环位于该第 一位置时，该导磁组件具有 PN1个该些导磁体， 当该第一环与该第二环位于该 第二位置时， 该导磁组件具有 PN2个该些导磁体。
20. 如权利要求 19所述的磁性变速组成， 其特征在于， 该第一环具有 多个第一导磁子块，该第二环具有多个第二导磁子块， 当该第一环与该第二环 位于该第一位置时， 两相邻的该些第一导磁子块与该些第二导磁子块形成该 PN1个导磁体之一， 当该第一环与该第二环位于该第二位置时， 该些第一导磁 子块与该些第二导磁子块各自形成该 PN2个导磁体之一。
21. 一种分段相位驱动马达， 其特征在于， 包含：
一转子， 具有多个磁极， 该转子的该些磁极具有 R个极对数；
一定子， 与该转子同轴套设， 该定子具有多个磁极， 该定子的该些磁极 具有 ST1个极对数； 以及
一导磁组件， 配置于该转子与该定子之间并具有 PN1个导磁子块， 该些 导磁子块对应于该转子与该定子之间并形成一定子侧极对数 R2， 其中 R2= | R- PN1 |或 R2=R+PN1， 而 R2 与 ST1 则符合一分段相位绕线表（Winding Chart)。
22. 一种磁性变速组成， 其特征在于， 包含：
一转子， 具有多个磁极， 该转子的该些磁极具有 R个极对数；
一定子， 与该转子同轴套设， 该定子具有多个磁极， 该定子的该些磁极 具有 ST1个极对数； 以及
一导磁组件， 配置于该转子与该定子之间并具有 PN1个导磁子块， PN1个 该些导磁子块对应于该转子与该定子之间， 其中， PN1- 3≤ R+ST1 ≤ ΡΝ1+3、 或 R- 3 ≤ PN1+ST1 ≤ R+3、 或 ST1- 3 ≤ PN1+R ≤ STl+3。
PCT/CN2011/000454 2010-04-20 2011-03-21 磁性变速组成及其分段相位驱动马达 WO2011131021A1 (zh)

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