WO2010089875A1 - インバータ回路 - Google Patents
インバータ回路 Download PDFInfo
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- WO2010089875A1 WO2010089875A1 PCT/JP2009/052036 JP2009052036W WO2010089875A1 WO 2010089875 A1 WO2010089875 A1 WO 2010089875A1 JP 2009052036 W JP2009052036 W JP 2009052036W WO 2010089875 A1 WO2010089875 A1 WO 2010089875A1
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- switch element
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- snubber
- capacitor
- voltage
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/32—Means for protecting converters other than automatic disconnection
- H02M1/34—Snubber circuits
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/538—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a push-pull configuration
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/32—Means for protecting converters other than automatic disconnection
- H02M1/34—Snubber circuits
- H02M1/342—Active non-dissipative snubbers
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Definitions
- This invention relates to an inverter circuit having a snubber circuit and a regenerative circuit on the primary side of a transformer.
- a snubber circuit is provided in parallel with the switch element to prevent a surge voltage from being applied to the switch element due to the leakage inductance between the primary side and the secondary side of the transformer. Connected. It has also been proposed to provide a regenerative circuit that regenerates the charge charged in the snubber capacitor of the snubber circuit to the power supply. By providing this regenerative circuit, the charge is not consumed by the snubber resistor, and the charging energy of the snubber capacitor is regenerated to the power source, so that the efficiency of the inverter circuit can be increased.
- the inverter shown in Patent Document 1 includes a snubber circuit and a regenerative circuit as described above.
- a first switch element and a second switch element are connected to the primary side.
- a snubber circuit is connected in parallel to the first switch element.
- a regenerative circuit is connected between the snubber circuit and the power source.
- the snubber circuit is composed of a series circuit of a snubber diode and a snubber capacitor.
- the regenerative circuit includes a regenerative switch element, a series circuit of a reactor and a regenerative diode. Similarly, the snubber circuit and the regenerative circuit are connected to the second switch element.
- the control unit alternately turns on and off the first switch element and the second switch element, and turns on the regenerative switch element for a predetermined time.
- the regenerative switch element is on, the charge charged in the snubber capacitor is completely discharged and regenerated to the power source.
- the loss due to charging / discharging of the snubber capacitor may be larger than the loss improvement due to the ZVS operation.
- the inverter circuit as shown in Patent Document 1 has a problem that the efficiency is deteriorated at a light load.
- an object of the present invention is to provide an inverter circuit that is highly efficient regardless of the size of the load.
- the inverter circuit of this invention is A first switch element; A second switch element; An output transformer in which current is supplied to the primary side via the first switch element and the second switch element, and current is output from the secondary side to the load; A first freewheeling diode connected in antiparallel to the first switch element; A second freewheeling diode connected in antiparallel to the second switch element; A first snubber circuit connected in parallel to the first switch element and including a series circuit of a first snubber diode and a first snubber capacitor; A second snubber circuit connected in parallel to the second switch element and including a series circuit of a second snubber diode and a second snubber capacitor; A voltage source for applying a voltage to the first switch element and the second switch element; A first regeneration circuit connected between the first snubber circuit and the voltage source; A second regeneration circuit connected between the second snubber circuit and the voltage source.
- the first switch element and the second switch element are composed of, for example, an IGBT (insulated gate bipolar transistor) or a MOS-FET.
- IGBT insulated gate bipolar transistor
- MOS-FET MOS-FET
- the action of the first snubber circuit and the second snubber circuit prevents the surge voltage from being applied to the first switch element and the second switch element, and the snubber is provided by the first regenerative circuit and the second regenerative circuit. The electric charge charged in the circuit is regenerated to the power source.
- the first regeneration circuit includes a series circuit of a third switch element, a first reactor, and a first regeneration diode
- the second regeneration circuit includes a series circuit of a fourth switching element, a second reactor, and a second regeneration diode.
- the inverter circuit includes a control unit that alternately turns on and off the first switch element and the second switch element and alternately turns on and off the third switch element and the fourth switch element. As described below, the control unit controls the period Tb during which the third switch element and the fourth switch element are alternately turned on and off according to the magnitude of the output power. It is a point to do.
- the controller turns on the third switch element for a period Tb from when the first switch element is turned on.
- the third switch element is turned on, the first regeneration circuit regenerates the electric charge charged in the first snubber capacitor to the power supply via the first regeneration diode.
- the control unit controls the length of the period Tb according to the magnitude of the output power detected by the output detection unit.
- the output detection unit is configured, for example, by providing a sensor that detects an output current in a DC-DC converter circuit that outputs a constant voltage.
- control unit sets the period Tb when the output current is greater than or equal to a predetermined current to a time during which the charge charge of the first snubber capacitor is substantially completely discharged, and when the output current is less than the predetermined current, Is set to a time during which the charge of the first snubber capacitor is partially discharged.
- the substantially completely discharged time includes a time when the charged electric charge of the first snubber capacitor is completely discharged and a time when it is almost completely discharged.
- control unit sets the period Tb when the output current is greater than or equal to a predetermined current to a time during which the charge of the first snubber capacitor is substantially completely discharged, and the output current is less than the predetermined current.
- the period Tb is set to zero.
- control unit sets the period Tb to be shorter as the output current becomes smaller.
- the ON period Tb of the fourth switch element is controlled by the control unit in the same manner as the third regeneration circuit.
- FIG. 1 is a circuit diagram of a DC-DC converter circuit according to a first embodiment of the present invention. It is a timing chart of the mode of soft switching. It is a timing chart of the mode of hard switching. It is a figure which shows the efficiency according to a mode, and a switch element both-ends voltage. It is a circuit diagram of the DC-DC converter circuit which is the 2nd Embodiment of this invention. It is a basic lineblock diagram of a current balanced push pull type inverter circuit. It is a timing chart of the mode of soft switching. It is a timing chart of the mode of hard switching.
- FIG. 1 is a circuit diagram of a DC-DC converter circuit according to a first embodiment of the present invention.
- the DC-DC converter circuit includes an inverter circuit, a rectifier circuit connected to the secondary side of an output transformer (hereinafter referred to as a transformer) T, and a control unit CNT.
- a transformer an output transformer
- the inverter circuit includes a first switch element S1 and a second switch element S2 connected in series, and the first terminal of the primary winding of the transformer T is connected to the connection point thereof.
- the power source Vin is connected in parallel to the series circuit of the first voltage source capacitor C1 and the second voltage source capacitor C2, and the second terminal of the primary winding of the transformer T is connected to the connection points of the capacitors C1 and C2. It is connected.
- Each of the capacitors C1 and C2 is charged with (1/2) Vin. From the above connection form, this inverter circuit operates as a half-bridge type inverter circuit.
- a free wheel diode df1 is connected in antiparallel to the first switch element S1.
- a first snubber circuit SB1 is connected in parallel to the switch element S1.
- the first snubber circuit SB1 is composed of a series circuit of a first snubber diode ds1 and a first snubber capacitor Cs1.
- a first regenerative circuit RG1 is connected between the first snubber circuit SB1 and a connection point between the capacitor C1 and the capacitor C2.
- the first regenerative circuit RG1 includes a third switch element S3, a reactor Lf, and a first regenerative diode df3.
- Reactor Lf is connected between the connection point of capacitors C1 and C2 and third switch element S3.
- the first regenerative diode df3 is connected between the third switch element S3 and the first snubber capacitor Cs1.
- a freewheel diode df2 is connected in antiparallel to the second switch element S2.
- a second snubber circuit SB2 is connected in parallel to the switch element S2.
- the second snubber circuit SB2 is composed of a series circuit of a second snubber diode ds2 and a second snubber capacitor Cs2.
- a second regeneration circuit RG2 is connected between the second snubber circuit SB2 and the connection point between the capacitor C1 and the capacitor C2.
- the second regenerative circuit RG2 includes a fourth switch element S4, a reactor Lf, and a second regenerative diode df4.
- Reactor Lf is connected between a connection point between capacitors C1 and C2 and fourth switch element S4.
- the second regenerative diode df4 is connected between the fourth switch element S4 and the second snubber capacitor Cs2.
- reactor Lf is also used as the first regeneration circuit RG1 and the second regeneration circuit RG2.
- a diode df5 connected between the third switch element S3 and the power supply and a diode df6 connected between the fourth switch element S4 and the power supply are diodes for preventing backflow.
- the secondary side of the transformer T, a rectifying diode d1 and d2 are connected, further, the smoothing reactor L 0 and a smoothing capacitor C 0 is connected.
- a load R 0 is connected to the smooth output terminal.
- a current detection sensor (output detection unit) DC for detecting an output current and a voltage detection unit DV for detecting an output voltage composed of resistors R1 and R2 are connected to the output circuit on the secondary side.
- the control unit CNT outputs the control signals G1 and G2, and alternately controls the first switch element S1 and the second switch element S2 on and off with a pause period.
- the control unit CNT controls the pulse widths of the control signals G1 and G2 so that the output voltage detected by the voltage detection unit DV becomes a constant voltage. Further, the control unit CNT controls the ON time Tb of the third switch element S3 and the fourth switch element S4 according to the magnitude of the output current detected by the current detection sensor DC, that is, the magnitude of the output power.
- the time Tb is ⁇ (Lf), which is one half of the resonance period of the reactor Lf and the snubber capacitor Cs (Cs1 or Cs2) when the output power is 350 W or more (a constant power or more).
- ⁇ (Lf) which is one half of the resonance period of the reactor Lf and the snubber capacitor Cs (Cs1 or Cs2) when the output power is 350 W or more (a constant power or more).
- the output power is set to 150 ns, which is about 0.005 of the switching period T.
- FIG. 2 and 3 are time charts of the DC-DC converter circuit.
- FIG. 2 shows a time chart when the output power is 350 W or more
- FIG. 3 shows a time chart when the magnitude of the output power is less than 350 W (light load). That is, FIG. 2 shows a time chart when the output current detected by the control unit CNT with the current detection sensor DC is equal to or higher than a certain value (350 W / rated voltage), and FIG. 3 shows the control unit CNT with the current detection sensor DC.
- the time chart when the detected output current is less than a constant (350 W / rated voltage) is shown.
- control unit CNT determines that the current detected by the current detection sensor DC is equal to or greater than a certain level, the operation is performed according to the time chart of FIG.
- the first switch element S1 and the second switch element S2 are both off.
- the voltage S1Vds across the switch element S1 is the same (1/2) Vin as the voltages VC1 and VC2 of the capacitors C1 and C2 (Vin is a power supply voltage).
- the snubber diode ds1 prevents the capacitor Cs1 from discharging, so that the voltage of the capacitor Cs1 is maintained.
- the switch element S1 is turned on. Then, electric power is supplied to the load R0 via the transformer T, and the current S1Id starts to flow through the switch element S1.
- the current S1Id increases linearly with a constant slope due to the current reducing action of the leakage inductance Le between the primary side and the secondary side of the transformer T. Therefore, switching-on is a ZCS (Zero-Current-Switching) operation.
- the voltage S2Vds across the switch element S2 is Vin.
- the control unit CNT turns on the control signal G1 and turns on the control signal G3 and turns on the third switch element S3.
- the switch element S3 When the switch element S3 is turned on, the charge of the first snubber capacitor Cs1 is regenerated in the capacitor C1 by the first regeneration circuit RG1. That is, in the first regenerative circuit RG1, the regenerative reactor Lf and the snubber capacitor Cs1 resonate, and the charge of the capacitor Cs1 is passed through the regenerative reactor Lf, the switch element S3, and the regenerative diode df3. It is regenerated.
- the control unit CNT turns on the switch element S3 for a time Tb from the time t0.
- the time Tb is set to a time sufficient for the charge of the snubber capacitor Cs1 to be completely discharged.
- the current ICs1 starts to flow as a regenerative current in the first regenerative circuit RG1 based on the charge charged in the snubber capacitor Cs1.
- the reactor Lf and the snubber capacitor Cs1 resonate, and the current ICs1 flowing from the snubber capacitor Cs1 becomes a current corresponding to a positive half cycle of the sine wave current due to the action of the regenerative diode df3.
- the time when the resonance current becomes zero (1/2 time of the resonance period (2 ⁇ (Lf ⁇ Cf)) is when the charge of the snubber capacitor Cs1 is completely discharged, and in FIG. . Therefore, the control unit CNT continues to turn on the switch element S3 until a time t2 slightly exceeding the time t1. As a result, the entire charge of the snubber capacitor Cs1 is regenerated in the capacitor C1.
- the control unit CNT turns off the control signal G1, thereby turning off the switch element S1.
- the snubber capacitor Cs1 is gradually charged with the stored energy of the leakage inductance Le.
- the voltage S1Vds across the switching element S1 gradually rises from time t3, so that the switching-off operation is a ZVS (Zero Voltage Switching) operation (hereinafter, this operation is referred to as soft switching).
- the displacement of the charging potential VCs1 of the snubber capacitor Cs1 is caused by the resonance system of the leakage inductance Le and the snubber capacitor Cs1 in the second half of the charging period, and is finally clamped to Vin.
- control signals G2 and G4 are turned on by the control unit CNT, and the switch element S2, the second snubber circuit SB2, and the second regeneration circuit RG2 are the same as described above. Operation is performed.
- the voltage VCs1 is maintained by the snubber diode ds1.
- the switch element S1 is turned on. Then, electric power is supplied to the load R0 via the transformer T, and a current S1Id starts to flow through the switch element S1.
- the current S1Id increases linearly with a constant slope by the current reducing action of the leakage inductance Le between the primary side and the secondary side of the transformer T. Therefore, switching-on becomes a ZCS (Zero Current Switching) operation.
- ZCS Zero Current Switching
- the control unit CNT turns on the control signal G1 and turns on the control signal G3 and turns on the third switch element S3.
- the switch element S3 When the switch element S3 is turned on, the charge of the first snubber capacitor Cs1 starts to be regenerated in the capacitor C1 by the first regenerative circuit RG1.
- the voltage S1Vds is caused by a residual inductance other than the leakage inductance Le (for example, a residual inductance existing between the capacitor C1 and the switch element S1 or between the capacitor C2 and the diode df2) or a conduction delay of the diode df2. Tries to rise above the voltage Vin.
- This energy charges the capacitor Cs1 connected in parallel to the switch element s1 via the diode ds1.
- the voltage Vds converges to a voltage of 0.5 Vin through ringing caused by resonance between the leakage inductance Le and the residual inductance of the circuit, the output capacitance of the switch element S1, and the floating capacitance.
- the voltage VCs1 of the capacitor Cs1 is maintained at Vin + 0.5 ⁇ by preventing discharge of the diode ds1. This completes the operation of the 1 ⁇ 2 cycle, and subsequently, the control signals G2 and G4 are turned on by the control unit CNT, and the switch element S2, the second snubber circuit SB2, and the second regeneration circuit RG2 are the same as described above. Operation is performed.
- FIG. 2 is referred to herein as a soft switching mode because the voltage S1Vds performs a ZVS operation. Since the voltage S1Vds does not perform the ZVS operation, FIG. 3 is referred to as a hard switching mode (second mode because Tb> 0 as will be described later).
- the time Tb is set to about 0.005 of the switching period T and 150 ns, but there is an option to set the time Tb to zero.
- FIG. 4 shows the efficiency of the circuit when the time Tb is set to three modes.
- the first mode is the soft switching mode shown in FIG.
- the first mode is the most efficient.
- the charge of the snubber capacitor Cs1 is completely discharged at time Tb and charged until the voltage Vin is reached at time t3-t4.
- the control unit CNT selects the soft switching mode and performs the operation shown in the time chart of FIG.
- the third mode is most efficient, and then the second mode is efficient.
- the second mode as shown in the time chart of FIG. 3, the charged charge of the snubber capacitor Cs1 is discharged (partially) by time ⁇ at time Tb and charged by ⁇ until voltage Vin is reached at time t3-t4.
- the control unit CNT sets the time Tb so as to enter the second mode as shown in FIG. It is also possible to select the third mode instead of the second mode.
- the control unit CNT performs switching control in the first mode (soft switching mode) when the output power is higher than 350 W, and the output power is higher than 350 W.
- the third mode of hard switching when switching control is performed in the third mode when the power is less than 350 W, the charge across the snubber capacitor is not discharged, and the voltage across the switch element gradually increases. In such a case, it is preferable to switch from the third mode of hard switching to the second mode of hard switching periodically or irregularly.
- the load point for switching from the soft switching mode (first mode) to the hard switching mode (second mode or third mode) is 30 to 50% when the rated load is 100%. It is preferable to set within the range.
- the efficiency at the time of light load of the DC-DC inverter circuit including the snubber circuit and the regenerative circuit can be improved.
- FIG. 5 is a circuit diagram of a DC-DC converter circuit according to the second embodiment of the present invention.
- This DC-DC converter circuit includes an inverter circuit, a rectifier circuit connected to the secondary side of the transformer T, and a control unit CNT.
- the inverter circuit is configured by a current balanced push-pull type (Current Balanced P.P) inverter circuit, which will be described in detail later.
- Current Balanced P.P Current Balanced P.P
- Fig. 6 shows the basic circuit of a current balanced push-pull inverter circuit.
- the inverter circuit includes a first switch element S1, a second switch element S2, a first switch connected in series between the positive electrode side of the first switch element S1 and the positive electrode side of the second switch element S2.
- Primary winding P1 (P1a, P1b) and a second primary winding P2 (P2a, P2b) connected in series between the negative side of the first switch element S1 and the negative side of the second switch element S2.
- the power source V connected between the center tap of the first primary winding P1 and the center tap of the second primary winding P2, the first terminal of the first primary winding P1, and the second primary winding.
- a capacitor C1 which is a first voltage source, connected between the first terminals of the line P2, and a second terminal of the first primary winding P1 and a second terminal of the second primary winding P2 And a capacitor C2, which is a second voltage source to be connected.
- the secondary winding S of the transformer T is connected to a diode bridge rectifier circuit, a reactor L 0 that smoothes the rectified output, and a load R 0 .
- the first switch element S1 and the second switch element S2 are alternately turned on and off by a control unit (not shown).
- the current flowing through the primary windings P1a and P2b is obtained by subtracting the charging current
- This current imbalance is not a problem. This is because the average winding current balance is maintained by alternately turning on and off the switch elements S1 and S2 (by commutation). Therefore, there is no problem that the core of the transformer is particularly demagnetized.
- the alternating voltage applied to the first primary winding P1 and the second primary winding P2 is the power supply voltage V, which is the same as the full bridge type.
- the center tap provided in the first primary winding P1 and the second primary winding P2 is for supplying energy from the power source V, and the current shown by the thick line in FIG. All windings of the first primary winding P1 and the second primary winding P2 are used. Therefore, unlike the center tap push-pull type, no idle winding is generated every half cycle. That is, it is not necessary to consider the leakage inductance between P1a and P1b and the leakage inductance between P2a and P3b, and therefore no surge voltage is generated during commutation.
- a charging current 0.5Ii always flows from the power source V to the capacitors C1 and C2 via the first primary winding P1 and the second primary winding P2.
- the leakage inductance between the windings P1 and P2 functions as a filter that removes the ripple component, so that the current Ii supplied from the power supply V becomes a continuous direct current. Therefore, as the power source V, a battery that dislikes the ripple component (deteriorates the life characteristics due to the ripple), for example, a fuel cell can be used.
- the coupling between the first primary winding P1 and the secondary winding S and the coupling between the second primary winding P2 and the secondary winding S are symmetrical because it is necessary to balance the shunt current. There must be.
- the current balanced push-pull inverter circuit does not require a large current to flow through the switch element unlike the half-bridge inverter circuit, and also has a leakage inductance between P1a and P1b and a leakage inductance between P2a and P3b.
- the DC-DC converter circuit shown in FIG. 5 uses a current balanced push-pull inverter circuit having the above basic configuration. Furthermore, a snubber circuit and a regenerative circuit similar to the half-bridge inverter circuit shown in FIG. 1 are added to the current balanced push-pull inverter circuit. That is, the snubber circuit is composed of a first snubber circuit connected in parallel to the first switch element S1 and a second snubber circuit connected in parallel to the second switch element.
- the regenerative circuit includes a first regenerative circuit connected between the first snubber circuit and the first capacitor C1, and a second regenerator circuit connected between the second snubber circuit and the second capacitor C2. 2 regenerative circuits.
- the first snubber circuit is composed of a series circuit of a first snubber diode ds1 and a first snubber capacitor Cs1.
- the first regenerative circuit includes a third switch element S3, a first reactor Lf1, and a first regenerative diode df3.
- the second snubber circuit is composed of a series circuit of a second snubber diode ds2 and a second snubber capacitor Cs2.
- the second regeneration circuit includes a fourth switch element S4, a second reactor Lf2, and a second regeneration diode df4.
- the leakage inductance Le is displayed on the secondary side of the transformer T. However, the leakage inductance Le is equivalently displayed on the primary side as shown in FIG.
- the control unit CNT controls the time Tb in the same manner as the half-bridge inverter circuit shown in FIG. As shown in FIGS. 7 and 8, the operation of the circuit is the same as in FIGS. 7 and 8, the charging voltage VCs1 of the snubber capacitor Cs1 is clamped to 2Vin, whereas in FIG. 2 and FIG. 3, the charging voltage VCs1 is clamped to Vin.
- the current detection sensor (output detection unit) DC that detects the output current on the secondary side of the transformer is provided under the control of constant voltage output. Instead of this, it is possible to provide a sensor for detecting the primary current. When performing constant current output, it is also possible to provide a resistance voltage dividing circuit for detecting the output voltage on the secondary side of the transformer and detect the output power based on the output voltage.
- a circuit for detecting the voltages of the first and second snubber capacitors Cs1 and Cs2 is provided, the voltage is equal to or higher than a predetermined value, and the load current and the load voltage are less than a certain value.
- the switch elements S3 and S4 may be turned on for a short period. It is also possible to dynamically control the on-time of the switch elements so that the voltages of the snubber capacitors Cs1, Cs2 do not exceed a predetermined value.
- the present invention can be applied to a full-bridge inverter circuit and a push-pull inverter circuit in addition to the half-bridge inverter circuit and the current balanced push-pull inverter circuit.
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Abstract
Description
第1のスイッチ素子と、
第2のスイッチ素子と、
前記第1のスイッチ素子及び前記第2のスイッチ素子を介して一次側に電流が供給され、二次側から負荷に対して電流が出力される出力トランスと、
前記第1のスイッチ素子に逆並列に接続される第1のフリーホイールダイオードと、
前記第2のスイッチ素子に逆並列に接続される第2のフリーホイールダイオードと、
前記第1のスイッチ素子に並列に接続され、第1のスナバダイオードと第1のスナバコンデンサの直列回路を含む第1のスナバ回路と、
前記第2のスイッチ素子に並列に接続され、第2のスナバダイオードと第2のスナバコンデンサの直列回路を含む第2のスナバ回路と、
前記第1のスイッチ素子及び前記第2のスイッチ素子に電圧を印加する電圧源と、
前記第1のスナバ回路と前記電圧源間に接続される第1の回生回路と、
前記第2のスナバ回路と前記電圧源間に接続される第2の回生回路と、を備えている。
前記第2の回生回路は、第4のスイッチ素子と、第2のリアクトルと、第2の回生用ダイオードとの直列回路を含んでいる。
S2-第2のスイッチ素子
S3-第3のスイッチ素子
S4-第4のスイッチ素子
SB1-第1のスナバ回路
SB2-第2のスナバ回路
RG1-第1の回生回路
RG2-第2の回生回路
CNT-制御部
VCs1=Vin+0.5α-α=Vin-0.5αとなる。当然、スイッチS1がオンしてもスナバダイオードds1の放電阻止作用により、コンデンサC1の電荷がスイッチ素子S1で短絡されることはない。
S1Vds=Leの誘起電圧+Vin/2となる。この誘起電圧がVin/2になると、
スイッチ素子S2に並列接続されているフリーホイールダイオードdf2が導通し、電流S1IdがコンデンサC2に流れてリーケージインダクタンスLeのエネルギーが電源に回生される。このため、理想的には上記誘起電圧がVin/2にクランプされて電圧S1Vdsは電圧Vin以上にはならない。
VCs1=Vin-0.5α+α=Vin+0.5αとなる。
ID1=I0・aである。
IP1a,Ip2b=0.5(ID1-Ii)
IP1b,Ip2a=0.5(ID1+Ii)
である。この電流アンバランスは問題ない。なぜなら、スイッチ素子S1、S2が交互にオンオフすることで(転流することで)平均巻線電流の平衡が保たれるからである。したがって、特にトランスのコアが偏磁するという問題を生じることはない。
Claims (6)
- 第1のスイッチ素子と、
第2のスイッチ素子と、
前記第1のスイッチ素子及び前記第2のスイッチ素子を介して一次側に電流が供給され、二次側から負荷に対して電流が出力される出力トランスと、
前記第1のスイッチ素子に逆並列に接続される第1のフリーホイールダイオードと、
前記第2のスイッチ素子に逆並列に接続される第2のフリーホイールダイオードと、
前記第1のスイッチ素子に並列に接続され、第1のスナバダイオードと第1のスナバコンデンサの直列回路を含む第1のスナバ回路と、
前記第2のスイッチ素子に並列に接続され、第2のスナバダイオードと第2のスナバコンデンサの直列回路を含む第2のスナバ回路と、
前記第1のスイッチ素子及び前記第2のスイッチ素子に電圧を印加する電圧源と、
前記第1のスナバ回路と前記電圧源間に接続される第1の回生回路と、
前記第2のスナバ回路と前記電圧源間に接続される第2の回生回路と、を備え、
前記第1の回生回路は、第3のスイッチ素子と、第1のリアクトルと、第1の回生用ダイオードとの直列回路を含み、
前記第2の回生回路は、第4のスイッチ素子と、第2のリアクトルと、第2の回生用ダイオードとの直列回路を含み、さらに、
前記第1のスイッチ素子と前記第2のスイッチ素子を交互にオンオフし、前記第3のスイッチ素子と前記第4のスイッチ素子を交互にオンオフする制御部と、
出力電力の大きさを検出する出力検出部とを備え、
前記制御部は、前記出力検出部で検出した出力電力の大きさに応じて前記第3のスイッチ素子と前記第4のスイッチ素子のオン時間を制御することを特徴とするインバータ回路。 - 前記第1のリアクトルと前記第2のリアクトルは一つのリアクトルで兼用されており、
前記電圧源は、第1の電圧源コンデンサと第2の電圧源コンデンサの直列回路と該直列回路に並列に接続された電源とで構成され、
前記第1の回生回路は、前記第1のスナバ回路と前記第1の電圧源コンデンサ間に接続され、
前記第2の回生回路は、前記第2のスナバ回路と前記第2の電圧源コンデンサ間に接続され、
前記第1の回生回路の前記第1のリアクトルは前記第3のスイッチ素子と前記第1の電圧源コンデンサ間に接続され、
前記第2の回生回路の前記第2のリアクトルは前記第4のスイッチ素子と前記第2の電圧源コンデンサ間に接続されている、請求項1記載のインバータ回路。 - 前記出力トランスは、
前記第1のスイッチ素子の正極側と前記第2のスイッチ素子の正極側間に接続される第1の一次巻線と、前記第1のスイッチ素子の負極側と前記第2のスイッチ素子の負極側間に接続される第2の一次巻線とを備え、
前記電圧源は、
前記第1の一次巻線が前記第2のスイッチ素子に接続される第1の接続点と前記第1のスイッチ素子間に接続され、前記第1の一次巻線を介して前記第1のスイッチ素子に電圧を印加する第1の電圧源と、
前記第1の一次巻線が前記第1のスイッチ素子に接続される第2の接続点と前記第2のスイッチ素子間に接続され、前記第1の一次巻線を介して前記第2のスイッチ素子に電圧を印加する第2の電圧源と、
前記第1の一次巻線のセンタータップと、前記第2の一次巻線のセンタータップ間に接続され、前記第1、第2の電圧源に対して前記第1の一次巻線及び前記第2の一次巻線を介してエネルギー供給する電源と、を備える請求項1記載のインバータ回路。 - 前記制御部は、前記出力検出部で検出した出力電力が一定電力以上のときは前記第3のスイッチ素子と前記第4のスイッチ素子のオン時間を、前記第1のスナバコンデンサと前記第2のスナバコンデンサの充電電荷が略完全放電される時間に設定し、前記出力検出部で検出した出力電力が一定電力未満のときは前記第3のスイッチ素子と前記第4のスイッチ素子のオン時間を、前記第1のスナバコンデンサと前記第2のスナバコンデンサの充電電荷が部分的に放電される時間に設定する、請求項1~3のいずれかに記載のインバータ回路。
- 前記制御部は、前記出力検出部で検出した出力電力が一定電力以上のときは前記第3のスイッチ素子と前記第4のスイッチ素子のオン時間を、前記第1のスナバコンデンサと前記第2のスナバコンデンサの充電電荷が略完全放電される時間に設定し、前記出力検出部で検出した出力電力が一定電力未満のときは前記第3のスイッチ素子と前記第4のスイッチ素子のオン時間をゼロに設定する、請求項1~3のいずれかに記載のインバータ回路。
- 前記制御部は、前記出力検出部で検出した出力電力が小さくなるに応じて、前記第3のスイッチ素子と前記第4のスイッチ素子のオン時間を短く設定する、請求項1~3のいずれかに記載のインバータ回路。
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US12/740,432 US8400799B2 (en) | 2009-02-06 | 2009-02-06 | Inverter circuit with controller for controlling switching elements based on a magnitude of output power |
EP09839652.6A EP2395646A4 (en) | 2009-02-06 | 2009-02-06 | Inverter circuit |
KR1020107010474A KR101558496B1 (ko) | 2009-02-06 | 2009-02-06 | 인터버 회로 |
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CN104158424B (zh) * | 2014-08-28 | 2017-01-04 | 深圳维普创新科技有限公司 | 推挽逆变器 |
JP2017163691A (ja) * | 2016-03-09 | 2017-09-14 | 株式会社三社電機製作所 | 三相ブリッジインバータ回路 |
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EP2548296B1 (fr) * | 2010-03-16 | 2015-05-06 | Devialet | Alimentation à découpage |
JP5492648B2 (ja) * | 2010-04-20 | 2014-05-14 | 株式会社三社電機製作所 | Dc−dcコンバータ回路 |
US20160277017A1 (en) * | 2011-09-13 | 2016-09-22 | Fsp Technology Inc. | Snubber circuit |
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