WO2010064489A1 - 電源装置 - Google Patents
電源装置 Download PDFInfo
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- WO2010064489A1 WO2010064489A1 PCT/JP2009/067724 JP2009067724W WO2010064489A1 WO 2010064489 A1 WO2010064489 A1 WO 2010064489A1 JP 2009067724 W JP2009067724 W JP 2009067724W WO 2010064489 A1 WO2010064489 A1 WO 2010064489A1
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
- H02M1/4225—Arrangements for improving power factor of AC input using a non-isolated boost converter
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0003—Details of control, feedback or regulation circuits
- H02M1/0016—Control circuits providing compensation of output voltage deviations using feedforward of disturbance parameters
- H02M1/0022—Control circuits providing compensation of output voltage deviations using feedforward of disturbance parameters the disturbance parameters being input voltage fluctuations
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Definitions
- the present invention relates to a power supply device, and more particularly to a power supply device including an active filter.
- an AC voltage from a commercial power source is rectified by a rectifier circuit such as a diode bridge, and smoothed by a smoothing circuit such as a capacitor to generate a DC voltage.
- a rectifier circuit such as a diode bridge
- a smoothing circuit such as a capacitor
- an active filter is provided between the rectifier circuit and the smoothing circuit, and the waveform and phase of the input current and the input voltage are matched.
- detection of input current, input voltage and output voltage, and generation of control signals for switching elements are all performed by hardware (electronic circuit).
- Patent Document 2 There is also a method of generating a control signal for the switching element by software (for example, see Japanese Patent Application Laid-Open No. 2004-260871 (Patent Document 2)).
- the target duty ratio is stored in the internal memory, only the output voltage of the active filter is detected, the control signal of the switching element is generated so that the detected voltage matches the target voltage, the input current and the input The voltage is not detected.
- Patent Document 1 since the control signal for the switching element is generated by hardware, flexible control according to changes in the input current, input voltage, and output voltage is possible, but many electrical elements are required. Thus, there is a problem that the space for the board for mounting them becomes large and the cost increases. In addition, a soft start circuit (for example, an RC series circuit) for preventing a steep increase in duty ratio at the time of start-up is required separately, which further increases the cost.
- a soft start circuit for example, an RC series circuit
- Patent Document 2 since the input current and the input voltage are not detected, when the duty ratio is corrected when the input signal is disturbed, or when a duty ratio that does not require correction is given, a switching element is used. The loss of will increase. Further, when the input voltage decreases, the difference between the input voltage and the output voltage increases, and the loss in the switching element increases. For this reason, the switching element may be destroyed.
- a main object of the present invention is to provide a power supply device that is small in size, low in price, and low in switching element loss.
- a power supply device includes a rectifier circuit that rectifies a first AC voltage, an active filter that is provided at the next stage of the rectifier circuit, and a smoothing circuit that generates a DC voltage by smoothing an output voltage of the active filter. And an inverter for converting a DC voltage into a second AC voltage.
- the active filter includes a reactor having one terminal receiving the output voltage of the rectifier circuit, a diode having an anode connected to the other terminal of the reactor, a cathode connected to the smoothing circuit, and the other terminal of the reactor and a reference voltage line. Switching elements connected between them.
- the power supply device further detects the input current, input voltage, and output voltage of the active filter, generates a target voltage based on the input voltage, matches the phase of the input current and the input voltage, and outputs the active filter.
- a microcomputer for controlling on / off of the switching element so that the voltage matches the target voltage is provided.
- the microcomputer reduces the target voltage in response to a decrease in the input voltage.
- the microcomputer stops the on / off control of the switching element, and the microcomputer has a second current larger than the first threshold current.
- the threshold current exceeds the inverter control
- the inverter control is further stopped.
- the microcomputer stops the on / off control of the switching element, and the second output is larger than the first threshold voltage. If the threshold voltage is exceeded, the inverter control is further stopped.
- the microcomputer includes a first calculation unit that calculates a target duty ratio based on an input voltage, an input current, an output voltage, and a target voltage, a storage unit that stores the duty ratio of the previous cycle, and a first And a second calculation unit that calculates the duty ratio of the current cycle based on the target duty ratio calculated by the calculation unit and the duty ratio of the previous cycle stored in the storage unit.
- the second calculation unit calculates the duty ratio of the current period so that the deviation between the target duty ratio and the duty ratio of the previous period gradually decreases.
- the second calculation unit calculates the duty ratio of the current period so that the deviation between the target duty ratio and the duty ratio of the previous period is gradually reduced at the time of startup.
- the second calculation unit calculates the duty ratio of the current period so that the deviation gradually decreases.
- the microcomputer stops the on / off control of the switching element, and the microcomputer has a second current larger than the first threshold current.
- the threshold current exceeds the inverter control
- the inverter control is further stopped.
- the microcomputer stops the on / off control of the switching element, and the second output is larger than the first threshold voltage. If the threshold voltage is exceeded, the inverter control is further stopped.
- the microcomputer includes a first calculation unit that calculates a target duty ratio based on an input voltage, an input current, an output voltage, and a target voltage, a storage unit that stores a duty ratio of a previous period, and a first calculation unit And a second calculation unit that calculates the duty ratio of the current cycle so that the deviation between the target duty ratio calculated by the above and the duty ratio of the previous cycle stored in the storage unit is gradually reduced.
- the second calculation unit calculates the duty ratio of the current period so that the deviation is not the first time when restarting from the state where only the on / off control of the switching element is stopped, and controls the inverter. At the time of restart from the state where is stopped, the duty ratio of the current cycle is calculated so that the deviation disappears in the second time shorter than the first time.
- the input current, the input voltage, and the output voltage of the active filter are detected, the target voltage is generated based on the input voltage, the phase of the input current and the input voltage coincides, and the active filter
- a microcomputer for controlling on / off of the switching element so that the output voltage matches the target voltage. Therefore, for example, the loss in the switching element can be reduced by reducing the target voltage in response to the reduction in the input voltage.
- the active filter is controlled by the microcomputer, the size of the apparatus can be reduced and the cost can be reduced.
- FIG. 5 is a diagram for describing an operation of a duty ratio calculation unit illustrated in FIG. 4.
- FIG. 5 is a diagram for explaining an operation of a storage unit illustrated in FIG. 4.
- 10 is a flowchart illustrating a modification of the third embodiment.
- FIG. 20 is a block diagram showing another modification example of the third embodiment.
- FIG. 1 is a block diagram showing a configuration of a power supply device according to Embodiment 1 of the present invention.
- the power supply device includes a rectifier circuit 2, voltage dividing resistors 7 and 15, a current detection resistor 8, an amplifier 9, an active filter 10, a smoothing capacitor 14, an inverter 16, and a microcomputer 18.
- the rectifier circuit 2 includes four diodes 3 to 6 that are bridge-connected, and full-wave rectifies the AC voltage from the AC power source 1. An AC voltage is applied between the anodes of the diodes 3 and 4.
- the cathodes of the diodes 3 and 4 are both connected to the positive output node 2a, the cathodes of the diodes 5 and 6 are connected to the anodes of the diodes 3 and 4, respectively, and the anodes of the diodes 5 and 6 are both connected to the negative output node 2b. Is done.
- the voltage dividing resistor 7 is connected between the positive-side output node 2a of the rectifier circuit 2 and the reference voltage line, and divides the output voltage of the rectifier circuit 2, that is, the input voltage Vin of the active filter 10, to reduce the input voltage Vin.
- a signal shown is generated and given to the microcomputer 18.
- the current detection resistor 8 is connected between the negative side input node 16b of the inverter 16 and the negative side output node 2b of the rectifier circuit 2, and outputs a signal indicating the input current Iin of the active filter 10.
- the amplifier 9 amplifies the output signal of the current detection resistor 8 and supplies it to the microcomputer 18.
- the negative input node 16b of the inverter 16 is connected to a reference voltage line.
- the active filter 10 includes a reactor 11, a diode 12, and an IGBT (Insulated Gate Bipolar Transistor) 13.
- One terminal of the reactor 11 is connected to the positive output node 2 a of the rectifier circuit 2.
- the anode of diode 12 is connected to the other terminal of reactor 11, and its cathode is connected to positive side input node 16 a of inverter 16.
- the collector of IGBT 13 is connected to the other terminal of reactor 11, its emitter is connected to a reference voltage line, and its gate receives control signal ⁇ C from microcomputer 18.
- the smoothing capacitor 14 is connected between the cathode of the diode 12 and the reference voltage line, and smoothes the output voltage Vo of the active filter 10 to generate a DC voltage.
- the voltage dividing resistor 15 is connected in parallel to the smoothing capacitor 14, divides the output voltage Vo of the active filter 10, generates a signal indicating the output voltage Vo, and supplies the signal to the microcomputer 18.
- the inverter 16 converts the output voltage Vo of the active filter 10 into a three-phase AC voltage and applies the three-phase AC voltage to the AC motor 17.
- the microcomputer 18 controls the inverter 16 based on the DC current signal from the inverter 16 and the motor position signal from the motor 17. Further, the microcomputer 18 performs on / off control of the IGBT 13 based on the input voltage Vin, the input current Iin, and the output voltage Vo, and makes the power factor 1 by matching the waveforms and phases of the input voltage Vin and the input current Iin. At the same time, the output voltage Vo is matched with the target voltage Vt. Further, the microcomputer 18 decreases the target voltage Vt in response to the decrease of the input voltage Vin.
- the microcomputer 18 includes voltage detection units 20 and 22, a current detection unit 21, a target voltage setting unit 23, and a signal generation unit 24.
- the voltage detector 20 generates a digital signal indicating the waveform, phase, amplitude, and the like of the input voltage Vin of the active filter 10 based on the output signal of the voltage dividing resistor 7.
- the current detection unit 21 generates a digital signal indicating the waveform, phase, amplitude, and the like of the input current Iin of the active filter 10 based on the output signal of the amplifier 9.
- the voltage detector 22 generates a digital signal indicating the level of the output voltage Vo of the active filter 10 based on the output signal of the voltage dividing resistor 15.
- the target voltage setting unit 23 generates the target voltage Vt based on the output signal of the voltage detection unit 20.
- the target voltage Vt decreases as the input voltage Vin of the active filter 10 decreases.
- the signal generation unit 24 generates a control signal ⁇ C based on the input voltage Vin, the input current Iin, the output voltage Vo, and the target voltage Vt, controls the IGBT 13 on / off, and the waveforms of the input voltage Vin and the input current Iin The phase is matched to bring the power factor close to 1, and the output voltage Vo is matched to the target voltage Vt.
- the input voltage Vin and the output voltage Vo are controlled to have a certain relationship. Further, the target voltage Vt is lowered as the input voltage Vin decreases so that the power loss does not change even when the input voltage Vin decreases.
- the on / off cycle of the IGBT 13 by the control signal ⁇ C is determined by an arbitrary set value stored in the microcomputer 18.
- an arbitrary set value can be changed by storing an arbitrary set value using a flash memory capable of rewriting data. Due to noise and noise terminal voltage problems, the switching period of the active filter 10 is generally set to 15 kHz to 20 kHz.
- the control signal ⁇ C is generated with a zero cross detection signal ⁇ ZC generated by the microcomputer 18 based on the input voltage Vac as shown in FIG. 2 as a trigger.
- the voltage Vac is obtained by full-wave rectifying a sinusoidal AC voltage.
- the microcomputer 18 samples the input voltage Vac, and raises the zero cross detection signal ⁇ ZC to the “H” level when the input voltage Vac falls below a preset threshold voltage Vth (times t0, t2, t4)
- the zero cross detection signal ⁇ ZC is lowered to the “L” level (time t1, t3, t5), and the zero cross detection signal ⁇ ZC is generated by software.
- a zero cross detection signal ⁇ ZC is generated by using a circuit combining a resistance element, a diode, and a photocoupler, or hardware such as a comparator, and the signal ⁇ ZC is input to the microcomputer 18 as an output trigger of the control signal ⁇ C. Also good.
- the voltage level is compared and the control signal ⁇ C of the IGBT 13 is generated in the microcomputer 18. That is, since the microcomputer 18 performs the basic operation of detecting the input voltage Vin, the input current Iin, and the output voltage Vo and matching the phases of the input voltage Vin and the input current Iin, the power can be reduced while reducing the hardware configuration. The rate can be improved and the harmonic current can be suppressed.
- the loss at the IGBT 13 can be reduced.
- FIG. 3 is a diagram showing a main part of a power supply device according to Embodiment 2 of the present invention.
- the overall configuration of this power supply apparatus is the same as that of the power supply apparatus of the first embodiment.
- an alternating current comparison unit 30 and a direct current voltage comparison unit 31 are added to the microcomputer 18 in addition to the configuration of FIG.
- the alternating current comparison unit 30 obtains the input current Iin based on the output signal of the current detection unit 21 in FIG. 1, and the input current Iin and preset threshold currents Ith1, Ith2 (where Ith1> Ith2) ).
- AC current comparator 30 sets both signals ⁇ I1 and ⁇ I2 to “H” level when Ith2> Iin, and sets signals ⁇ I1 and ⁇ I2 to “H” level and “L” level when Ith1> Iin> Ith2, When Iin> Ith1, both signals ⁇ I1 and ⁇ I2 are set to the “L” level.
- the DC voltage comparison unit 31 obtains the output voltage Vo based on the output signal of the voltage detection unit 22 of FIG. 1, and the output voltage Vo and preset threshold voltages Vth1, Vth2 (where Vth1> Vth2 Compared to).
- DC voltage comparison unit 31 sets both signals ⁇ V1 and ⁇ V2 to “H” level when Vth2> Vo, and sets signals ⁇ V1 and ⁇ V2 to “H” level and “L” level when Vth1> Vo> Vth2, When Vo> Vth1, the signals ⁇ V1 and ⁇ V2 are both set to the “L” level.
- the microcomputer 18 controls the inverter 16 when both the signals ⁇ I1 and ⁇ V1 are at “H” level, and when at least one of the signals ⁇ I1 and ⁇ V1 is at the “L” level, All the transistors are turned off to stop the control of the inverter 16.
- the signal generator 24 When the signals ⁇ I2 and ⁇ V2 are both at “H” level, the signal generator 24 generates the control signal ⁇ C and controls the IGBT 13 on / off, and at least one of the signals ⁇ I2 and ⁇ V2 is “L”. When the level is reached, generation of the control signal ⁇ C is stopped and the IGBT 13 is turned off.
- FIG. 4 is a diagram showing a main part of a power supply device according to Embodiment 3 of the present invention.
- the overall configuration of this power supply apparatus is the same as that of the power supply apparatus of the first embodiment.
- the signal generation unit 24 of the microcomputer 18 includes a target duty ratio calculation unit 35, a storage unit 36, a duty ratio calculation unit 37, and a signal waveform generation unit 38.
- one cycle of the input voltage Vin and the input current Iin is divided into (N + 1) sections (N is a positive integer), and a duty ratio DU is set for each section.
- the target duty ratio calculation unit 35 calculates a target duty ratio DUt for each section based on the input voltage Vin, the input current Iin, the output voltage Vo, and the target voltage Vt.
- the duty ratios DUp0 to DUpN of all sections of the previous cycle are stored in the addresses 0 to N of the storage unit 36, respectively.
- the duty ratio calculation unit 37 gradually eliminates the deviation between the target duty ratio DUt of the current section and the duty ratio DUp of the section corresponding to the previous period stored in the storage unit 36 during a predetermined number of periods.
- the duty ratio DU of the current section of the current cycle is calculated.
- the signal waveform generator 38 generates a waveform of the control signal ⁇ C based on the duty ratio DU generated by the duty ratio calculator 37.
- an excessive rapid increase in the input current Iin and the output voltage Vo can be suppressed, so that damage to electronic elements such as the IGBT 13 can be prevented.
- the duty ratio DU may be approximated to the target duty ratio DUt using PID control, which is a feedback control technique, may be approximated to the target duty ratio DUt by a predetermined percentage of deviation, or other methods are adopted. May be.
- duty ratio DUp of the storage unit 36 may be rewritten for each period or may be rewritten for each arbitrary period.
- the duty ratio DU is controlled so as to gradually approach the target duty ratio DUt for each cycle. Control may be performed so as to gradually approach the ratio DUt.
- the duty ratio calculation unit 37 outputs the target duty ratio DUt as it is to the signal waveform generation unit 38 as the duty ratio DU.
- the above startup includes not only a normal startup but also a restart after stopping only the control of the IGBT 13 shown in the second embodiment, and a restart after driving of the IGBT 13 and the inverter 16 is stopped.
- an excessive rapid increase in the input current Iin and the output voltage Vo accompanying a sudden increase in the duty ratio DU at the time of startup can be suppressed, so that damage to electronic elements such as the IGBT 13 can be prevented. .
- the duty ratio DU is controlled to gradually approach the target duty ratio DUt for each period.
- the duty ratio DU may be adjusted only when the deviation Dsa from the duty ratio DUp of the section to be exceeded exceeds a predetermined threshold deviation Dth.
- FIG. 7 is a flowchart showing the operation of the signal generator 24 of such a modification.
- the signal generator 24 detects an input voltage Vin, an input current Iin, an output voltage Vo, and a target voltage Vt (step S1), and calculates a target duty ratio DUt based on the detection result (step S2). .
- a deviation Dsa between the target duty ratio DUt of the current section and the duty ratio DUp of the section corresponding to the previous period stored in the storage unit 36 is calculated (step S3), and the deviation Dsa is calculated from the threshold deviation Dth. Is also larger (step S4).
- the function f (Dsa) used in step S5 is a function that, for example, brings the duty ratio DU closer to the target duty ratio DUt by a predetermined ratio of the deviation Dsa.
- FIG. 8 is a block diagram showing a configuration of the signal generation unit 24 according to still another modification of the third embodiment, and is a diagram contrasted with FIG. In FIG. 8, this modified example is different from the third embodiment in that the signals ⁇ I1, ⁇ I2, ⁇ V1, and ⁇ V2 shown in FIG.
- the duty ratio calculating unit 37 restarts after the on / off control of the IGBT 13 and the control of the inverter 16 are stopped by the signals ⁇ I2 and ⁇ V2
- the duty ratio DU is set to the target duty ratio by a relatively small ratio of the deviation Dsa.
- a function f1 (Dsa) that approaches DUt is employed to bring the duty ratio DU closer to the target duty ratio DUt at a relatively slow speed.
- the load impedance of the active filter 10 is small, when the duty ratio DU increases rapidly, the input current Iin and the output voltage Vo increase rapidly, and electronic elements such as the IGBT 13 are likely to be damaged. .
- the duty ratio calculation unit 37 restarts only after the on / off control of the IGBT 13 is stopped by the signals ⁇ I1 and ⁇ V1
- the duty ratio DU is changed to the target duty ratio DUt by a relatively large ratio of the deviation Dsa.
- the approaching function f2 (Dsa) is employed to bring the duty ratio DU closer to the target duty ratio DUt at a relatively high speed.
- the inverter 17 is controlled and the motor 17 is driven to rotate, the DC voltage Vo is necessary, and the input current Iin and the output voltage Vo are not affected even when the on / off control of the IGBT 13 is resumed. This is because a drastic increase in the amount is unlikely to occur.
- it is possible to prevent damage to the IGBT 13 and to smoothly restart it.
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Abstract
Description
図1は、この発明の実施の形態1による電源装置の構成を示すブロック図である。図1において、この電源装置は、整流回路2、分圧抵抗器7,15、電流検出抵抗器8、アンプ9、アクティブフィルタ10、平滑コンデンサ14、インバータ16、およびマイクロコンピュータ18を備える。
このような電源装置では、一般的に入力電流Iinや出力電圧Voが過大になった場合は、IGBT13の破損を防止するために全体のシーケンス制御を停止するような手段が設けられている。しかし、インバータ16を停止させると、負荷であるモータ17も停止してしまい、その影響は大きい。そこで、この実施の形態2では、インバータ16を停止させる前に、まずIGBT13の制御のみを停止させてIGBT13の破損を防止する。
図4は、この発明の実施の形態3による電源装置の要部を示す図である。この電源装置の全体構成は、実施の形態1の電源装置と同じである。この電源装置では、マイクロコンピュータ18の信号生成部24は、目標デューティ比算出部35、記憶部36、デューティ比算出部37、および信号波形生成部38を含む。
Claims (8)
- 第1の交流電圧を整流する整流回路(2)と、
前記整流回路(2)の次段に設けられたアクティブフィルタ(10)と、
前記アクティブフィルタ(10)の出力電圧(Vo)を平滑化して直流電圧を生成する平滑回路(14)と、
前記直流電圧を第2の交流電圧に変換するインバータ(16)とを備え、
前記アクティブフィルタ(10)は、
一方端子が前記整流回路(2)の出力電圧を受けるリアクトル(11)と、
アノードが前記リアクトル(11)の他方端子に接続され、カソードが前記平滑回路(14)に接続されたダイオード(12)と、
前記リアクトル(11)の他方端子と基準電圧のラインとの間に接続されたスイッチング素子(13)とを含み、
さらに、前記アクティブフィルタ(10)の入力電流(Iin)、入力電圧(Vin)、および出力電圧(Vo)を検出し、前記入力電圧(Vin)に基づいて目標電圧(Vt)を生成し、前記入力電流(Iin)と前記入力電圧(Vin)の位相が一致し、かつ前記アクティブフィルタ(10)の出力電圧(Vo)が前記目標電圧(Vt)に一致するように前記スイッチング素子(13)をオン/オフ制御するマイクロコンピュータ(18)を備える、電源装置。 - 前記マイクロコンピュータ(18)は、前記入力電圧(Vin)が低下したことに応じて前記目標電圧(Vt)を低下させる、請求の範囲第1項に記載の電源装置。
- 前記マイクロコンピュータ(18)は、
前記入力電流(Iin)が第1のしきい値電流(Ith2)を超えた場合は、前記スイッチング素子(13)のオン/オフ制御を停止し、前記入力電流(Iin)が前記第1のしきい値電流(Ith2)よりも大きな第2のしきい値電流(Ith1)を超えた場合は、さらに前記インバータ(16)の制御を停止し、
前記出力電圧(Vo)が第1のしきい値電圧(Vth2)を超えた場合は、前記スイッチング素子(13)のオン/オフ制御を停止し、前記出力電圧(Vo)が前記第1のしきい値電圧(Vth2)よりも大きな第2のしきい値電圧(Vth1)を超えた場合は、さらに前記インバータ(16)の制御を停止する、請求の範囲第1項に記載の電源装置。 - 前記マイクロコンピュータ(18)は、
前記入力電圧(Vin)、前記入力電流(Iin)、前記出力電圧(Vo)、および前記目標電圧(Vt)に基づいて目標デューティ比(DUt)を算出する第1の算出部(35)と、
前周期のデューティ比(DUp)を記憶した記憶部(36)と、
前記第1の算出部(35)によって算出された目標デューティ比(DUt)と前記記憶部(36)に記憶された前周期のデューティ比(DUp)とに基づいて現周期のデューティ比(DU)を算出する第2の算出部(37)とを含む、請求の範囲第1項に記載の電源装置。 - 前記第2の算出部(37)は、前記目標デューティ比(DUt)と前記前周期のデューティ比(DUp)との偏差が徐々に小さくなるように現周期のデューティ比(DU)を算出する、請求の範囲第4項に記載の電源装置。
- 前記第2の算出部(37)は、起動時には、前記目標デューティ比(DUt)と前記前周期のデューティ比(DUp)との偏差が徐々に小さくなるように現周期のデューティ比(DU)を算出する、請求の範囲第4項に記載の電源装置。
- 前記第2の算出部(37)は、前記目標デューティ比(DUt)と前記前周期のデューティ比(DUp)との偏差(Dsa)がしきい値偏差(Dth)を超えた場合は、前記偏差(Dsa)が徐々に小さくなるように現周期のデューティ比(DU)を算出する、請求の範囲第4項に記載の電源装置。
- 前記マイクロコンピュータ(18)は、
前記入力電流(Iin)が第1のしきい値電流(Ith2)を超えた場合は、前記スイッチング素子(13)のオン/オフ制御を停止し、前記入力電流(Iin)が前記第1のしきい値電流(Ith2)よりも大きな第2のしきい値電流(Ith1)を超えた場合は、さらに前記インバータ(16)の制御を停止し、
前記出力電圧(Vo)が第1のしきい値電圧(Vth2)を超えた場合は、前記スイッチング素子(13)のオン/オフ制御を停止し、前記出力電圧(Vo)が前記第1のしきい値電圧(Vth2)よりも大きな第2のしきい値電圧(Vth1)を超えた場合は、さらに前記インバータ(16)の制御を停止し、
前記マイクロコンピュータ(18)は、
前記入力電圧(Vin)、前記入力電流(Iin)、前記出力電圧(Vo)、および目標電圧(Vt)に基づいて目標デューティ比(DUt)を算出する第1の算出部(35)と、
前周期のデューティ比(DUp)を記憶した記憶部(36)と、
前記第1の算出部(35)によって算出された目標デューティ比(DUt)と前記記憶部(36)に記憶された前周期のデューティ比(DUp)との偏差(Dsa)が徐々に小さくなるように現周期のデューティ比(DU)を算出する第2の算出部(37)とを含み、
前記第2の算出部(37)は、前記スイッチング素子(13)のオン/オフ制御のみが停止された状態からの再起動時は、前記偏差(Dsa)が第1の時間でなくなるように現周期のデューティ比(DU)を算出し、前記インバータ(16)の制御が停止された状態からの再起動時は、前記第1の時間よりも短い第2の時間で前記偏差(Dsa)がなくなるように現周期のデューティ比(DU)を算出する、請求の範囲第1項に記載の電源装置。
Priority Applications (3)
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US13/128,905 US8743569B2 (en) | 2008-12-03 | 2009-10-13 | Power supply device |
CN2009801475274A CN102227866A (zh) | 2008-12-03 | 2009-10-13 | 电源装置 |
EP09830257A EP2369732A1 (en) | 2008-12-03 | 2009-10-13 | Power supply device |
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JP2008308434A JP4487009B2 (ja) | 2008-12-03 | 2008-12-03 | 電源装置 |
JP2008-308434 | 2008-12-03 |
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EP (1) | EP2369732A1 (ja) |
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JP4566267B1 (ja) * | 2009-04-21 | 2010-10-20 | シャープ株式会社 | 電源装置 |
JP5752234B2 (ja) * | 2011-03-10 | 2015-07-22 | 三菱電機株式会社 | 電力変換装置 |
JP5881477B2 (ja) * | 2012-03-06 | 2016-03-09 | 三菱電機株式会社 | スイッチング素子駆動回路 |
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EP3014738A4 (en) * | 2013-06-25 | 2017-03-22 | Hewlett-Packard Development Company, L.P. | Uninterruptible power supply with inverter,charger, and active filter |
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US10291122B2 (en) | 2015-06-29 | 2019-05-14 | Semiconductor Components Industries, Llc | Input voltage detection circuit and power supply including the same |
US9939463B2 (en) * | 2016-04-06 | 2018-04-10 | United Microelectronics Corp. | Test circuit for testing a device-under-test by using a voltage-setting unit to pull an end of the device-under-test to a predetermined voltage |
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US8743569B2 (en) | 2014-06-03 |
CN102227866A (zh) | 2011-10-26 |
JP4487009B2 (ja) | 2010-06-23 |
EP2369732A1 (en) | 2011-09-28 |
JP2010136493A (ja) | 2010-06-17 |
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