WO2002097958A2 - Schaltungsanordnung mit einer regelschaltung - Google Patents
Schaltungsanordnung mit einer regelschaltung Download PDFInfo
- Publication number
- WO2002097958A2 WO2002097958A2 PCT/IB2002/002067 IB0202067W WO02097958A2 WO 2002097958 A2 WO2002097958 A2 WO 2002097958A2 IB 0202067 W IB0202067 W IB 0202067W WO 02097958 A2 WO02097958 A2 WO 02097958A2
- Authority
- WO
- WIPO (PCT)
- Prior art keywords
- circuit
- duty cycle
- value
- predeterminable
- maximum value
- Prior art date
Links
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0003—Details of control, feedback or regulation circuits
- H02M1/0012—Control circuits using digital or numerical techniques
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Definitions
- the invention relates to a circuit arrangement with a control circuit. It can be used to control converters, in particular resonant converters, with several outputs.
- a DC voltage present on the input side is first chopped, and the AC voltage thus created, which is present as a chopped DC voltage, is processed by means of circuit parts which contain resonance circuit elements.
- transformers are also used which cause electrical isolation of the input and output sides of the converter.
- Such converters can be inexpensive, small and light
- Manufacture power supply devices / switching power supplies that can be used advantageously, for example, in consumer electronics devices such as set-top boxes, satellite receivers, television sets, computer monitors, video recorders, compact audio systems. These applications often require converters that generate multiple output voltages from one DC input voltage at several converter outputs.
- German patent application with the official file number 101 22 534.2 (filing date May 9, 2001) describes a resonant converter which has several outputs and which contains a transformer with a primary winding and at least two secondary windings with different winding orientations.
- the converter also contains a control circuit for regulating the converter output voltages.
- a known concept for a converter protection circuit includes the use of fuses arranged on the secondary side which blow in the event of an overload. The blown fuses must be replaced with new fuses before the converter is started up again.
- the invention has for its object to provide a circuit arrangement with a control circuit for converters with multiple outputs, one with contains as little circuit and computing effort as possible to produce protective circuit that reliably protects against overloads.
- the object is achieved by a circuit arrangement with a control circuit which is used to generate a pulse-width-modulated control signal as a function of two measurement signals present at the inputs of the control circuit, and with a comparison circuit for comparing the duty cycle of the control signal with a predeterminable duty cycle maximum value and duty cycle minimum value, with one outside of the range between the maximum duty cycle value and the minimum duty cycle value, the circuit arrangement provides for the control information corresponding to this overrange to be output.
- this circuit arrangement is able to reliably switch off a converter.
- the protection circuit against overload can be implemented with a few inexpensive components.
- the control information is in particular by simply switching off the
- Control signal i.e. Setting the control signal to the value zero, delivered (claim 2); other variants would be, for example, the transmission of a digital signal in the control signal or the delivery of a control signal via a separate output of the circuit arrangement.
- Claims 3 to 5 characterize an overvoltage protection that protects precisely and reliably against overvoltages and thereby interacts with the overload protection circuit.
- Claim 6 enables a feedback loop, in which a feedback path for the transmission of feedback signals, which in particular cause the connected converter to be switched off, is still present even if an optocoupler fails.
- the invention also relates to integrated circuits which carry parts of the circuit arrangement according to the invention (claims 7 to 9).
- the invention also relates to a resonant converter which has the circuit arrangement according to the invention and / or at least one of the integrated circuits according to the invention (claim 10).
- a resonant converter which has the circuit arrangement according to the invention and / or at least one of the integrated circuits according to the invention (claim 10).
- FIG. 1 shows a resonant converter with two outputs
- FIG. 2 shows a half-bridge circuit for the resonant converter
- FIGS. 3A, 3B and 3C different output filters for the resonant converter
- 4 shows an equivalent circuit diagram for the resonant converter
- FIG. 5 to FIG. 7 voltage and current profiles in the resonant converter
- FIG. 8 to FIG. 10 shows various design options for a resonant converter according to the invention
- FIG. 11 shows an example for the coupling of converter outputs with the
- Fig. 12 is a block diagram for an embodiment of the control circuit of the resonant converter.
- Fig. 13 is a block diagram for a control circuit with overvoltage and overload protection circuits.
- the circuit arrangement shown in Fig.l shows a resonant converter 1 with an inverter 2, which is designed here as a chopper and a DC voltage (not shown) into an AC voltage, i.e. converts a chopped DC voltage Us here.
- the inverter 2 is coupled via a capacitor 3 to a transformer 4 which has a primary winding 5 and two secondary windings 6a and 6b.
- the secondary windings 6a and 6b have different winding orientations, so that with a positive voltage Up across the primary winding 5, the voltage Usa generated at the secondary winding 6a is also positive, whereas the voltage Usb falling across the secondary winding 6b is negative with a positive voltage Up.
- the transformer 4 has a common transformer core for both the primary winding 5 and
- a current flowing through the capacitor 3 into the primary winding 5 is designated Ic.
- the secondary winding 6a is coupled via a diode Da and an output filter Fa to an output 7a at which an output voltage Ua drops.
- the secondary winding 6b is connected via a diode Db and a filter Fb to an output 7b at which an output voltage U drops.
- the converter 1 also contains a feedback loop with a control circuit 8, which is coupled on the input side to the outputs 7a and 7b of the converter 1 and on the output side to the inverter 2.
- the control circuit 8 depending on the voltages Ua and 7b present at the outputs 7a and 7b, sets the frequency and the duty cycle of the
- Inverter 2 supplied voltage Us in order to regulate the output voltages Ua and Uu to predetermined desired voltage values.
- the capacitor 3, the main inductance and the leakage inductances of the transformer 4 constitute resonant circuit elements represent which are excited to oscillate by the alternating voltage Us and cause a corresponding course of the current Ic flowing in the circuit part having the resonance circuit elements and the voltage Up dropping across the primary winding.
- a current Ia which flows through the diode Da to the filter Fa, is generated, specifically for the time in which
- the voltage Usa is greater than the voltage present at the input of the filter Fa minus the diode forward voltage across the diode Da. If the voltage Up on the primary winding 5 has positive voltage values, no current is generated by the secondary winding 6b, since in this case the diode Db blocks. In the case of negative voltage values of the voltage Up there is a positive one
- FIG. 2 shows an embodiment variant of the inverter or chopper 2 from FIG.
- a control signal 20 generated by the control circuit 8, which represents a pulse sequence here, is fed to a half-bridge driver circuit 21, which generates control signals 22 and 23 for the switching elements 24 and 25, which form a half-bridge circuit, from the control signal 20.
- the switching elements 24 and 25 are designed as MOSFET transistors.
- the control signals 22 and 23 are supplied to gate terminals (control terminals) of the transistors 24 and 25.
- the inverter 2 converts a direct voltage U DC into the alternating voltage Us by alternately switching the switching elements 24 and 25 on and off.
- the DC voltage UD C is generated, for example, in the case of power supply devices / power supply units / chargers from the AC voltage of an AC voltage network by rectification.
- 3A to 3C show design variants of the output filters Fa and Fb of the resonant converter 1. These have a connection A which is connected to the diodes Da and Db. The connections B and C are connected to the outputs 7a and 7b of the converter 1. 3 contains only a capacitor 30.
- the output filter according to FIG. 3B contains two capacitors 31 and 32 and an inductor 33.
- the output filter according to FIG. 3C contains a capacitor 34, an inductor 35 and a diode 36.
- 4 shows an equivalent circuit diagram for the resonant converter 1 from FIG. 1, in which the transformer 4 has been replaced by a transformer equivalent circuit diagram.
- the electrical function of the transformer 4 can here essentially by a primary-side leakage inductance Lrp, a main inductance Lh, a secondary-side leakage inductance Lrsa for the secondary winding 6a and a secondary-side
- Leakage inductance Lrsb for the secondary winding 6b are shown.
- the filters Fa and Fb are assumed to be ideal here and not shown, and neither is the control circuit 8.
- the pulse duty factor is determined here by the time period tsH and tsL, the upper switching element 24 being switched on and the lower switching element 25 being switched off during a time period tsH, and the upper switching element 24 being switched off and the lower switching element 25 being switched on during a time period tsL.
- the duty cycle results in tsH / tO.
- Time periods t0 each show the profiles of the alternating voltage Us, the current Ic through the capacitor 3, the current Ia through the main inductance La of the transformer 4, the current Ia supplied by the secondary winding 6a and the current Ib supplied by the secondary winding 6b. All winding ratios in the underlying circuit example according to the equivalent circuit shown in FIG. 4 are assumed to be one; Lrsa is also equal to Lrsb.
- the duty cycle is selected to be 50% in the operating case according to FIG. 5.
- current profiles of Ia and Ib with (almost) identical half-waves are generated in the periods tsH and tsL during the periods tsH and tsL.
- the duty cycle is reduced to 40%.
- the course of the current Ia is almost remained the same.
- the course of the current Ib now has half-waves with a reduced amplitude, so that the power transported via the secondary winding 6b to the output 7b is reduced.
- the current Ia is essentially reduced to zero and the amplitude of the half-waves of Ib are increased compared to FIG. 6, so that in this operating case there is no power from the secondary winding 6a to the output 7a, but one from the secondary winding 6b compared to FIG. 6 increased power is transported from the secondary winding 6b to the output 7b.
- FIGS. 5 to 7 make it clear that a very variable adaptation to different loads of the various converter outputs is possible with the converter circuit according to the invention.
- the converter according to the invention small tolerances of the output voltages can be achieved, in particular even with small output voltages and large output currents.
- 8 and 9 show variants of the converter 1 from FIG. 1, which are denoted by 1 'and 1 ".
- the two secondary windings 6a and 6b are galvanically coupled to one another; in the present case, they are connected to a common ground potential
- the secondary windings 6a and 6b are galvanically separated from one another in the configuration of converter 1. According to FIG.
- an additional external inductance L1 is also provided as a further variant, which is located on the primary side of transformer 4 between capacitor 3 and The primary winding 5 is arranged and acts as an additional inductive resonance circuit element in addition to the inductances of the transformer 4. With a given design of the transformer 4 with certain transformer inductances, this additional inductance can be used to adapt the resonance frequency of the converter.
- FIG. 9 shows additional external inductances L2a and L2b on the secondary side of the transformer 4.
- the inductor L2a is arranged between the secondary winding 6a and the diode Ta, the inductor L2b lies between the secondary winding 6b and the diode Db.
- converter variants are also possible in which additional external inductances are provided both on the primary side of the transformer 4 and on the secondary side of the transformer 4. 10 shows a converter variant 1 '"with a larger number of converter outputs. In the present case, the converter has four converter outputs.
- the transformer 4 now has two groups of secondary windings with different winding orientations (indicated by the letters a and b) , which on the one hand contain the secondary windings 6al and 6a2 and on the other hand the secondary windings 6b 1 and 6b2.
- the output voltages Ual and Ubl are supplied as measured variables to the control circuit 8.
- the control circuit 8 thus evaluates two output voltages here, the one output voltage Ual being generated by the secondary winding 6al from the group of secondary windings with the first winding orientation other of the rules sc Attitude 8 supplied output voltage Ubl is assigned to the secondary winding 6b 1 from the group of secondary windings of the opposite winding orientation.
- a measured variable, ie output voltage is evaluated here and used for regulation. This represents a particularly simple and effective regulation of the output voltages of the converter.
- Fig.l 1 shows that the control circuit as measured variables either directly evaluates the voltages at the converter outputs or the voltages at the connected loads of the converter, the latter being reduced compared to the corresponding output voltages due to voltage drops on the leads between the converter and the loads. Both variants are shown as examples in Fig.l 1.
- the two output voltages Ua and Ueb are present here at the converter outputs, to each of which a load Ra and a load Rb are connected.
- the connecting lines between the converter output supplying the output voltage Ua and the load Ra are represented here by a block 31.
- the connection lines between the output of the converter delivering the output voltage U i and the load Rb are represented by block 32.
- Fig.12 shows an exemplary embodiment of the control circuit 8.
- a first measurement signal Va and a second measurement signal Vb which correspond to the output voltages Ua and Uu or Ual and Ubl, are fed to the control circuit at their two inputs.
- the measurement signals Va and Vb are compared with reference signals Varef and Vbref.
- Subtractors 100 and 101 are used here.
- the subtractor 100 delivers the difference Varef -Va to a circuit block 102.
- the subtractor 101 supplies the difference Vbref -Vb to a circuit block 103.
- the circuit blocks 102 and 103 contain amplifiers and normalization circuits, so that the difference signal supplied by the subtractor 100 with a factor KA and that from the subtractor 101 delivered difference signal is multiplied by a factor KB.
- the following relationship applies here in this exemplary embodiment:
- kA-Varef kB -Vbref
- circuit blocks 102 and 103 are from one
- Adder 104 and a subtractor 105 further processed.
- the adder 104 adds the output signals of the circuit blocks 102 and 103 and supplies its output signal to a frequency controller 106, which is designed, for example, as a PID controller.
- the difference signal supplied by the subtractor 105 is fed to a duty cycle controller 107, which is also designed, for example, as a PID controller.
- the control signal 20 supplied by the control circuit 8 to the inverter 2 is now generated, which is a pulse-width-modulated signal here.
- the frequency of the signal 20, which is decisive for the frequency of the alternating voltage Us of the resonant converter, is set by the output signal of the frequency regulator 106.
- the duty cycle of the signal 20 that determines the duty cycle of the AC voltage Us is set by the duty cycle controller 107.
- the value of the measurement signal Va decreases in the control circuit according to FIG. 12, so that Va ⁇ Varef, this leads on the one hand to a decrease in the frequency set by the controller 106 and thus tends to increase in accordance with the behavior of a resonant converter output voltages generated by the resonant converter.
- the duty cycle of the signal 20 or the alternating voltage Us determined by the controller 107 is also reduced. This case is present, for example, in the operating state according to FIG. 6, where the power transported from the secondary winding 6a to the output 7a is increased compared to the power transported from the secondary winding 6b to the output 7b.
- the controller 107 increases the duty cycle of the signal 20 or the duty cycle of the alternating voltage Us, so that in this operating case the power distribution changes so that the power transported to the output 7b increases compared to the power transported to the output 7a is.
- the control behavior also applies accordingly to the design variants with more than two converter outputs. 13 shows a circuit arrangement which contains the components of the above control circuit 8 and is supplemented by an overload protection circuit and an overvoltage protection circuit; Furthermore, the half-bridge driver circuit 21 is part of this circuit arrangement. 13 are the input side of the circuit arrangement
- the measuring signal Va and a reference signal Varef are fed to an adding / subtracting device 201.
- the measuring signal Vb and a reference signal Vbref are fed to an adding / subtracting device 202.
- comparators 203 and 204 designed as comparators are provided.
- the comparator 203 compares the measurement signal Va with a maximum value Vamax.
- the comparator 204 compares the measurement signal Vb with a maximum value Vbmax. If the measurement signal Va exceeds the maximum value Vamax or if the measurement signal Vb exceeds the maximum value Vbmax, there is an overvoltage case.
- the output voltage of the comparator 203 jumps from its minimum value Vkmin to its maximum value Vkmax.
- an adjustment value 205 is generated, which is fed to the adding / subtracting device 202.
- the output voltage of the comparator 204 jumps from its minimum value Vkmin to its maximum value Vkmax.
- an adaptation value 206 is generated, which is fed to the adding / subtracting device 201.
- the adding / subtracting device 201 forms the difference between the reference signal Varef and the measuring signal Va and adds the adaptation value 206 to the resulting difference.
- the adding / subtracting device 202 forms the difference between the reference signal Vbref and the measuring signal Vb and adds them resulting difference the adaptation value 205.
- the outputs of the add / subtract devices 201 and 201 are connected to a circuit block 207 which comprises the circuit parts 102, 103, 104, 105, 106 and 107 of the control circuit 8 shown in FIG. 12, ie the outputs of adding / subtracting devices 201 and 202 are connected to the inputs of circuit blocks 102 and 103.
- the output signals 208 and 209 of the circuit block 207 that is to say the output signals of the controllers 106 and 107, are fed via two optocouplers 210 and 211, which bring about potential isolation, to the signal generator circuit 108, which generates the control signal 20 and its frequency and duty cycle depending on the Signals 208 and 209 sets.
- the control signal 20 is converted into control signals 22 and 23 by the half-bridge driver circuit.
- the circuit arrangement in FIG. 13 also contains a comparison circuit 212 which evaluates the respectively set pulse duty factor ⁇ of the control signal 20.
- the duty cycle represents the power distribution across the various converter outputs for the respective converter.
- the comparison circuit 212 determines whether the duty cycle ⁇ lies in a range between a predeterminable duty cycle minimum value ⁇ min and a predefinable duty cycle maximum value ⁇ max.
- the comparison circuit 212 causes the signal generator circuit 108 to provide control information to the half-bridge driver circuit of the respective resonant converter
- the Control information causes the control signals 22 and 23 to be switched off and thus the respective resonant converter to be switched off.
- the control information is passed on by switching off the control signal 20 and by switching off the control signals 22 and 23, which is the simplest solution for transmitting the control information. After the control information has been submitted, the connected converter is switched off.
- Blocks 213 and 214 indicate how circuit parts of the circuit arrangement shown in FIG. 13 can preferably be combined by means of one or more integrated circuits; Block 213 and / or block 214 are then implemented by means of an integrated circuit.
- Block 213 contains those with 21, 108, 212, 213, ⁇ max and ⁇ min designated circuit parts;
- the output signals of the optocouplers 210 and 211 are fed to the block 213 on the input side and the control signals 22 and 23 are output on the output side.
- Block 214 contains the circuit parts designated Varef, Vbref, 201, 202, 203, 204, 205, Wa and Wb.
- Block 214 receives the measurement signals Va and Vb on the input side; On the output side, signals 208 and 209 are emitted from block 214 to optocouplers 210 and 211
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
- Pulse Circuits (AREA)
- Electronic Switches (AREA)
Abstract
Description
Claims
Priority Applications (3)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
US10/479,091 US6898091B2 (en) | 2001-06-01 | 2002-05-30 | Circuit configuration comprising a control loop |
EP02733145A EP1397857A2 (de) | 2001-06-01 | 2002-05-30 | Schaltungsanordnung mit einer regelschaltung |
JP2003501035A JP4198588B2 (ja) | 2001-06-01 | 2002-05-30 | 制御ループを具える回路形態 |
Applications Claiming Priority (2)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
DE10126925.0 | 2001-06-01 | ||
DE10126925A DE10126925A1 (de) | 2001-06-01 | 2001-06-01 | Schaltungsanordnung mit einer Regelschaltung |
Publications (2)
Publication Number | Publication Date |
---|---|
WO2002097958A2 true WO2002097958A2 (de) | 2002-12-05 |
WO2002097958A3 WO2002097958A3 (de) | 2003-11-27 |
Family
ID=7687021
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
PCT/IB2002/002067 WO2002097958A2 (de) | 2001-06-01 | 2002-05-30 | Schaltungsanordnung mit einer regelschaltung |
Country Status (5)
Country | Link |
---|---|
US (1) | US6898091B2 (de) |
EP (1) | EP1397857A2 (de) |
JP (1) | JP4198588B2 (de) |
DE (1) | DE10126925A1 (de) |
WO (1) | WO2002097958A2 (de) |
Families Citing this family (14)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US7102320B1 (en) * | 2005-03-01 | 2006-09-05 | Hewlett-Packard Development Company, L.P. | Half-bridge control circuit |
CN1992493B (zh) * | 2005-12-30 | 2011-05-18 | 艾默生网络能源系统北美公司 | 一种谐振直流/直流变换器及其控制方法 |
JP4222421B2 (ja) * | 2007-02-28 | 2009-02-12 | サンケン電気株式会社 | 多出力スイッチング電源装置 |
FR2954511B1 (fr) * | 2009-12-17 | 2012-05-18 | Sagem Defense Securite | Procede de detection de panne d'une source de courant a decoupage et source de puissance correspondante |
EP2534746A2 (de) | 2010-02-08 | 2012-12-19 | Koninklijke Philips Electronics N.V. | Treiberschaltkreis zum antreiben eines lastenschaltkreises |
CN102214944B (zh) * | 2010-04-06 | 2015-09-02 | 力博特公司 | 一种ups电源的系统增益控制方法 |
KR101920673B1 (ko) * | 2012-01-31 | 2018-11-22 | 주식회사 솔루엠 | 컨버터 구동회로, 듀얼 모드 llc 공진 컨버터 시스템 및 듀얼 모드 llc 공진 컨버터 구동방법 |
US9201441B2 (en) * | 2012-12-18 | 2015-12-01 | Fairchild Semiconductor Corporation | DC/DC converter with shunt circuitry |
JP2015145830A (ja) * | 2014-02-03 | 2015-08-13 | 株式会社デンソーウェーブ | フォトカプラの劣化判定装置 |
JP6112529B2 (ja) * | 2014-10-02 | 2017-04-12 | 三菱電機株式会社 | チョッパ回路制御装置 |
JP7124297B2 (ja) * | 2017-10-31 | 2022-08-24 | 富士電機株式会社 | 電力変換装置 |
CN109004702B (zh) * | 2018-07-16 | 2021-10-26 | 成都安普利菲能源技术有限公司 | 一种电池放电分压系统 |
WO2022094830A1 (en) * | 2020-11-05 | 2022-05-12 | Astec International Limited | Control circuits and methods for regulating output voltages |
CN113394987B (zh) * | 2021-06-01 | 2023-01-20 | 深圳供电局有限公司 | 容量可调的供电设备 |
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US4578630A (en) | 1984-11-23 | 1986-03-25 | At&T Bell Laboratories | Buck boost switching regulator with duty cycle limiting |
US6212079B1 (en) | 2000-06-30 | 2001-04-03 | Power Integrations, Inc. | Method and apparatus for improving efficiency in a switching regulator at light loads |
DE10122534A1 (de) | 2001-05-09 | 2002-11-21 | Philips Corp Intellectual Pty | Resonanter Konverter |
Family Cites Families (7)
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US4084103A (en) * | 1977-06-07 | 1978-04-11 | Burns Iii William Wesley | System-state and operating condition sensitive control method and apparatus for electric power delivery systems |
US4941076A (en) * | 1988-10-12 | 1990-07-10 | Zenith Electronics Corporation | Start-up circuit for a high voltage DC to AC converter |
JP2690409B2 (ja) * | 1991-05-07 | 1997-12-10 | 株式会社テック | 高圧電源制御装置 |
US5659460A (en) | 1994-11-03 | 1997-08-19 | Vlt Corporation | Switch control in quantized power converters |
JPH10127047A (ja) | 1996-10-17 | 1998-05-15 | Canon Inc | スイッチング電源装置及び位相制御機器 |
EP0922323B1 (de) * | 1997-03-27 | 2002-10-30 | Koninklijke Philips Electronics N.V. | Numerisch gesteuerter schaltspannungswandler |
US6301128B1 (en) * | 2000-02-09 | 2001-10-09 | Delta Electronics, Inc. | Contactless electrical energy transmission system |
-
2001
- 2001-06-01 DE DE10126925A patent/DE10126925A1/de not_active Withdrawn
-
2002
- 2002-05-30 EP EP02733145A patent/EP1397857A2/de not_active Withdrawn
- 2002-05-30 US US10/479,091 patent/US6898091B2/en not_active Expired - Fee Related
- 2002-05-30 WO PCT/IB2002/002067 patent/WO2002097958A2/de active Application Filing
- 2002-05-30 JP JP2003501035A patent/JP4198588B2/ja not_active Expired - Fee Related
Patent Citations (3)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US4578630A (en) | 1984-11-23 | 1986-03-25 | At&T Bell Laboratories | Buck boost switching regulator with duty cycle limiting |
US6212079B1 (en) | 2000-06-30 | 2001-04-03 | Power Integrations, Inc. | Method and apparatus for improving efficiency in a switching regulator at light loads |
DE10122534A1 (de) | 2001-05-09 | 2002-11-21 | Philips Corp Intellectual Pty | Resonanter Konverter |
Also Published As
Publication number | Publication date |
---|---|
DE10126925A1 (de) | 2002-12-05 |
US6898091B2 (en) | 2005-05-24 |
EP1397857A2 (de) | 2004-03-17 |
JP4198588B2 (ja) | 2008-12-17 |
US20040145923A1 (en) | 2004-07-29 |
JP2004533198A (ja) | 2004-10-28 |
WO2002097958A3 (de) | 2003-11-27 |
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