US5825152A - Load-commutated synchronous motor drive - Google Patents

Load-commutated synchronous motor drive Download PDF

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US5825152A
US5825152A US08/750,086 US75008697A US5825152A US 5825152 A US5825152 A US 5825152A US 75008697 A US75008697 A US 75008697A US 5825152 A US5825152 A US 5825152A
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side converter
current
pulse
machine
pulse number
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Per-Lennart Eriksson
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ABB Industry Oy
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P25/00—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details
    • H02P25/02—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details characterised by the kind of motor
    • H02P25/022—Synchronous motors
    • H02P25/024—Synchronous motors controlled by supply frequency

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  • the present invention relates to a load-commutated synchronous motor drive, which comprise
  • a line-commutated network-side converter with dc terminals, and with ac terminals for connection to an alternating voltage network, and with a natural pulse number
  • a load-commutated machine-side converter with ac terminals for connection to a synchronous machine, and with dc terminals which are connected to the dc terminals of the network-side converter via a current-source dc intermediate link.
  • Synchronous motor drives of the kind described above are previously known from, for example, ABB Handbok Industri, Asea Brown Boveri AB Vasteras 1993 (referred to in the following as "ABB Handbok"), pages 276-284, from IEEE Transactions on Industry Applications Vol. IA-19, No.2, March/April 1983 (referred to in the following as "IEEE”), pages 217-222, and from H. Buhler:"Einbowung in die Theorie geregelter Drehstromantriebe", Birkhauser, Basel-Stuttgart 1977 (referred to in the following as "Buhler”), e.g. Band I, pages 21-23; Band II, pages 88-158.
  • the machine-side converter is of a line-commutated type, and the induced alternating voltage of the synchronous machine constitutes the commutating voltage of the converter.
  • This voltage decreases with the frequency, that is, with the speed of the machine, but since the resistance in the commutating circuit is negligible in comparison with the reactance down to relatively low speeds, the commutating capability of the machine is not influenced in any practical sense. At very low speeds, however, the effect of the resistance is no longer negligible, and the commutating capability of the machine is then not sufficient for commutation of intermediate-link currents which are greater than the limiting current for discontinuous current.
  • the torque disturbances occur with a frequency which is proportional to the machine frequency. It has proved that the frequency of the torque disturbances may typically coincide with a mechanical natural oscillation frquency of the drive system. This means that the torque disturbances will excite mechanical natural oscillations in the drive system. In such drive systems as are operating with a high current and a high torque at low speeds, these oscillations may become considerable, and the oscillations entail considerable disadvantages in the form of, for example, a high sound level, increased wear and a risk of mechanical damage. These disadvantages are particularly great in drive systems which are operating for lengthy periods at a critical speed, or which often pass through a critical speed range.
  • the invention aims to provide a synchronous motor drive of the kind described in the introductory part of the description, in which the above-mentioned torque disturbances and the drawbacks caused thereby are greatly reduced or completely eliminated in a simple and advantageous way.
  • the motor drive is provided with control members adapted, in connection with the commutations in the machine-side converter, and in dependence on the actual operating quantities of the machine, to determine whether the commutating capability of the machine is sufficient for commutation of the current in question and, if this is not the case, to execute the switching of the network-side converter to operation with a lower pulse number.
  • this determination is made by calculating the maximum current which the machine is capable of commutating, and comparing this current with the actual current.
  • the network-side converter is designed for operation with a plurality of different pulse numbers which are lower than the natural pulse number.
  • the system is then provided with control members adapted, in connection with commutation in the machine-side converter, to determine the highest of the pulse numbers which ensure commutation and to switch over the network-side converter for operation with this pulse number.
  • improved properties may be obtained by taking into account, when determining which pulse number of the network-side converter is to be used in connection with the commutation of the machine-side converter, the fact that also an insufficient machine voltage makes a contribution to the commutating capability.
  • FIG. 1a is a block diagram showing an example of a synchronous motor drive according to the invention
  • FIG. 1b shows the network-side converter in the motor drive according to FIG. 1a
  • FIG. 1c shows the machine-side converter in the motor drive according to FIG. 1a
  • FIG. 2 shows an example of the embodiment of the selector circuit for connection of the pulse number modulation and for switching between various pulse numbers
  • FIGS. 3a, 3b and 3e show commutating times and intermediate-link current for 12-pulse, 6-pulse and 3-pulse operation of the network-side converter
  • FIG. 4 shows how 2-pulse operation of the network-side converter may be achieved
  • FIG. 5 shows the function of an alternative embodiment of the invention, where the commutating capability of the machine, and also the recovery time of the thyristor valves, are taken into account when determining the pulse number during operation with a reduced pulse number,
  • FIG. 6 shows in the form of a flow chart how the selector circuit may be designed to achieve the function according to FIG. 5,
  • FIG. 8 illustrate how, according to a preferred embodiment of the invention, the commutating times are determined and the current is measured in such a way that the mean value thereof is kept constant both before and after and during the switching of the pulse number
  • FIG. 9 shows the principle of generation of control pulses for the network-side converter in FIG. 1, and
  • FIG. 10 shows in more detail how the current measurement is arranged in the converter according to FIG. 1.
  • a two-way single-phase bridge has the natural pulse number 2 and a two-way three-phase bridge the natural pulse number 6.
  • FIG. 1a An example of a 12-pulse synchronous motor drive according to the invention is shown in the form of a block diagram in FIG. 1a. It comprises a 6-phase synchronous machine 1, the six ac terminals of which are connected to a machine-side converter 2 consisting of the two dc series-connected two-way 6-pulse three-phase bridges 2A and 2B. This converter, in turn, is connected to a dc intermediate link consisting of the busbars PL and NL and an intermediate-link reactor 5. The intermediate link is supplied with direct current I d from a network-side converter 3, which consists of the two dc series-connected three-phase bridges 3A and 3B.
  • the latter are connected to a three-phase power network ACN via a converter transformer 4 with a delta-connected primary winding 40 and two secondary windings 41A and 41B, of which the former one is star-connected and the latter one delta-connected.
  • the intermediate-link reactor 5 is preferably designed with a relatively high inductance to reduce interharmonic disturbances, partly in the torque of the machine, partly in the network.
  • FIG. 1b schematically shows the network-side converter 3 with the two thyristor bridges 3A and 3B.
  • the bridges are dc series-connected and line-commutated.
  • the bridge 3A is connected to the star-connected secondary winding 41A of the transformer 4, and the bridge 3B is connected to the delta-connected secondary winding 41B.
  • Each bridge is a six-pulse two-way bridge. By the selected transformer connection, a phase displacement of 30° between the alternating voltages of the bridges is obtained, and the converter in its entirety is given the pulse number 12.
  • FIG. 1c schematically shows the machine-side converter 2 with the two three-phase bridges 2A and 2B.
  • the bridges are dc series-connected and line-commutated.
  • the synchronous machine 1 is of six-phase design and has two three-phase winding systems 104 and 105 which are displaced 30° between themselves.
  • the three windings in the system 104 are connected to the alternating-voltage connections of the bridge 2A, and the three windings in the system 105 are connected to the alternating-voltage connections of the bridge 2B.
  • this converter is in its entirety given the pulse number 12.
  • the valves of the two converters 2 and 3 consist of thyristor valves, equipped with conventional thyristors (i.e. thyristors which cannot be extinguished with the aid of a control signal).
  • the commutating voltages of the converters consist, for the converter 2, primarily of the induced alternating voltage of the synchronous machine and, for the converter 3, of the alternating voltage in the network ACN.
  • the synchronous machine 1 has a field winding 101, and the field current is obtained from a controllable rectifier 102. Further, the machine has a tachometer generator 103, for example of pulse transducer type, which delivers a signal cm corresponding to the angular velocity of the machine.
  • the terminal voltage U m and current I m of the machine are sensed, the latter with the aid of a current transformer ITM, and are supplied to a correction unit 6.
  • the measured signals are filtered and a signal U m ⁇ is generated, the amplitude and phase position of which correspond to the induced air-gap voltage of the machine.
  • the unit 6 may be designed in the way described in the Swedish patent specification with publication number 415 425.
  • a superordinate control unit 9 calculates a value of the firing angle ⁇ of the machine-side converter which is optimized to the prevailing operating conditions.
  • the angle ⁇ is the distance in electrical degrees from the beginning of a commutation (by firing of the commutated thyristor) to the immediately following zero crossing of the commutating voltage.
  • the desired firing angle ⁇ is supplied to the control pulse devices 8A and 8B of the machine-side converter.
  • control pulse devices determine, on the basis of the signals U m ⁇ , ⁇ and ⁇ m , the times for firing of the commutated thyristors and deliver firing pulses, SP2A and SP2B, to these thyristors with such a phase position in relation to the air-gap voltage of the machine that the firing angle is given the desired value ⁇ .
  • phase windings are current-carrying. This can be viewed as if the control pulses to the valves of the machine-side converter 12 form a pattern which changes for each commutation but which is constant in between.
  • a change detector 7 is supplied with the control pulses SP2A and SP2B and senses changes in the above-mentioned control pulse pattern. Each change is an indication that a commutation is about to be started, and at each change a detection signal SPC is delivered. This signal activates the pulse number modulation according to the invention in a way which will be described in the following.
  • the change detector may, for example, be designed with a 12-bit memory which stores a digital number which delivers the control pulse pattern. Continuously and at regular intervals, the control pulse pattern given by the control pulses SP2A, SP2B is compared with the stored pattern, whereupon the former pattern is stored in the memory. The comparison may be made as a simple subtraction, and if the result differs from zero, a signal SPC is delivered.
  • the network-side converter 3 controls the current in the main circuit.
  • the alternating current I N to the bridge 3A is sensed with the aid of a current transformer ITN.
  • a measured value I' d is formed, which is proportional to the current I d and which is compared with a current reference I ref in a summator 132.
  • the difference ⁇ I is supplied to a current regulator 12 with PI characteristic.
  • the output signal of the regulator is supplied to a function generator 121 for linearization of the control circuit, the output signal of this generator being an arcuscosine function of the input signal and corresponding to the control angle ⁇ of the network-side converter.
  • This signal is supplied via a summator 122 to the summators 123A and 123B, the output signals ⁇ A and ⁇ B of which constitute the control angles of the two bridges 3A and 3B of the converter 3.
  • the latter signals are supplied to the control pulse devices 10A and 10B of the bridges.
  • the control pulses are supplied with the sensed line voltage U N .
  • the control pulse devices deliver control pulses SP3A and SP3B to the valves of the two bridges with such phase positions in relation to the line voltage that the desired values ⁇ A and ⁇ B of the control angles of the bridges are obtained.
  • FIG. 10 shows in more detail how the circuits for the current measurement are formed in the motor drive according to FIG. 1a.
  • the current transformers ITNa, ITNb and ITNc are each arranged in a phase lead on the ac side of the converter.
  • a measured direct current i' d is generated, the instantaneous value of which is proportional to the instantaneous value of the actual direct current id of the converter.
  • the measured current generates a measured voltage u' d which is also proportional to the converter current id.
  • the measured voltage controls a voltage-controlled oscillator VCO.
  • VCO voltage-controlled oscillator
  • This generates a pulse train in the form of a square signal, the frequency of which is proportional to the voltage of the input of the VCO circuit.
  • the square signal is supplied to the input of a means CR for counting up which has data outputs D0-D15.
  • the counter calculates pulses until the value of the outputs D0-D15 becomes FFFF, whereafter the counter is automatically reset and restarted.
  • the counter register is read.
  • the change of the counter contents during an interval is then proportional to the current Id.
  • a measured signal I' d may be formed, which is proportional to the mean value I d of the converter current during the measurement interval.
  • Control pulses are generated according to the principle shown in FIG. 9.
  • phase-position reference there is used the zero crossing of one of the phase voltages on the network side of the converter.
  • This zero crossing ZC is detected by a comparator and is marked on a time axis, T ZC .
  • This event also sets a memory circuit to one, ZC-flag.
  • T cycle T Z (n)-T z (n-1)
  • T cycle T Z (n)-T z (n-1)
  • T.sub. ⁇ ⁇ .T cycle /360°
  • T trig T Z +T.sub. ⁇ +k. T cycle /6"
  • P(NCPP) a memory circuit
  • T trig This time, that is, T trig , may be used to determine the starting time for the calculation of the next commutation and so on.
  • T trig When controlling a series converter (two series-connected 6-pulse converters), two control angles are used, ⁇ master and ⁇ slave . During 12-pulse operation, the values of these two control angles are identically alike.
  • k is incremented by a number which is greater than one.
  • a speed reference ⁇ ref is obtained from a reference value transducer 130, for example a potentiometer, or from a superordinate control system.
  • the speed reference is compared in a summator 131 with the speed signal ⁇ m obtained from the tachometer generator 103, and the difference is supplied to a speed regulator 13 with PI characteristic.
  • the output signal of this regulator constitutes the above-mentioned current reference I ref .
  • the sensed line voltage U N is rectified in a measurement rectifier 171, the output signal U N ' of which corresponds to the amplitude of the line voltage.
  • a multiplier 172 the sensed current I' d is multiplied by a quantity Z i which corresponds to the internal impedance of the network ACN including the impedance of the transformer 4.
  • the product ⁇ U N is added in a summator 173 to the signal U N ', and the resultant signal U di ⁇ is a measure of the open-circuit voltage of the network.
  • the signal is supplied to a selector circuit 17, the function of which will be described below.
  • the highest commutatable current I Cmax is continuously calculated. This depends on the calculated air-gap voltage U m ⁇ of the machine and the measured frequency ⁇ m of the machine. Further, it is dependent on the firing angle ⁇ of the machine-side converter. At the low speeds when the commutating capability may become insufficient, this angle is normally set at a constant maximum value, for example 52°, which is chosen taking into account the power factor of the motor, the reason being to obtain the highest possible commutating capability.
  • the other parameters which determine the commutating capability namely, the commutating resistance per phase R C and the commutating inductance per phase L C , are treated during the calculation as as constants and are determined from factual data of the main circuit--machine, converter, cables.
  • a commutation of the current from, for example, the thyristor TY4 to the thyristor TY6 in a bridge in the machine-side converter is started by firing the thyristor TY6.
  • the commutating voltage that is, the difference between the phase voltages connected to these thyristors, drives an increasing commutating current i k through the commutating circuit which consists of the two thyristors and the phase windings, connected thereto, of the machine.
  • the decommutated thyristor TY4 the resultant current i d -i k flows, and through the commutated thyristor TY6 the current i k flows.
  • i k has risen to the value i d the thyristor TY4 expires and the commutation is completed.
  • the resistance in the commutating circuit cannnot be neglected, but during the calculation both this resistance and the commutating inductance must be taken into consideration.
  • the commutating process takes a certain amount of time which corresponds to the so-called overlap angle ⁇ . This angle must not exceed a certain maximum value determined by the firing angle ⁇ in order for a commutation to succeed. This condition is
  • the reason for the different values at the two pulse numbers is that during 12-pulse operation, the commutating notches n the voltage are inductively coupled between the two three-phase systems.
  • the recovery time of the thyristor valves is typically 400 ⁇ s, and at the low machine frequencies occurring, the term ⁇ m t q primarily be omitted.
  • the selector circuit 17 is composed in the manner shown in FIG. 2.
  • a calculating circuit 1701 calculates the limiting currents for discontinuous operation at different pulse numbers: I 012 during 12-pulse operation and I 06 during 6-pulse operation. These limiting currents are dependent, in a known manner, on the constant data of the main circuit, primarily on the inductance of the smoothing inductor 5, on the pulse number of the network-side converter, and on the open-circuit voltage U v0 of the network ACN, here represented by its rectified equivalence U di ⁇ .
  • the current reference I ref is compared with I Cmax , I 012 and I 06 .
  • the circuit 1702 delivers an output signal if I Cmax ⁇ I ref
  • the circuit 1703 an output signal if I ref ⁇ I 012
  • the circuit 1704 an output signal if I ref ⁇ I 06 .
  • the output signals from the circuits 1702, 1703, 1704 are supplied to an OR circuit 1705 and to two AND circuits 1706 and 1707.
  • the output signals from these circuits are supplied, in turn, to a memory circuit 1801 via switching members 1708, 1709, 1800 activated by the activating signal SPC.
  • the OR circuit 1705 delivers an output signal if I Cmax >I ref and/or if I ref ⁇ I 012 .
  • the output signal of the circuit 1705 is forwarded to the memory circuit 1801, where it causes storage of a value corresponding to 12 in the pulse number PN.
  • the AND circuit 1706 delivers a signal if I Cmax ⁇ I ref and at the same time I ref ⁇ I 012 and I ref ⁇ I 06 .
  • the output signal of the circuit 1706 is forwarded to the memory circuit 1801, where it causes storage of a value corresponding to 6 of the pulse number PN.
  • the AND circuit 1707 delivers an output signal if I Cmax ⁇ I ref and at the same time I ref >I 06 .
  • the output signal of the circuit 1707 is forwarded to the memory circuit 1801, where it causes storage of a value corresponding to 3 of the pulse number PN.
  • the output signal PN from the selector circuit 17 thus continuously constitutes a measure of the desired pulse number with which the network-side converter is to operate during the next commutating process in order that the current in question shall be commutated with certainty. It is updated by the signal SPN at the beginning of each commutation.
  • the signal PN is supplied to a circuit 16, which, if PN ⁇ 12, causes switching of a signal corresponding to 15° to the summators 123a and 123B.
  • a lower pulse number thus means, for example, lower intervals between the up-grades of the current response.
  • the signal PN is therefore supplied also to the speed regulator 13 and the current regulator 12, for adaptation of the characteristic of the regulators (time constant and reinforcement) to the pulse number in question.
  • the top graph in FIG. 3a shows the commutating times during normal 12-pulse operation during one cycle of the line alternating voltage U N of the two bridges 3A and 3B in the network-side converter 3.
  • the commutating times are displaced 30° between the bridges 3A and 3B.
  • the combinations of figures given in conjunction with the commutating times designate that thyristor pair which is to carry current during the following 60° interval.
  • This ripple has the fundamental frequency 12 times the mains frequency. Its peak-to-peak value is I 012 and is substantially determined by the open-circuit voltage U di ⁇ of the network ACN, by the inductance of the intermediate-link inductor 5, and by the pulse number of the network-side converter.
  • the mean value of the intermediate-link current is assumed in the figure to be at the limiting current I 012 to discontinuous operation, that is, the minimum value of the current barely reaches down to zero during each commutation.
  • I 012 the intermediate-link current and hence the current through the thyristors of the machine-side converter will be zero 12 times per line alternating voltage cycle, and, therefore, no commutating problems arise.
  • FIG. 3b shows the same quantities during 6-pulse operation. Since the commutations in the bridge 3A have been retarded by 15° and in the bridge 3B advanced by 15°, they will become synchronous in the two bridges.
  • the network-side converter therefore operates in 6-pulse operation, and the frequency of the ripple will be half as high as during 12-pulse operation and the peak-to-peak value I 06 will be higher. Also in this case, the mean value of the intermediate-link current is assumed to lie at the limiting current--I 06 --between continuous and discontinuous operation.
  • FIG. 3c shows the same quantities during 3-pulse operation. Below the two graphs, showing the commutating times for the bridges, it is shown how the quantity ⁇ varies with the time of the oscillator 15.
  • the network-side converter operates in 3-pulse operation, and the frequency of the ripple will be one-fourth of the frequency during 12-pulse operation and a high peak-to-peak value I 03 of the ripple is obtained.
  • the mean value of the intermediate-link current is assumed to lie at the limiting current--I 03 --between continuous and discontinuous drive.
  • both converters are operating in normal 12-pulse operation if the current is lower than the maximum commutatable current I Cmax at the motor speed in question.
  • the machine-side converter is then commutated by the induced voltage of the machine.
  • the converters are operating in normal 12-pulse operation if the current is lower than the limiting current during 12-pulse operation I 012 . In this case, zero crossings of the current are obtained because of the ripple generated by the network-side converter, and during these zero crossings, all the conducting thyristor valves in the machine-side converter expire.
  • the machine-side converter is commutated by the air-gap voltage of the machine.
  • this voltage decreases, and the commutating capability is reduced, which is reflected by a decreasing value of the quantity I Cmax .
  • the network-side converter is switched to such a lower pulse number that the current, because of the ripple which increases greatly with decreasing pulse number, becomes discontinuous, whereby commutations in the machine-side converter can be made.
  • this makes it possible to handle high currents also at the lowest speed of the machine without any risk of commutating faults in the machine-side converter.
  • the lowest possible pulse number of the network-side converter is 3. If desired, still higher currents and/or still lower machine speeds may be handled by providing the system with a possibility of a further reduction of the pulse number.
  • the pulse number 2 may be obtained in the same way as the pulse number 3, that is, with the aid of an oscillating control angle.
  • 2-pulse operation of the network-side converter and a limiting current I 02 which is considerably higher than the limiting current during 3-pulse operation are obtained.
  • FIG. 4 illustrates this and shows the same quantities as FIG. 3c.
  • the largest pulse which can be realized without changing voltage arcs i.e. without commutation from one to another phase-to-phase voltage
  • the largest pulse which can be realized without changing voltage arcs is 210° long, which results in the pulse number 15/7.
  • Pulse numbers other than those mentioned above may also be realized, for example by the introduction of extra commutations and/or by omitting commutations in other ways than those described above.
  • FIG. 5 illustrates the function. The figure shows as functions of time and for an intermediate-link current I d :
  • the commutating current i k (t) grows to a value I Cmax which constitutes the commutating capability of the machine.
  • I Cmax which constitutes the commutating capability of the machine.
  • the figure is made while assuming that a reduction of the pulse number to 6 is insufficient and a reduction to the pulse number 3 is barely sufficient for the current in question to be able to be commutated.
  • the minimum value of the current i d (3) falls short of the mean value I d by the amount ⁇ I d . If the recovery time of the thyristors is not taken into consideration, the condition for commutation is
  • ⁇ I d depends on the open-circuit voltage of the network and on the pulse number in question.
  • the recovery time t q of the thyristors is suitably taken into consideration, and this is done by reducing ⁇ I d by an amount ⁇ I(t q ) so large (see the figure) that a zero-current interval of the duration t q is obtained.
  • the commutation condition will then be
  • the selector unit 17 in this case preferably consists of a processor adapted to carry out the necessary calculations and to investigate whether the commutation condition is fulfilled.
  • the processor can thereby be programmed to operate according to the flow chart in FIG. 6.
  • the processor is supplied with the signals shown in FIG. 2, where I ref represents the intermediate-link current Id, and is activated at the beginning of, or immediately before, each commutation in the machine-side converter by the signal SPC.
  • the processor operates with a parameter "i" which, for example, may assume the values 0, 1, 2, . . . whereby a possible value of an assumed value PN' of the pulse number of the network-side converter corresponds to each value of "i", and where PN' depends on the variable "i" according to a prestored table, for example
  • the quantities ⁇ I d and ⁇ I(t q ) are calculated.
  • the process is repeated with successively lower pulse numbers until the commutation condition I ref ⁇ I k is fulfilled.
  • the pulse number modulation is activated in connection with a commutation of the machine-side converter being ordered. Alternatively, the activation cannot be made until the commutating current has grown a certain distance.
  • the overlap angle ⁇ is known or may be calculated by the calculating circuit 18. It may be suitable to activate the pulse number modulation, that is, where necessary, reduce the pulse number of the network-side converter so far that the commutation of the machine-side converter is ensured, a time corresponding to the overlap angle after the start of the commutation, or somewhat earlier.
  • the pulse-number modulation is not activated the whole time during operation in the low-speed range, where the commutating capability of the machine is reduced.
  • the maximum value of the overlap angle corresponds to a time (83 ms at 1 Hz) which is considerably greater than the time of a "current bubble" (i.e. the time between two commutations) of the network-side converter (during, e.g. 3-pulse operation and 50 Hz power frequency, this time is 6.6 ms).
  • a "current bubble” i.e. the time between two commutations
  • the network-side converter during, e.g. 3-pulse operation and 50 Hz power frequency, this time is 6.6 ms.
  • the network-side converter operates in stationary 12-pulse operation and the intermediate-link current is i d (12).
  • the first commutation is made in 3-pulse operation, and the time is so chosen that the first peak value of the intermediate-link current i d ( 3 ) in 3-pulse operation will have the same value as during stationary 3-pulse operation.
  • the following commutations in 3-pulse operation are made at t4 and t5.
  • t2 such a commutation is made that a change to 6-pulse operation occurs, and during the interval t3-t6 the converter is operating in stationary 6-pulse operation.
  • t7 By a commutation at t7, a return to 12-pulse operation is made.
  • the commutating times t2 and t7 are so chosen that a change is made directly to stationary 6-pulse operation at t2 and to stationary 12-pulse operation at t7.
  • the activation and the deactivation, respectively, of the pulse-number modulation are preferably performed in such a way that the mean value of the intermediate-link current is not at all--or only insignificantly--influenced.
  • the current measurement is therefore suitably synchronized with the commutations of the network-side converter.
  • the current is measured as a mean value between each pair of two consecutive commutations of the network-side converter.
  • the measurement time ⁇ is thus 1.7 ms during 12-pulse operation, 3.3 ms during 6-pulse operation and so on.
  • the current mean value should be maintained constant or practically constant.
  • the increased ripple current which is caused by the reduction of the pulse number must therefore have a mean value which corresponds to the mean value of the natural ripple current of the converter.
  • this mean value during 6-pulse operation and during 12-pulse operation is, with a very good approximation, 2/3 of the peak value of the ripple current.
  • this approximation is deteriorated to a certain extent.
  • the dashed voltage-time area ⁇ shown in FIG. 8 is added.
  • the intermediate-link voltage shall be reduced by the corresponding voltage-time area.
  • the voltage-time area ⁇ thus corresponds to an increase of the peak value of the intermediate-link current from I d (12) to I d (6). This current increase
  • ⁇ 012 is the stationary lead time during 12-pulse operation, that is, 1/12 of the period of the network.
  • ⁇ 06 are ⁇ 012 are those values of the voltage-time area ⁇ which apply during 6-pulse operation and during 12-pulse operation, respectively.
  • a correction for the deviation of the sine wave from the straight line can suitably be introduced in the manner described in the article by Torok, Hibner mentioned above.
  • the current is measured as a mean value over the interval ⁇ 126 in FIG. 8, and if the advance of the commutation is determined according to the above, a measured value is obtained with a negligible deviation relative to the measured values obtained during the preceding interval ⁇ 012 and during the subsequent interval ⁇ 06 , respectively. This means that the current regulator does not notice the change made in the pulse number (and nor does the speed regulator.
  • a system according to the invention utilizes a natural current ripple, at a reduced pulse number of the network-side converter, in order to distort the current through the machine-side converter such that the commutating current of the machine will exceed the instantaneous value of the distorted current, during intervals when this instantaneous value is lowest, and where the duration of these intervals exceeds the recovery time of the thyristors.
  • the current control system maintains the mean value of the intermediate-link current at the desired value independently of changes in the pulse number, and this also while a commutation process is in progress in the machine-side converter. Contrary to what is the case during intermediate-link discontinuous current operation, no loss of current-time area during each machine commutation is obtained with the system according to the invention.
  • the current mean value during each interval between two commutations in the network-side converter may be maintained constant with a high accuracy.
  • Such low-frequency disturbances in the air-gap moment which are caused by the fact that only two phases out of three carry current periodically, of course still remain and may excite the harmful mechanical natural oscillations mentioned in the introductory part of the description.
  • the torque control does not perceive the disturbance since the current measurement does not do so, and by a suitable synchronization, the speed measurement as well as the speed control may be rendered insensitive to the forced disturbance, that is, the pulse-number modulation of the current.
  • the forced disturbance that is, the pulse-number modulation of the current.
  • a motor drive of the type to which this application is related generates disturbances in the air-gap moment, the frequency f k of which is equal to the commutating frequency of the machine-side converter.
  • such a situation may be avoided by starting an oscillation of the commutating times of the machine-side converter, when the speed of the motor drive approaches a resonance frequency (e.g. 0,8 ⁇ f r ⁇ f m ⁇ 1,2 ⁇ f r ). At a constant speed and firing angle, these times are normally equidistant at intervals of 30°.
  • the time of the commutation of the machine-side converter is determined by the time at which the modulated current receives its minimum value. This time may be changed, and thus the corresponding control angle, without jeopardizing the commutation of the current.
  • the ripple in the motor current has a high frequency, for example 300 Hz during 6-pulse operation and 150 Hz during 3-pulse operation.
  • the mechanical system operates for these frequencies as a higher-order low-pass filter and effectively damps out these high frequencies. Torque pulsations transferred to the driven object therefore become unnoticeable and completely harmless.
  • An additional important advantage with the system according to the invention is that it makes possible a soft and, in principle, unnoticeable transition between on the one hand the lower speed range, where the machine-side converter needs commutation aid, and on the other hand the higher speed range where the machine has full commutating capability.
  • a synchronous motor drive according to the invention may be designed in a large number of alternative ways. For example, it is thus possible and may be practically suitable to design both the network-side converter and the machine-side converter with other natural pulse numbers than that described above (12). Primarily, it would be a question of designing one of the converters or both the converters with the natural pulse number 6. If the machine-side converter is designed for the natural pulse number 6, it is, of course, necessary to design the synchronous machine with a single three-phase winding instead of the twelve-pulse winding described above. According to one of the many possible alternatives, the synchronous machine may be a 12-pulse machine with two three-phase winding systems in the manner described above with reference to FIG.
  • each winding system has a separate intermediate-link converter, each one with, for example, a 6-pulse machine-side converter, a separate dc intermediate link and, for example, a 6-pulse network-side converter.
  • a synchronous motor drive according to the invention may be supplemented with means known per se for control of the current in such a way that such torque pulsations, which are caused by variations in the surrounded flux, are reduced or eliminated.

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Control Of Ac Motors In General (AREA)
  • Inverter Devices (AREA)
  • Control Of Multiple Motors (AREA)
  • Control Of Electric Motors In General (AREA)
  • Control Of Motors That Do Not Use Commutators (AREA)
  • Protection Of Generators And Motors (AREA)
  • Synchronous Machinery (AREA)
  • Seal Device For Vehicle (AREA)
US08/750,086 1994-07-01 1995-06-29 Load-commutated synchronous motor drive Expired - Fee Related US5825152A (en)

Applications Claiming Priority (3)

Application Number Priority Date Filing Date Title
SE9402326A SE503106C2 (sv) 1994-07-01 1994-07-01 Lastkommuterad synkronmotordrift
SE9402326 1994-07-01
PCT/SE1995/000807 WO1996001523A1 (en) 1994-07-01 1995-06-29 Load-commutated synchronous motor drive

Publications (1)

Publication Number Publication Date
US5825152A true US5825152A (en) 1998-10-20

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US08/750,086 Expired - Fee Related US5825152A (en) 1994-07-01 1995-06-29 Load-commutated synchronous motor drive

Country Status (11)

Country Link
US (1) US5825152A (sv)
EP (1) EP0769221B1 (sv)
JP (1) JPH10502240A (sv)
CN (1) CN1050470C (sv)
AT (1) ATE179557T1 (sv)
BR (1) BR9508197A (sv)
DE (1) DE69509391T2 (sv)
FI (1) FI965283A0 (sv)
PL (1) PL317899A1 (sv)
SE (1) SE503106C2 (sv)
WO (1) WO1996001523A1 (sv)

Cited By (10)

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US6567282B1 (en) * 2001-10-25 2003-05-20 Hitachi, Ltd. Apparatus and method of sensorless control for synchronous generator
US20070132424A1 (en) * 2005-12-08 2007-06-14 Sanyo Electric Co., Ltd. Motor driving control device
EP1974433A1 (en) * 2006-01-20 2008-10-01 ABB Technology Ltd A converter
CN101939902A (zh) * 2008-02-06 2011-01-05 西门子公司 转换器
US8169172B2 (en) 2010-05-03 2012-05-01 Hamilton Sundstrand Corporation Synchronous disturbance suppression in a variable speed motor drive
US20150097502A1 (en) * 2012-04-16 2015-04-09 Jan Wiik Method For Estimating Motor Parameter In A Load Commutated Inverter Arrangement, And A Load Commutated Inverter Arrangement Therefor
WO2018091682A1 (en) 2016-11-18 2018-05-24 Abb Schweiz Ag Switching an electrical voltage source converter
US10536104B2 (en) * 2015-02-25 2020-01-14 Hitachi Mitsubishi Hydro Corporation Variable speed generator-motor apparatus and variable speed generator-motor system
US20220038036A1 (en) * 2018-09-26 2022-02-03 Siemens Aktiengesellschaft METHOD FOR CONTROLLING THE SPEED OF A THREE-PHASE PERMANENT MAGNET MACHINE HAVING A SOFT STARTER BY MEANS OF A CONTROLLER CASCADE, AND THREE-PHASE MACHINE (As Amended)
US20220069583A1 (en) * 2020-09-02 2022-03-03 Siemens Energy Global GmbH & Co. KG Assembly and method for stabilizing an ac voltage grid

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GB0322806D0 (en) 2003-09-30 2003-10-29 Lifeforce Group Plc Cell bank for contingent autologous leukocyte transplantation

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GB1306193A (sv) * 1970-05-12 1973-02-07
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Cited By (21)

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Publication number Priority date Publication date Assignee Title
US6567282B1 (en) * 2001-10-25 2003-05-20 Hitachi, Ltd. Apparatus and method of sensorless control for synchronous generator
US20070132424A1 (en) * 2005-12-08 2007-06-14 Sanyo Electric Co., Ltd. Motor driving control device
US7443130B2 (en) * 2005-12-08 2008-10-28 Sanyo Electric Co., Ltd. Motor driving control device
EP1974433A1 (en) * 2006-01-20 2008-10-01 ABB Technology Ltd A converter
EP1974433A4 (en) * 2006-01-20 2013-06-19 Abb Technology Ltd CONVERTER
CN101939902A (zh) * 2008-02-06 2011-01-05 西门子公司 转换器
US8169172B2 (en) 2010-05-03 2012-05-01 Hamilton Sundstrand Corporation Synchronous disturbance suppression in a variable speed motor drive
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US20150097502A1 (en) * 2012-04-16 2015-04-09 Jan Wiik Method For Estimating Motor Parameter In A Load Commutated Inverter Arrangement, And A Load Commutated Inverter Arrangement Therefor
US9906173B2 (en) * 2012-04-16 2018-02-27 Abb Schweiz Ag Method for estimating motor parameter in a load commutated inverter arrangement, and a load commutated inverter arrangement therefor
US10536104B2 (en) * 2015-02-25 2020-01-14 Hitachi Mitsubishi Hydro Corporation Variable speed generator-motor apparatus and variable speed generator-motor system
US10784808B2 (en) * 2015-02-25 2020-09-22 Hitachi Mitsubishi Hydro Corporation Variable speed generator-motor apparatus and variable speed generator-motor system
CN109964399A (zh) * 2016-11-18 2019-07-02 Abb瑞士股份有限公司 开关电压源转换器
US20190273446A1 (en) * 2016-11-18 2019-09-05 Abb Schweiz Ag Switching an electrical voltage source converter
WO2018091682A1 (en) 2016-11-18 2018-05-24 Abb Schweiz Ag Switching an electrical voltage source converter
US10938321B2 (en) * 2016-11-18 2021-03-02 Abb Schweiz Ag Switching an electrical voltage source converter
CN109964399B (zh) * 2016-11-18 2023-06-27 Abb瑞士股份有限公司 开关电压源转换器
US20220038036A1 (en) * 2018-09-26 2022-02-03 Siemens Aktiengesellschaft METHOD FOR CONTROLLING THE SPEED OF A THREE-PHASE PERMANENT MAGNET MACHINE HAVING A SOFT STARTER BY MEANS OF A CONTROLLER CASCADE, AND THREE-PHASE MACHINE (As Amended)
US11637514B2 (en) * 2018-09-26 2023-04-25 Siemens Aktiengesellschaft Method for controlling the speed of a three-phase permanent magnet machine having a soft starter by means of a controller cascade, and three-phase machine
US20220069583A1 (en) * 2020-09-02 2022-03-03 Siemens Energy Global GmbH & Co. KG Assembly and method for stabilizing an ac voltage grid
US11817709B2 (en) * 2020-09-02 2023-11-14 Siemens Energy Global GmbH & Co. KG Method for stabilizing an AC voltage grid

Also Published As

Publication number Publication date
SE503106C2 (sv) 1996-03-25
PL317899A1 (en) 1997-04-28
JPH10502240A (ja) 1998-02-24
BR9508197A (pt) 1998-07-14
SE9402326D0 (sv) 1994-07-01
CN1152975A (zh) 1997-06-25
EP0769221B1 (en) 1999-04-28
EP0769221A1 (en) 1997-04-23
DE69509391D1 (de) 1999-06-02
DE69509391T2 (de) 1999-10-28
ATE179557T1 (de) 1999-05-15
SE9402326L (sv) 1996-01-02
CN1050470C (zh) 2000-03-15
WO1996001523A1 (en) 1996-01-18
FI965283A (sv) 1996-12-31
FI965283A0 (sv) 1996-12-31

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