TW202001864A - Gate driving apparatus - Google Patents
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本發明是有關於一種閘極驅動裝置,且特別是有關於一種顯示裝置的閘極驅動裝置。The invention relates to a gate driving device, and in particular to a gate driving device of a display device.
近年來有許多產品將顯示器驅動電路中的閘極驅動電路(Gate driver)整合於玻璃上,即為陣列上閘極驅動(Gate-Driver-on-Array, GOA)電路。而所述陣列上閘極驅動電路具有諸多優勢,其能夠降低顯示面板的邊框的寬度,以達到窄邊框的效果,進而有效地降低顯示器的內部電路的設計面積。In recent years, many products have integrated the gate driver circuit (Gate driver) in the display driver circuit on the glass, which is the gate-driver-on-array (GOA) circuit. The gate drive circuit on the array has many advantages. It can reduce the width of the frame of the display panel to achieve the effect of a narrow frame, thereby effectively reducing the design area of the internal circuit of the display.
在顯示裝置中,由於顯示面板所呈現的顯示畫面容易受到畫素電路中的驅動電晶體的導通電壓影響,導致顯示畫面的品質降低。因此,閘極驅動電路需要在補償階段時使同一列畫素開關同時被導通或被斷開,以對所述驅動電晶體進行補償動作。接著,閘極驅動電路需要在資料寫入階段時逐列導通所述畫素開關,以將畫入電壓(或畫素資料)寫入至對應的畫素電路中。In the display device, since the display screen presented by the display panel is easily affected by the turn-on voltage of the driving transistor in the pixel circuit, the quality of the display screen is reduced. Therefore, the gate driving circuit needs to make the pixel switches of the same column be turned on or off at the same time in the compensation stage to perform compensation operation on the driving transistor. Next, the gate drive circuit needs to turn on the pixel switches row by row during the data writing stage to write the drawing voltage (or pixel data) to the corresponding pixel circuit.
換言之,如何在閘極驅動裝置操作於補償階段時,能夠有效地產生一致的閘極驅動信號,並且在資料寫入階段時,能夠依序地產生所述閘極驅動信號,藉以提升閘極驅動裝置的效能,將是本領域相關技術人員重要的課題。In other words, how to effectively generate a consistent gate drive signal when the gate drive device is operating in the compensation stage, and to sequentially generate the gate drive signals during the data writing stage to improve gate drive The performance of the device will be an important issue for those skilled in the art.
本發明提供一種閘極驅動裝置,可以在補償階段時使各個閘極驅動信號同時被致能,並且在寫入階段時使各個閘極驅動信號依序被致能,藉以提升閘極驅動裝置的效能。The invention provides a gate drive device, which can enable each gate drive signal at the same time in the compensation phase, and enable each gate drive signal in sequence during the write phase, thereby enhancing the gate drive device efficacy.
本發明的閘極驅動裝置包括多個移位暫存電路。多個移位暫存電路相互串聯耦接,分別產生多個閘極驅動信號,其中第N級的移位暫存電路包括輸出級電路、補償電路以及第一至第四電壓調整器。輸出級電路具有第一控制端以及第二控制端以分別接收第一控制信號以及第二控制信號,依據第一控制信號以及第二控制信號以提供閘極低電壓或閘極高電壓對輸出端充電以產生第N級閘極驅動信號。補償電路耦接至第一控制端,其中補償電路包括電容以及第一電晶體。電容耦接於第一控制端以及第一節點之間。第一電晶體的第一端接收後級閘極驅動信號,第一電晶體的第二端耦接至第一節點,第一電晶體的控制端接收第一控制信號。第一電壓調整器耦接至第一控制端,依據第一模式選擇信號以及第二模式選擇信號以提供閘極低電壓或閘極高電壓以調整第一控制信號。第二電壓調整器耦接至第一控制端,依據切換信號以及反向時脈信號以提供前級閘極驅動信號或起始脈波信號以調整第一控制信號。第三電壓調整器耦接於第一控制端以及第二控制端之間,依據第二模式選擇信號以及第一控制信號以提供閘極低電壓或閘極高電壓以調整第二控制信號。第四電壓調整器耦接至第二控制端,依據反向時脈信號以調整第二控制信號。The gate driving device of the present invention includes a plurality of shift temporary storage circuits. A plurality of shift register circuits are coupled in series with each other to generate a plurality of gate drive signals, wherein the shift register circuit of the Nth stage includes an output stage circuit, a compensation circuit, and first to fourth voltage regulators. The output stage circuit has a first control terminal and a second control terminal to receive the first control signal and the second control signal, respectively, according to the first control signal and the second control signal to provide the gate low voltage or the gate high voltage to the output terminal Charge to generate the Nth gate drive signal. The compensation circuit is coupled to the first control terminal, wherein the compensation circuit includes a capacitor and a first transistor. The capacitor is coupled between the first control terminal and the first node. The first terminal of the first transistor receives the latter-stage gate driving signal, the second terminal of the first transistor is coupled to the first node, and the control terminal of the first transistor receives the first control signal. The first voltage regulator is coupled to the first control terminal, and provides a gate low voltage or a gate high voltage according to the first mode selection signal and the second mode selection signal to adjust the first control signal. The second voltage regulator is coupled to the first control terminal, and provides a previous-stage gate driving signal or a starting pulse signal according to the switching signal and the reverse clock signal to adjust the first control signal. The third voltage regulator is coupled between the first control terminal and the second control terminal, and provides the gate low voltage or the gate high voltage according to the second mode selection signal and the first control signal to adjust the second control signal. The fourth voltage regulator is coupled to the second control terminal and adjusts the second control signal according to the reverse clock signal.
基於上述,本發明的閘極驅動裝置的移位暫存電路可以在補償階段時,使輸出級電路所產生的第N級閘極驅動信號與後級閘極驅動信號進行同步輸出。並且在寫入階段時,使輸出級電路所產生的第N級閘極驅動信號與後級閘極驅動信號依序的被輸出,藉以提升閘極驅動裝置的效能。Based on the above, the shift temporary storage circuit of the gate drive device of the present invention can synchronize the output of the N-th gate drive signal generated by the output stage circuit and the subsequent-stage gate drive signal during the compensation stage. In the writing stage, the N-th gate driving signal and the subsequent-stage gate driving signal generated by the output stage circuit are output in order, thereby improving the performance of the gate driving device.
為讓本發明的上述特徵和優點能更明顯易懂,下文特舉實施例,並配合所附圖式作詳細說明如下。In order to make the above-mentioned features and advantages of the present invention more obvious and understandable, the embodiments are specifically described below in conjunction with the accompanying drawings for detailed description as follows.
在本案說明書全文(包括申請專利範圍)中所使用的「耦接(或連接)」一詞可指任何直接或間接的連接手段。舉例而言,若文中描述第一裝置耦接(或連接)於第二裝置,則應該被解釋成該第一裝置可以直接連接於該第二裝置,或者該第一裝置可以透過其他裝置或某種連接手段而間接地連接至該第二裝置。另外,凡可能之處,在圖式及實施方式中使用相同標號的元件/構件/步驟代表相同或類似部分。不同實施例中使用相同標號或使用相同用語的元件/構件/步驟可以相互參照相關說明。The term "coupling (or connection)" used in the entire specification of this case (including the scope of patent application) may refer to any direct or indirect connection means. For example, if it is described that the first device is coupled (or connected) to the second device, it should be interpreted that the first device can be directly connected to the second device, or the first device can be connected to another device or a certain device. Connection means indirectly connected to the second device. In addition, wherever possible, elements/components/steps using the same reference numbers in the drawings and embodiments represent the same or similar parts. Elements/components/steps that use the same reference numbers or use the same terminology in different embodiments may refer to related descriptions with each other.
圖1是依照本發明一實施例的第N級的移位暫存電路的電路圖。本發明實施例的閘極驅動裝置包括多個移位暫存電路,並且,這些移位暫存電路彼此之間相互串聯耦接,以分別產生多個閘極驅動信號。其中,圖1的移位暫存電路100即表示所述閘極驅動裝置的第N級的移位暫存電路,並且上述的N為正整數。FIG. 1 is a circuit diagram of an Nth-stage shift register circuit according to an embodiment of the invention. The gate driving device of the embodiment of the present invention includes a plurality of shift register circuits, and these shift register circuits are coupled in series with each other to generate a plurality of gate drive signals, respectively. Wherein, the
請參照圖1,在本實施例中,移位暫存電路100包括輸出級電路110、補償電路120以及電壓調整器130~160。其中,輸出級電路110包括電晶體M1~M2。電晶體M1的第一端接收閘極低電壓VGL,電晶體M1的第二端耦接至輸出端OUT,電晶體M1的控制端接收控制信號CS1。電晶體M2的第一端耦接至輸出端OUT,電晶體M2的第二端接收閘極高電壓VGH,電晶體M2的控制端接收控制信號CS2。Referring to FIG. 1, in this embodiment, the
具體而言,本實施例的輸出級電路110可以透過控制端CT1以及控制端CT2來分別接收控制信號CS1以及控制信號CS2。並且,輸出級電路110可以依據控制信號CS1以及控制信號CS2來使閘極低電壓VGL或閘極高電壓VGH對輸出端OUT進行充電動作,促使輸出級電路110產生第N級閘極驅動信號G[N]至後端的畫素電路。Specifically, the
接著,補償電路120耦接至控制端CT1。補償電路120包括電容C1以及電晶體M3。其中,電容C1耦接於控制端CT1以及節點P1之間。並且,電晶體M3的第一端接收後級閘極驅動信號G[N+1],電晶體M3的第二端耦接至節點P1,電晶體M3的控制端接收控制信號CS1。Next, the
另一方面,電壓調整器130耦接至控制端CT1。電壓調整器130包括電晶體M4~M6。其中,電晶體M4的第一端接收閘極低電壓VGL,電晶體M4的第二端耦接至控制端CT1,電晶體M4的控制端接收模式選擇信號SS1。電晶體M5的第一端接收閘極高電壓VGH,電晶體M5的控制端接收模式選擇信號SS2。電晶體M6的第一端耦接至電晶體M5的第二端,電晶體M6的第二端耦接至控制端CT1,電晶體M6的控制端接收模式選擇信號SS2。具體而言,本實施例的電壓調整器130可以依據模式選擇信號SS1以及模式選擇信號SS2的狀態來決定將閘極低電壓VGL或閘極高電壓VGH提供至控制端CT1,藉以使電壓調整器130可以透過閘極低電壓VGL或閘極高電壓VGH來調整控制信號CS1。On the other hand, the
接著,電壓調整器140耦接至控制端CT1。電壓調整器140包括電晶體M7~M8。其中,電晶體M7的第一端接收前級閘極驅動信號G[N-1]或起始脈波信號ST,電晶體M7的控制端接收反向時脈信號XCLK。電晶體M8的第一端耦接至電晶體M7的第二端,電晶體M8的第二端耦接至控制端CT1,電晶體M8的控制端接收切換信號CHA。具體來說,本實施例的電壓調整器140可以依據切換信號CHA以及反向時脈信號XCLK來決定將前級閘極驅動信號G[N-1]或起始脈波信號ST提供至控制端CT1,藉以使電壓調整器140可以透過前級閘極驅動信號G[N-1]或起始脈波信號ST來調整控制信號CS1。Next, the voltage regulator 140 is coupled to the control terminal CT1. The voltage regulator 140 includes transistors M7-M8. Among them, the first end of the transistor M7 receives the previous-stage gate drive signal G[N-1] or the start pulse signal ST, and the control end of the transistor M7 receives the reverse clock signal XCLK. The first terminal of the transistor M8 is coupled to the second terminal of the transistor M7, the second terminal of the transistor M8 is coupled to the control terminal CT1, and the control terminal of the transistor M8 receives the switching signal CHA. Specifically, the voltage regulator 140 of this embodiment may determine to provide the previous-stage gate driving signal G[N-1] or the start pulse signal ST to the control terminal according to the switching signal CHA and the reverse clock signal XCLK CT1, so that the voltage regulator 140 can adjust the control signal CS1 through the previous-stage gate driving signal G[N-1] or the start pulse signal ST.
特別一提的,在本實施例中,當移位暫存電路100操作於補償階段時,電壓調整器140可以依據具有高電壓準位的切換信號CHA來使電晶體M8被斷開。藉此,在補償階段中,輸出級電路110所輸出的閘極驅動信號G[N]的輸出狀態將可不受前級閘極驅動信號G[N-1]的輸出狀態而被影響。In particular, in this embodiment, when the
另一方面,電壓調整器150耦接於控制端CT1以及控制端CT2之間。電壓調整器150包括電晶體M9~M12。其中,電晶體M9的第一端接收閘極低電壓VGL,電晶體M9的第二端耦接至控制端CT2,電晶體M9的控制端接收模式選擇信號SS2。電晶體M10的第一端耦接至控制端CT2,電晶體M10的第二端接收閘極高電壓VGH,電晶體M10的控制端接收控制信號CS1。電晶體M11的第一端耦接至控制端CT1,電晶體M11的控制端耦接至控制端CT2。電晶體M12的第一端耦接至電晶體M11的第二端,電晶體M12的第二端接收閘極高電壓VGH,電晶體M12的控制端耦接至控制端CT2。具體來說,本實施例的電壓調整器150可以依據模式選擇信號SS2以及控制信號CS1來決定將閘極低電壓VGL或閘極高電壓VGH提供至控制端CT2,藉以使電壓調整器150可透過閘極低電壓VGL或閘極高電壓VGH來調整控制信號CS2。On the other hand, the
接著,電壓調整器160耦接至控制端CT2。電壓調整器160包括電晶體M13~M14。其中,電晶體M13的第一端以及控制端共同接收反向時脈信號XCLK。電晶體M14的第一端耦接至電晶體M13的第二端,電晶體M14的第二端耦接至控制端CT2,電晶體M14的控制端接收反向時脈信號XCLK。具體來說,本實施例的電壓調整器160可以依據反向時脈信號XCLK來調整控制信號CS2。值得一提的是,本實施例的電晶體M13~M14可以依據二極體組態(Diode Connection)的連接方式來形成一個二極體。其中,所述二極體的陰極(亦即電晶體M13的第一端)接收反向時脈信號XCLK,所述二極體的陽極(亦即電晶體M14的第二端)耦接至控制端CT2。順帶一提的是,本實施例的電晶體M1~M14是以P型電晶體為例,但本發明實施例不以此為限。Next, the
圖2是依照本發明一實施例的第N級的移位暫存電路的波形示意圖。請參照圖2,在本實施例中,移位暫存電路100的一個畫素期間TFR可以區分為補償階段TC、寫入階段TR以及電壓保持階段TVH,並且補償階段TC、寫入階段TR以及電壓保持階段TVH彼此不相互重疊。其中,寫入階段TR致能於補償階段TC之後,電壓保持階段TVH致能於寫入階段TR之後。FIG. 2 is a waveform diagram of the shift register circuit of the Nth stage according to an embodiment of the invention. Referring to FIG. 2, in this embodiment, one pixel period TFR of the
圖3是依照本發明一實施例的第N級的移位暫存電路在補償階段的第一子階段的電路示意圖。請同時參照圖2以及圖3,具體來說,當移位暫存電路100操作於補償階段TC的第一子階段TC_1時,外接於移位暫存電路100的時脈產生器(未繪製)可以提供具有高電壓準位的時脈信號CLK以及具有低電壓準位的反向時脈信號XCLK至移位暫存電路100。另外,移位暫存電路100可以設定模式選擇信號SS1為低電壓準位狀態,且設定模式選擇信號SS2為高電壓準位狀態。FIG. 3 is a circuit schematic diagram of the first sub-stage of the Nth-stage shift register circuit in the compensation stage according to an embodiment of the invention. Please refer to FIG. 2 and FIG. 3 at the same time. Specifically, when the
詳細來說,電壓調整器130可以依據模式選擇信號SS1而將閘極低電壓VGL傳送至控制端CT1,藉以拉低控制信號CS1的電壓準位。並且,電壓調整器120可依據被拉低的控制信號CS1而被導通。在此同時,移位暫存電路100可以設定切換信號CHA為高電壓準位狀態,以使電晶體M8可以被斷開。在此情況下,電壓調整器140將無法傳送前級閘極驅動信號G[N-1]或起始脈波信號ST至控制端CT1。藉此,本實施例可以有效地隔絕前級閘極驅動信號G[N-1]或起始脈波信號ST與控制信號CS1之間的影響。In detail, the
另一方面,在第一子階段TC_1中,電壓調整器160可以依據反向時脈信號XCLK而被導通,並對控制信號CS2進行充電動作。接著,電壓調整器150可以依據被拉低的控制信號CS1來將閘極高電壓VGH傳送至控制端CT2,進而將控制信號CS2拉高至閘極高電壓VGH的電壓準位。On the other hand, in the first sub-stage TC_1, the
換言之,在本實施例中,當移位暫存電路100操作於第一子階段TC_1時,輸出級電路110可以依據被拉低的控制信號CS1來提供閘極低電壓VGL以對輸出端OUT進行充電動作,並使輸出級電路110可以透過輸出端OUT來產生具有閘極低電壓VGL的電壓準位的第N級閘極驅動信號G[N]。In other words, in this embodiment, when the
圖4是依照本發明一實施例的第N級的移位暫存電路在補償階段的第二子階段的電路示意圖。請同時參照圖2以及圖4,具體來說,當移位暫存電路100操作於第二子階段TC_2時,移位暫存電路100可以設定模式選擇信號SS1以及模式選擇信號SS2皆為高電壓準位狀態。並且,外接的時脈產生器(未繪製)可以提供以週期性轉態的時脈信號CLK以及反向時脈信號XCLK至移位暫存電路100。FIG. 4 is a circuit schematic diagram of the second sub-stage of the N-stage shift register circuit in the compensation stage according to an embodiment of the invention. Please refer to FIGS. 2 and 4 at the same time. Specifically, when the
詳細來說,電壓調整器130可以依據模式選擇信號SS1以及模式選擇信號SS2而被斷開,並且電壓調整器140可以依據切換信號CHA而持續被斷開。接著,補償電路120可以依據被拉低的控制信號CS1而被導通。值得一提的是,由於此時後級閘極驅動信號G[N+1]操作在閘極低電壓VGL的電壓準位上,因此,節點P1上的電壓值可以依據後級閘極驅動信號G[N+1]而同步地被下拉至閘極低電壓VGL的電壓準位。如此一來,補償電路120可以藉由電容C1的耦合效應,以使控制信號CS1的電壓準位被調整為閘極低電壓VGL的電壓值與一電壓值V1的總和。需注意到的是,所述電壓值V1可以表示為電晶體M4的導通電壓|VTH4|與經由耦合效應後的一偏移值△V之間的電壓差值。亦即,此時的控制信號CS1的電壓準位為VGL+V1=VGL+|VTH4|-△V。In detail, the
另一方面,電壓調整器160依據反向時脈信號XCLK而週期性的被斷開。並且,電壓調整器150可以依據被拉低的控制信號CS1而提供閘極高電壓VGH至控制端CT2,以使控制信號CS2的電壓準位可以維持於閘極高電壓VGH的電壓值。On the other hand, the
換言之,在本實施例中,當移位暫存電路100操作於第二子階段TC_2時,輸出級電路110可以依據被拉低的控制信號CS1來提供閘極低電壓VGL以對輸出端OUT進行充電動作,並使輸出級電路110可以透過輸出端OUT來產生具有閘極低電壓VGL的電壓準位的第N級閘極驅動信號G[N]。In other words, in the present embodiment, when the
圖5是依照本發明一實施例的第N級的移位暫存電路在補償階段的第三子階段的電路示意圖。請同時參照圖2以及圖5,具體來說,當移位暫存電路100操作於補償階段TC的第三子階段TC_3時,移位暫存電路100可以設定模式選擇信號SS1持續維持於高電壓準位狀態,並且設定模式選擇信號SS2為低電壓準位狀態。此外,外接的時脈產生器(未繪製)可以提供具有高電壓準位的時脈信號CLK以及具有低電壓準位的反向時脈信號XCLK。FIG. 5 is a circuit schematic diagram of the third sub-stage of the shift register circuit of the Nth stage in the compensation stage according to an embodiment of the invention. Please refer to FIGS. 2 and 5 at the same time. Specifically, when the
詳細來說,電壓調整器130可以依據模式選擇信號SS2來提供閘極高電壓VGH至控制端CT1,進而使控制信號CS1的電壓準位可以被上拉至閘極高電壓VGH的電壓值。在此同時,電壓調整器120可依據被上拉的控制信號CS1而被斷開。並且,電壓調整器140依據切換信號CHA而持續的被斷開。In detail, the
另一方面,電壓調整器160可以依據反向時脈信號XCLK而被導通,以對控制信號CS2進行充電動作。接著,電壓調整器150可以依據模式選擇信號SS2來提供閘極低電壓VGL至控制端CT2,以使控制信號CS2的電壓準位被調整為閘極低電壓VGL的電壓值與一電壓值V2的總和。需注意到的是,所述電壓值V2可以表示為電晶體M9的導通電壓|VTH9|。亦即,此時的控制信號CS2的電壓準位為VGL+ V2=VGL+|VTH9|。On the other hand, the
換言之,在本實施例中,當移位暫存電路100操作於第三子階段TC_3時,輸出級電路110可以依據被拉低的控制信號CS2來提供閘極高電壓VGH以對輸出端OUT進行充電動作,並使輸出級電路110可以透過輸出端OUT來產生具有閘極高電壓VGH的電壓準位的第N級閘極驅動信號G[N]。In other words, in the present embodiment, when the
依據上述圖3至圖5的說明內容可以清楚得知,在補償階段TC中,移位暫存電路100可以透過將切換信號CHA設定為高電壓準位狀態的方式,以斷開前級閘極驅動信號G[N-1]傳送至控制端CT1的路徑,進而使輸出級電路110所產生的閘極驅動信號G[N]將不會受到前級閘極驅動信號G[N-1]的影響,而使閘極驅動信號G[N]能夠與後級閘極驅動信號G[N+1]進行同步輸出,藉以提升顯示閘極驅動裝置的效能。According to the above descriptions of FIGS. 3 to 5, it is clear that during the compensation stage TC, the
圖6是依照本發明一實施例的第N級的移位暫存電路在寫入階段的第一子階段的電路示意圖。請同時參照圖2以及圖6,具體來說,當移位暫存電路100操作於寫入階段TR的第一子階段TR_1時,移位暫存電路100可以設定模式選擇信號SS1以及模式選擇信號SS2皆為高電壓準位狀態。外接的時脈產生器(未繪製)可以提供具有高電壓準位的時脈信號CLK以及具有低電壓準位的反向時脈信號XCLK至移位暫存電路100。FIG. 6 is a circuit schematic diagram of the first sub-stage of the shift register circuit of the Nth stage in the writing stage according to an embodiment of the invention. Please refer to FIGS. 2 and 6 at the same time. Specifically, when the
詳細來說,電壓調整器130可以依據模式選擇信號SS1以及模式選擇信號SS2而被斷開。並且,電壓調整器120可依據被拉低的控制信號CS1而被導通。不同於補償階段TC的是,在寫入階段TR中,移位暫存電路100可以設定切換信號CHA為低電壓準位狀態,以使電壓調整器140可以依據切換信號CHA以及反向時脈信號XCLK而被導通。In detail, the
在此情況下,電壓調整器140可以將前級閘極驅動信號G[N-1]或起始脈波信號ST傳送至控制端CT1,以使控制信號CS1的電壓準位可以被下拉至閘極低電壓VGL的電壓值與一電壓值V3的總和。需注意到的是,所述電壓值V3可以表示為電晶體M7的導通電壓|VTH7|。亦即,此時的控制信號CS1的電壓準位為VGL+V3=VGL+|VTH7|。In this case, the voltage regulator 140 can transmit the previous-stage gate drive signal G[N-1] or the start pulse signal ST to the control terminal CT1, so that the voltage level of the control signal CS1 can be pulled down to the gate The sum of the voltage value of the very low voltage VGL and a voltage value V3. It should be noted that the voltage value V3 can be expressed as the on-voltage |VTH7| of the transistor M7. That is, the voltage level of the control signal CS1 at this time is VGL+V3=VGL+|VTH7|.
另一方面,在第一子階段TR_1中,電壓調整器160可以依據被下拉的反向時脈信號XCLK而持續的被導通,並對控制信號CS2持續的進行充電動作。接著,電壓調整器150可以依據被下拉的控制信號CS1而將閘極高電壓VGH傳送至控制端CT2,以使控制信號CS2的電壓準位可以被上拉至閘極高電壓VGH的電壓值。On the other hand, in the first sub-stage TR_1, the
換言之,本實施例中,當移位暫存電路100操作於第一子階段TR_1時,輸出級電路110可以依據被拉低的控制信號CS1來產生第N級閘極驅動信號G[N]。其中,此時的第N級閘極驅動信號G[N]的電壓準位為閘極低電壓VGL的電壓值與一電壓值V4的總和。需注意到的是,所述電壓值V4可以表示為電晶體M7的導通電壓|VTH7|以及電晶體M1的導通電壓|VTH1|。亦即,此時的閘極驅動信號G[N]的電壓準位為VGL+V4=VGL+|VTH7|+|VTH1|。In other words, in the present embodiment, when the
圖7是依照本發明一實施例的第N級的移位暫存電路在寫入階段的第二子階段的電路示意圖。請同時參照圖2以及圖7,具體來說,當移位暫存電路100操作於寫入階段TR的第二子階段TR_2時,移位暫存電路100可以設定模式選擇信號SS1以及模式選擇信號SS2持續維持為高電壓準位狀態。外接的時脈產生器(未繪製)可以提供具有低電壓準位的時脈信號CLK以及具有高電壓準位的反向時脈信號XCLK至移位暫存電路100。7 is a circuit schematic diagram of the second sub-stage of the N-stage shift register circuit in the writing stage according to an embodiment of the invention. Please refer to FIGS. 2 and 7 at the same time. Specifically, when the
詳細來說,電壓調整器130可以依據模式選擇信號SS1以及模式選擇信號SS2而持續的被斷開,並且電壓調整器120可依據被拉高的反向時脈信號XCLK而重新被斷開。接著,補償電路120可以依據被拉低的控制信號CS1而被導通。在此同時,由於後級閘極驅動信號G[N+1]的被拉低至電壓準位VA,因此,節點P1上的電壓值可以依據後級閘極驅動信號G[N+1]而同步地被下拉至電壓準位VA。如此一來,補償電路120可以藉由電容C1的耦合效應,以使控制信號CS1的電壓準位進一步的被調整為閘極低電壓VGL的電壓值與一電壓值V5的總和。需注意到的是,所述電壓值V5可以表示為電晶體M7的導通電壓|VTH7|與經由耦合效應後的一偏移值△V之間的電壓差值。亦即,此時的控制信號CS1的電壓準位為VGL+V5=VGL+|VTH7|-△V。In detail, the
另一方面,電壓調整器160可以依據被上拉的反向時脈信號XCLK而重新被斷開。接著,電壓調整器150可以依據被拉低的控制信號CS1來提供閘極高電壓VGH至控制端CT2以使控制信號CS2的電壓準位維持為閘極高電壓VGH的電壓值。On the other hand, the
換言之,在本實施例中,當移位暫存電路100操作於第二子階段TR_2時,輸出級電路110可以依據被拉低的控制信號CS1來提供閘極低電壓VGL以對輸出端OUT進行充電動作,並使輸出級電路110可以透過輸出端OUT來產生具有閘極低電壓VGL的電壓準位的第N級閘極驅動信號G[N]。In other words, in the present embodiment, when the
圖8是依照本發明一實施例的第N級的移位暫存電路在電壓保持階段的電路示意圖。請同時參照圖2以及圖8,具體來說,當移位暫存電路100操作於電壓保持階段TVH時,移位暫存電路100可以設定模式選擇信號SS1以及模式選擇信號SS2持續為高電壓準位狀態,並且,外接的時脈產生器(未繪製)可以提供以週期性轉態的時脈信號CLK以及反向時脈信號XCLK至移位暫存電路100。FIG. 8 is a circuit schematic diagram of the Nth-stage shift register circuit in the voltage holding stage according to an embodiment of the invention. Please refer to FIG. 2 and FIG. 8 at the same time. Specifically, when the
詳細來說,電壓調整器130可以依據模式選擇信號SS1以及模式選擇信號SS2而維持被斷開。在此同時,電壓調整器140可以依據反向時脈信號XCLK而週期性的被導通,並且電壓調整器140可以週期性的對控制信號CS1進行充電動作,藉以拉高控制信號CS1。接著,電壓調整器120可以依據被拉高的控制信號CS1而再次被斷開。In detail, the
另一方面,電壓調整器160可以依據反向時脈信號XCLK而週期性的被導通,並且電壓調整器160可以週期性的對控制信號CS2進行充電動作,藉以拉低控制信號CS2的電壓準位。On the other hand, the
換言之,在本實施例中,當移位暫存電路100操作於電壓保持階段TVH時,輸出級電路110可以依據被拉低的控制信號CS2來提供閘極低電壓VGH以對輸出端OUT進行充電動作,並使輸出級電路110透過輸出端OUT來產生具有閘極高電壓VGH的電壓準位的第N級閘極驅動信號G[N]。In other words, in the present embodiment, when the
需注意到的,上述的高電壓準位可以是閘極高電壓VGH的電壓值,並且低電壓準位可以是閘極低電壓VGL的電壓值。It should be noted that the above-mentioned high voltage level may be the voltage value of the gate high voltage VGH, and the low voltage level may be the voltage value of the gate low voltage VGL.
依據上述的圖6至圖8的說明內容可以清楚得知,在寫入階段TR中,移位暫存電路100可以透過電容C1的耦合效應,來使控制信號CS1可以同步的被下拉,進而使閘極驅動信號G[N]與後級閘極驅動信號G[N+1]可以依序的被輸出,藉以提升閘極驅動裝置的效能。According to the above descriptions of FIGS. 6 to 8, it can be clearly understood that during the writing stage TR, the
綜上所述,本發明的閘極驅動裝置的移位暫存電路可以在補償階段時,使輸出級電路所產生的第N級閘極驅動信號與後級閘極驅動信號進行同步輸出。並且在寫入階段時,使輸出級電路所產生的第N級閘極驅動信號與後級閘極驅動信號依序的被輸出,藉以提升閘極驅動裝置的效能。In summary, the shift temporary storage circuit of the gate driving device of the present invention can synchronize the output of the Nth stage gate driving signal and the latter stage gate driving signal generated by the output stage circuit during the compensation stage. In the writing stage, the N-th gate driving signal and the subsequent-stage gate driving signal generated by the output stage circuit are output in order, thereby improving the performance of the gate driving device.
雖然本發明已以實施例揭露如上,然其並非用以限定本發明,任何所屬技術領域中具有通常知識者,在不脫離本發明的精神和範圍內,當可作些許的更動與潤飾,故本發明的保護範圍當視後附的申請專利範圍所界定者為準。Although the present invention has been disclosed as above with examples, it is not intended to limit the present invention. Any person with ordinary knowledge in the technical field can make some changes and modifications without departing from the spirit and scope of the present invention. The scope of protection of the present invention shall be subject to the scope defined in the appended patent application.
100‧‧‧移位暫存電路110‧‧‧輸出級電路120‧‧‧補償電路130~160‧‧‧電壓調整器CT1~CT2‧‧‧控制端CS1~CS2‧‧‧控制信號CHA‧‧‧切換信號C1‧‧‧電容G[N-1]~G[N+1]‧‧‧閘極驅動信號M1~M14‧‧‧電晶體OUT‧‧‧輸出端P1‧‧‧節點VGL‧‧‧閘極低電壓VGH‧‧‧閘極高電壓SS1~SS2‧‧‧模式選擇信號ST‧‧‧起始脈波信號TFR‧‧‧畫素期間TC‧‧‧補償階段TR‧‧‧寫入階段TVH‧‧‧電壓保持階段TC_1~TC_3、TR_1~TR_2‧‧‧子階段V1~V5‧‧‧電壓值VA‧‧‧電壓準位XCLK‧‧‧反向時脈信號100‧‧‧ Shift
圖1是依照本發明一實施例的第N級的移位暫存電路的電路圖。 圖2是依照本發明一實施例的第N級的移位暫存電路的波形示意圖。 圖3是依照本發明一實施例的第N級的移位暫存電路在補償階段的第一子階段的電路示意圖。 圖4是依照本發明一實施例的第N級的移位暫存電路在補償階段的第二子階段的電路示意圖。 圖5是依照本發明一實施例的第N級的移位暫存電路在補償階段的第三子階段的電路示意圖。 圖6是依照本發明一實施例的第N級的移位暫存電路在寫入階段的第一子階段的電路示意圖。 圖7是依照本發明一實施例的第N級的移位暫存電路在寫入階段的第二子階段的電路示意圖。 圖8是依照本發明一實施例的第N級的移位暫存電路在電壓保持階段的電路示意圖。FIG. 1 is a circuit diagram of an Nth-stage shift register circuit according to an embodiment of the invention. FIG. 2 is a waveform diagram of the shift register circuit of the Nth stage according to an embodiment of the invention. FIG. 3 is a circuit schematic diagram of the first sub-stage of the Nth-stage shift register circuit in the compensation stage according to an embodiment of the invention. FIG. 4 is a circuit schematic diagram of the second sub-stage of the N-stage shift register circuit in the compensation stage according to an embodiment of the invention. FIG. 5 is a circuit schematic diagram of the third sub-stage of the shift register circuit of the Nth stage in the compensation stage according to an embodiment of the invention. FIG. 6 is a circuit schematic diagram of the first sub-stage of the shift register circuit of the Nth stage in the writing stage according to an embodiment of the invention. 7 is a circuit schematic diagram of the second sub-stage of the N-stage shift register circuit in the writing stage according to an embodiment of the invention. FIG. 8 is a circuit schematic diagram of the Nth-stage shift register circuit in the voltage holding stage according to an embodiment of the invention.
100‧‧‧移位暫存電路 100‧‧‧shift temporary storage circuit
110‧‧‧輸出級電路 110‧‧‧ output stage circuit
120‧‧‧補償電路 120‧‧‧Compensation circuit
130~160‧‧‧電壓調整器 130~160‧‧‧Voltage regulator
CT1~CT2‧‧‧控制端 CT1~CT2‧‧‧Control terminal
CS1~CS2‧‧‧控制信號 CS1~CS2‧‧‧Control signal
CHA‧‧‧切換信號 CHA‧‧‧switch signal
C1‧‧‧電容 C1‧‧‧Capacitance
G[N-1]~G[N+1]‧‧‧閘極驅動信號 G[N-1]~G[N+1]‧‧‧Gate drive signal
M1~M14‧‧‧電晶體 M1~M14‧‧‧Transistor
OUT‧‧‧輸出端 OUT‧‧‧Output
P1‧‧‧節點 P1‧‧‧ Node
VGL‧‧‧閘極低電壓 VGL‧‧‧gate low voltage
VGH‧‧‧閘極高電壓 VGH‧‧‧gate high voltage
SS1~SS2‧‧‧模式選擇信號 SS1~SS2‧‧‧Mode selection signal
ST‧‧‧起始脈波信號 ST‧‧‧Start pulse signal
XCLK‧‧‧反向時脈信號 XCLK‧‧‧Reverse clock signal
Claims (17)
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CN201910451004.4A CN110060620B (en) | 2018-06-14 | 2019-05-28 | Gate driving device |
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US201862684913P | 2018-06-14 | 2018-06-14 | |
US62,684/913 | 2018-06-14 |
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TW107141083A TWI675359B (en) | 2018-06-14 | 2018-11-19 | Gate driving apparatus |
TW107141082A TWI689904B (en) | 2018-06-14 | 2018-11-19 | Gate driving apparatus |
TW107141056A TWI688942B (en) | 2018-06-14 | 2018-11-19 | Gate driving apparatus |
TW107141158A TWI670707B (en) | 2018-06-14 | 2018-11-20 | Gate driving apparatus |
TW107141167A TWI673704B (en) | 2018-06-14 | 2018-11-20 | Gate driving apparatus |
TW107141210A TWI677865B (en) | 2018-06-14 | 2018-11-20 | Gate driving apparatus |
TW108100427A TWI699742B (en) | 2018-06-14 | 2019-01-04 | Pixel circuit |
TW108100430A TWI688943B (en) | 2018-06-14 | 2019-01-04 | Pixel circuit and driving method thereof |
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TW107141083A TWI675359B (en) | 2018-06-14 | 2018-11-19 | Gate driving apparatus |
TW107141082A TWI689904B (en) | 2018-06-14 | 2018-11-19 | Gate driving apparatus |
TW107141056A TWI688942B (en) | 2018-06-14 | 2018-11-19 | Gate driving apparatus |
TW107141158A TWI670707B (en) | 2018-06-14 | 2018-11-20 | Gate driving apparatus |
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TW107141210A TWI677865B (en) | 2018-06-14 | 2018-11-20 | Gate driving apparatus |
TW108100427A TWI699742B (en) | 2018-06-14 | 2019-01-04 | Pixel circuit |
TW108100430A TWI688943B (en) | 2018-06-14 | 2019-01-04 | Pixel circuit and driving method thereof |
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- 2018-11-20 TW TW107141158A patent/TWI670707B/en active
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- 2018-11-20 TW TW107141210A patent/TWI677865B/en active
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2019
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TWI762286B (en) * | 2021-04-27 | 2022-04-21 | 友達光電股份有限公司 | Driving device and display |
TWI794960B (en) * | 2021-09-08 | 2023-03-01 | 凌巨科技股份有限公司 | Gate driving device |
Also Published As
Publication number | Publication date |
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TW202001840A (en) | 2020-01-01 |
TWI677865B (en) | 2019-11-21 |
TW202001839A (en) | 2020-01-01 |
TWI689904B (en) | 2020-04-01 |
TWI699742B (en) | 2020-07-21 |
TWI688942B (en) | 2020-03-21 |
TWI673704B (en) | 2019-10-01 |
TW202001862A (en) | 2020-01-01 |
TW202001863A (en) | 2020-01-01 |
TWI670707B (en) | 2019-09-01 |
TW202001848A (en) | 2020-01-01 |
TWI675359B (en) | 2019-10-21 |
TW202001849A (en) | 2020-01-01 |
TW202001865A (en) | 2020-01-01 |
TWI688943B (en) | 2020-03-21 |
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