EP2991159B1 - Réseau d'alimentation pour systèmes d'antennes - Google Patents

Réseau d'alimentation pour systèmes d'antennes Download PDF

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Publication number
EP2991159B1
EP2991159B1 EP15169109.4A EP15169109A EP2991159B1 EP 2991159 B1 EP2991159 B1 EP 2991159B1 EP 15169109 A EP15169109 A EP 15169109A EP 2991159 B1 EP2991159 B1 EP 2991159B1
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EP
European Patent Office
Prior art keywords
waveguide
feed network
microstrip
network according
conductor
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EP15169109.4A
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German (de)
English (en)
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EP2991159A1 (fr
Inventor
Thomas Merk
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Lisa Draexlmaier GmbH
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Lisa Draexlmaier GmbH
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/0006—Particular feeding systems
    • H01Q21/0037—Particular feeding systems linear waveguide fed arrays
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P5/00—Coupling devices of the waveguide type
    • H01P5/08—Coupling devices of the waveguide type for linking dissimilar lines or devices
    • H01P5/10—Coupling devices of the waveguide type for linking dissimilar lines or devices for coupling balanced with unbalanced lines or devices
    • H01P5/107—Hollow-waveguide/strip-line transitions
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P3/00—Waveguides; Transmission lines of the waveguide type
    • H01P3/02—Waveguides; Transmission lines of the waveguide type with two longitudinal conductors
    • H01P3/08—Microstrips; Strip lines
    • H01P3/081—Microstriplines
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P3/00—Waveguides; Transmission lines of the waveguide type
    • H01P3/12—Hollow waveguides
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P5/00—Coupling devices of the waveguide type
    • H01P5/02—Coupling devices of the waveguide type with invariable factor of coupling
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P5/00—Coupling devices of the waveguide type
    • H01P5/08—Coupling devices of the waveguide type for linking dissimilar lines or devices
    • H01P5/085—Coaxial-line/strip-line transitions
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P5/00—Coupling devices of the waveguide type
    • H01P5/12—Coupling devices having more than two ports
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P5/00—Coupling devices of the waveguide type
    • H01P5/12—Coupling devices having more than two ports
    • H01P5/16—Conjugate devices, i.e. devices having at least one port decoupled from one other port
    • H01P5/19—Conjugate devices, i.e. devices having at least one port decoupled from one other port of the junction type
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/0006—Particular feeding systems
    • H01Q21/0075—Stripline fed arrays
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/06—Arrays of individually energised antenna units similarly polarised and spaced apart
    • H01Q21/061—Two dimensional planar arrays
    • H01Q21/065—Patch antenna array
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q13/00—Waveguide horns or mouths; Slot antennas; Leaky-waveguide antennas; Equivalent structures causing radiation along the transmission path of a guided wave
    • H01Q13/02—Waveguide horns

Definitions

  • the invention relates to feed network with waveguide and two microstrip conductors for antenna systems, in particular for the bidirectional, in the Ka, Ku or X-band operated satellite communication for mobile and aeronautical applications.
  • antennas In order to connect aircraft for the transmission of multimedia data to a satellite network, it requires wireless broadband channels for data transmission at very high data rates.
  • antennas must be installed on the aircraft, which are small in size to be installed under a radome and yet for a directed wireless data communication with the satellite (eg in Ku-, Ka- or X-band) extreme requirements on the transmission characteristics meet, as a disturbance of adjacent satellites must be reliably excluded.
  • the antenna continues to be movable below the radome to track the satellite's orientation as the aircraft moves.
  • the antenna must be made compact in order to remain mobile under the radome.
  • antennas consist of antenna fields, which are constructed from single radiators and have suitable feed networks. They can be run in any geometry and any length to aspect ratio without sacrificing antenna efficiency. In particular, antenna fields can be realized with low height.
  • feed networks can be represented by a combination of waveguides and microstrip lines, but the number of power dividers needed is high. Power dividers in the waveguide area of the feed network require installation space that is available only to a limited extent.
  • JP 2010 028345 A is the feeding of an antenna by means of capacitive coupling by microstrip lines known.
  • the US Pat. No. 6,201,453 B1 shows a conductor loop for a probe on a transition conductor, which cooperates with a loop conductor for impedance matching without decoupling.
  • feed networks allow to distribute a sum signal amplitude and phase correct to the individual emitters in the transmission case or vice versa in the case of reception to correctly add the signals of the individual emitters to a sum signal.
  • the feed network consists of microstrip conductors which combine the first single emitter groups (eg NxN or NxM elements) and a waveguide network to again combine several N * N or N * M groups.
  • Motomi Abe et al "A waveguide-based power divider using H-plane probes short-circuited with substrate metallization patterns", Microwave Symposium Digest, 2008 IEEE MTT-S International, IEEE, Piscataway, NJ, USA, June 15, 2008 (2008-06-15), pages 1003-1006, XP031441274, DOI: 10.1109 / MWSYM.2008.4633004 ISBN: 978-1-4244-1780- 3 shows a power divider for coaxial lines, which in a closed hollow cuboid as H-sample, which are short-circuited via a substrate, coupled together. Thus, even large ratios such as 1: 8 can be realized.
  • Microstrip conductors have the advantage of a small footprint and thus enable a high integration density.
  • the disadvantage is higher electrical losses compared to waveguides, which, however, require a significantly larger volume compared to microstrip conductors.
  • the feed network includes a waveguide with broad sides and narrow sides, and two microstrip conductors, each containing a conductor loop.
  • the conductor loops each project from one of the narrow sides into the waveguide and are galvanically connected to a broad side of the waveguide, ie are short-circuited to the waveguide at the broad side.
  • the waveguide On the narrow side, the waveguide has a small opening through which the microstrip conductor is guided without being electrically in contact with the waveguide itself.
  • the conductor loops protrude from opposite narrow sides into the waveguide.
  • the microstrip conductors can connect a large number of antenna elements, if necessary via further microstrip power dividers, in the sense of their own feed networks and with low-loss short paths.
  • the H-field coupling of the waveguide and two microstrip conductors advantageously produces a power divider, the signals arriving via the waveguide. So you get a kind of "hybrid” power divider, which distributes the signal from a waveguide gate on 2 microstrip gates.
  • the conductor loops have an equal length within the waveguide.
  • the signals on both microstrip lines have the same phase position and in the control of the following antenna elements, no further phase compensation is required.
  • the conductor loops are also advantageous to arrange the conductor loops so that they project centrally from the narrow sides into the waveguide.
  • a maximum of power can be coupled into the microstrip line and the adaptation to the transition optimized.
  • the arrangement of the microstrip conductors in the waveguide advantageously takes place approximately ⁇ / 4 away from one end of the short-circuited waveguide.
  • divider ratios of 50:50 to 80:20 can be set in a broad range, as a result of which desired aperture tolerances of the antenna can be easily implemented.
  • one of the microstrip lines of the feed network can have a phase compensation arc which adapts the length of this microstrip line to the length of the other microstrip line and thus produces an equal microstrip line length and thus equal phase position of the signals of both microstrip lines despite asymmetry in the conductor loop shape.
  • phase compensation arc is assigned to the microstrip conductor which is electrically connected to the waveguide at a greater distance from the center of the broadside than the other microstrip conductor.
  • the conductor loops are advantageously not straight, but include width jumps and set pieces. By specifying the position and size of stride jumps and set pieces, the reflections are reduced for the desired frequency range.
  • the microstrip conductors consist of a board with a dielectric having a thickness of 0.1 to 1 mm, preferably 0.127 mm, and a copper strip arranged on the board with a thickness of 15 to 50 ⁇ m, preferably 17.5 ⁇ m.
  • the width of the copper strip is 0.2 to 3 mm, preferably 0.5 mm.
  • the waveguide or the waveguide network is performed according to an advantageous embodiment of the invention, at least in sections as ridge waveguide.
  • the ridge waveguide allows a wider band frequency range than a "normal” rectangular waveguide, particularly interesting for the Ka band.
  • a ridge waveguide allows more compact designs (reduction of the broad side) compared to a "normal” rectangular waveguide at the same cutoff frequency (interesting even at lower frequencies (X-band and Ku-band), in which the waveguide dimensions would otherwise be larger.
  • a distance between one end of the waveguide and the microstrip conductor is advantageously only ⁇ / 8 to ⁇ / 12, ie significantly less than ⁇ / 4, for which a maximum of the field strength would exist. It has been shown that with reasonable losses, the size of the feed network can be reduced once again.
  • the waveguide of the feed network may contain restrictions whereby a ridge waveguide is formed.
  • the galvanic connection of the conductor loops to the broad side of the waveguide does not interfere, but takes place in a rectilinear section.
  • the conductor loop with the larger power output advantageously has the width of the microstrip line larger than in the conductor loop with the lower power output.
  • the antenna comprising a plurality of horn radiators as antenna elements, which are connected via microstrip conductors with a waveguide having broad sides and narrow sides.
  • the microstrip conductors each consist of a conductor loop which protrudes from one of the narrow sides into the waveguide and is electrically connected to a broad side of the waveguide.
  • Horn radiators are very efficient single radiators, which are arranged in antenna fields. In addition, horns can be designed broadband.
  • the antenna is suitable for bidirectional operation in vehicle-based satellite communication in a frequency band of 7.25-8.4 GHz (X-band), 12-18 GHz (Ku-band) and 27-40 GHz (Ka-band).
  • X-band 7.25-8.4 GHz
  • Ku-band 12-18 GHz
  • Ka-band 27-40 GHz
  • FIG. 1 shows a waveguide HL, which is filled with air and has the dimensions 16 x 6 mm for the Ku band or 7 x 2.5 mm for the Ka band.
  • the termination at the end AB of the waveguide HL is about A / 4 of a coupling of two microstrip MS1, MS2 away.
  • the microstrip conductors MS1, MS2 protrude from a narrow side b1, b2 into the waveguide HL.
  • the microstrip lines MS1, MS2 consist of a Suspended Strip Line (SSL), which consists of a circuit board on which a copper strip, a copper layer, is applied.
  • SSL Suspended Strip Line
  • the board itself consists of a dielectric with a thickness of 0.1 to 1 mm, preferably 0.127 mm.
  • the copper strip thereon has a width of 0.2 to 3 mm, preferably 0.5 mm, and a thickness of 15 to 50 microns, preferably 17.5 pm. So that the microstrip conductors MS1, MS2 can protrude into the waveguide HL, the narrow sides b1, b2 at the level of the coupling have a narrow slot, which is adapted to the shape of the microstrip line MS1 and MS2.
  • the SSL is surrounded by metal, so there are no power losses from radiation out of the structure and through the passage at the slots. By appropriate dimensioning of the slot and the interference on the field of the waveguide HL is negligible.
  • both microstrip conductors MS1, MS2 are galvanically connected to the waveguide HL.
  • This connection in each case represents a short circuit 1 of the respective microstrip line MS1, MS2 with the waveguide HL.
  • the inductive H-field coupling is in FIG. 2 shown again. On a sectional plane through the coupling can be seen at the locations near the short circuits 1 as the H-field coupled as TE mode from the waveguide HL in the two microstrip lines MS1, MS2 as TEM mode.
  • the feeding network according to the invention consisting of the two microstrip conductors MS1, MS2 and the waveguide HL, will now be described with reference to FIGS. 3 to 5 further explained.
  • the conductor loops l1, l2 within the waveguide HL form two loops of equal size, which extend from the narrow sides b1 or b2 to the broadside a1. These equal areas of the conductor loops l1, l2 mean a symmetrical power division.
  • the conductor loops l1, l2 also contain set pieces and width jumps, which favor the adaptation of the microstrip conductor MS1 or MS2 to the conditions of the waveguide HL.
  • a conductor loop piece, which in each case adjoins the broad side a1 is narrowest and a conductor loop piece which represents the transition to the microstrip conductor MS1 or MS2 outside the waveguide HL is widest. Size and position of the wide jumps or set pieces are optimized accordingly for the desired frequency band.
  • microstrip conductors MS1, MS2 continue after the slot in the narrow side b1, b2 of the waveguide HL and form microstrip conductor networks, with which, as shown later, antenna elements are supplied.
  • FIG. 4 shows in comparison to FIG. 3 a variant in which a phase shift of the signals between the microstrip conductors MS1, MS2 is effected in that the electrical connection of the conductor loops l1, l2 takes place on opposite broad sides a1 and a2 of the waveguide HL.
  • the positioning of the conductor loops l1 and l2 is here again symmetrical, but with respect to the top and bottom of the waveguide HL mirror image. This means that once again a balanced power line is achieved, but the signals on one microstrip line MS1 are 180 ° out of phase with respect to the other microstrip line MS2.
  • a center M of the broad sides of the waveguide is located.
  • the conductor loop l1 on the left side of the waveguide has a larger flooded area than the conductor loop l2 on the right side.
  • the lengths of the conductor loops l1 and l2 within the waveguide differ with it.
  • the microstrip conductor MS2 with the lower power output contains an additional phase arc P, which brings about a length compensation of the microstrip line MS2 and an adjustment to the length of the other microstrip line MS1.
  • divider ratios can be set from 50:50 to 80:20 become. This allows multiple aperture assignments for the antenna driven by the feed network. Due to a set phase shift between the two microstrip lines MS1, MS2, see FIG. 4 , geometrically mirrored antenna elements or possible phase shifts can be compensated by subsequent waveguide networks.
  • FIG. 6 is an alternative waveguide shape to the otherwise rectangular waveguide HL as in FIG. 1 , shown.
  • the waveguide HL is provided as a ridge waveguide, each with a restriction RI centered in the broad sides a1, a2.
  • the waveguide HL broadband.
  • the web waveguide HL has a width paragraph SP, in which the dimensions of the narrow sides b1, b2 and broad sides a1, a2 change abruptly, and a length of the restriction RI is changed. This is used to minimize the reflections.
  • the food network according to the invention is used in particular in antennas with multiple horns as antenna elements.
  • FIG. 7 shows an antenna with 16 antenna elements, a feed network is able to feed 8 antenna elements A1 to A8 alone.
  • a waveguide HL is arranged centrally within eight antenna elements A1 to A8, and on both narrow sides the signals are divided into two microstrip conductors MS1 or MS2 decoupled. These microstrip conductors MS1, MS2 in turn form microstrip conductor networks, which connect in each case 4 antenna elements A1 to A4 or A5 to A8 to the waveguide HL.
  • the waveguide HL in turn forms the conclusion of a waveguide network.
  • only one waveguide power divider is shown.
  • the waveguide network is in turn connected to a transmitting and receiving device Tx / Rx, which receives corresponding signals from the antenna or sends to the antenna.
  • the feed network shown here allows the feeding of a large number of antenna elements with a minimum of power dividers in the waveguide network.
  • lightweight compact antennas are represented, as they are needed in the aircraft-based satellite communication in the X, Ku or Ka band.
  • FIGS. 8 to 13 show alternative embodiments of the feed networks according to the invention, which except for the embodiment according to FIG. 13 Include climbing ladders with restrictions RI.
  • FIG. 8 shows a symmetrical power divider (power output 50% / 50%), in which the electrical connection of the conductor loops l1, l2 is just right and left of the restriction RI of the waveguide HL. Both conductor loops l1, l2 frame the same area and have the same widths of the conductor tracks.
  • the food network after FIG. 9 is particularly suitable for narrow frequency bands, for example in X-band.
  • a distance AB1 of one end of the waveguide HL to the microstrip conductor is only about ⁇ / 10, that is to say significantly less than ⁇ / 4 or half the length A1 of the broad side a1.
  • the size of the feed network is reduced again.
  • FIGS. 10 and 11 show asymmetrical dividers with a divider ratio of 66.7% / 33.3% and 57% / 43% respectively, which are set by the fact that the left conductor loop l1 encloses a larger area than the right conductor loop l2. Also in these feed networks, the galvanic electrical connection between the conductor loop l1, l2 and waveguide HL is done without the restriction RI is touched in a rectilinear region of the waveguide HL. In FIG. 9 this is clear. The restriction RI starts from the end of the waveguide AB only shortly after the microstrip MS2. How out FIG.
  • the width D of the left conductor loop l1 with the larger power output coupling is greater than the width of the right conductor loop l2.
  • the left conductor loop l1 is lower impedance than the right conductor loop l2 and well adapted.
  • the area to be set for the power division - essentially determined by the length of the first line section of the short circuit A and the length of the second line section in the direction of the narrow waveguide side B, which framing the respective line loop l1, l2, are for a reflection-poor adaptation of the microstrip MS1, MS2 after FIG. 12
  • the width of the first line section C, the width of the second line section D are selected according to the impedance of the conductor loop necessary for a reflection-poor matching.
  • the conductor loop with the greater power output has the designations in FIG. 12 a larger width C, D of the microstrip line than the other conductor loop with the lower power output - see FIG. 10 ,
  • the waveguide HL contains a Opening in which a circuit board PL is inserted with the conductor loops forming conductors L on the surface.
  • the interconnects L of both sides of the board PL are interconnected by means of vias V.
  • the insulation I is formed by an electrically insulating coating, eg solder resist.
  • the conductor tracks L are made of copper, the waveguide HL is made of aluminum.

Claims (20)

  1. Réseau d'alimentation pour systèmes d'antennes comportant un guide d'ondes (HL) ayant des côtés larges (a1, a2) et des côtés étroits (b1, b2),
    deux lignes à microrubans (MS1, MS2), chacune constituée d'une boucle conductrice (11, 12), qui dépasse de l'un des côtés étroits (b1, b2) dans le guide d'ondes (HL) et est reliée galvaniquement à un côté large (a1, a2) du guide d'ondes (HL), et dans lequel les boucles conductrices (11, 12) ne sont pas formées exclusivement da manière à ce qu'elles soient droites, mais contiennent des discontinuités de largeur et des pièces décalées.
  2. Réseau d'alimentation selon la revendication 1, dans lequel les boucles conductrices (11, 12) dépassent des côtés étroits opposés (b1, b2) dans le guide d'ondes (HL).
  3. Réseau d'alimentation selon l'une des revendications précédentes, dans lequel un couplage de guides d'ondes (HL) et de lignes à microrubans (MS1, MS2) fait office de diviseur de puissance pour les signaux pénétrant par l'intermédiaire du guide d'ondes (HL) .
  4. Réseau d'alimentation selon l'une des revendications précédentes, dans lequel les boucles conductrices (11, 12) présentent la même longueur à l'intérieur du guide d'ondes (HL).
  5. Réseau d'alimentation selon l'une des revendications précédentes, dans lequel les boucles conductrices (11, 12) font saillie centralement dans le guide d'ondes (HL) par rapport aux côtés étroits (b1, b2).
  6. Réseau d'alimentation selon l'une des revendications 1 à 3, dans lequel les raccordements électriques des deux boucles conductrices (11, 12) au côté large (a1, a2) du guide d'ondes (HL) sont espacés différemment d'un centre (M) du côté large (a1, a2).
  7. Réseau d'alimentation selon les revendications 1 à 3, dans lequel au moins une ligne à microruban (MS2) présente un arc de compensation de phase (P) qui adapte la longueur de ladite ligne à microruban (MS2) à la longueur de l'autre ligne à microruban (MS1).
  8. Réseau d'alimentation selon la revendication précédente, dans lequel la ligne à microruban (MS2) est reliée électriquement au guide d'ondes (HL) à une plus grande distance du centre du côté large (a1, a2) que l'autre ligne à microruban (MS1) au moyen d'arcs à compensation de phase (P).
  9. Réseau d'alimentation selon l'une des revendications précédentes, dans lequel le raccordement électrique des boucles conductrices (11, 12) s'effectue sur différents côtés larges (a1, a2) du guide d'ondes creux (HL).
  10. Réseau d'alimentation selon l'une des revendications précédentes, dans lequel les lignes à microrubans (MS1, MS2) sont définies comme étant des SSL (suspended strip line).
  11. Réseau d'alimentation selon la revendication précédente, dans lequel les lignes à microruban (MS1, MS2) comprend une carte de circuit imprimé constituée d'un diélectrique ayant une épaisseur de 0,1 à 1 mm, de préférence 0,127 mm, et d'une bande de cuivre disposée sur la carte de circuit imprimé et ayant une épaisseur de 15 à 50 µm, de préférence 17,5 µm, et une largeur de 0,2 à 3 mm, de préférence 0,5 mm.
  12. Réseau d'alimentation selon l'une des revendications précédentes, dans lequel le guide d'ondes (HL) peut être relié à plusieurs éléments d'antenne (A1 ... A8) au moyen des lignes à microrubans (MS1, MS2), dans lequel les éléments d'antenne Al... A8) sont des éléments rayonnants à cornet et les lignes à microrubans (MS1, MS2) sont disposées à environ λ/4 d'une extrémité (AB) du guide d'ondes (HL).
  13. Réseau d'alimentation selon l'une des revendications précédentes, dans lequel le guide d'ondes (HL) fait partie d'un réseau d'alimentation de guide d'ondes pouvant être relié à des dispositifs d'émission et de réception (Tx/Rx).
  14. Réseau d'alimentation selon l'une des revendications précédentes, dans lequel le guide d'ondes (HL) est conçu au moins par sections sous la forme d'un guide d'ondes à moulures.
  15. Réseau d'alimentation selon l'une des revendications 1 à 1, dans lequel une distance (AB1) entre une extrémité (AB) du guide d'ondes (HL) et la ligne à microruban (MS1, MS2) est de λ/8 à λ/12.
  16. Réseau d'alimentation selon l'une des revendications précédentes, dans lequel la liaison galvanique des boucles conductrices (11, 12) au côté large (a1, a2) du guide d'ondes (HL) s'effectue sur une section droite du guide d'ondes (HL).
  17. Réseau d'alimentation selon l'une des revendications 1 à 3, dans lequel les boucles conductrices (11, 12) encadrent une surface différente et ajustent un diviseur de puissance asymétrique.
  18. Réseau d'alimentation selon la revendication 17, dans lequel la boucle conductrice (11) présentant le couplage de sortie de puissance le plus élevé la largeur (D) de la ligne à microruban (MS1) est supérieure à celle de l'autre boucle conductrice (12).
  19. Antenne comportant plusieurs éléments rayonnants à cornet en tant qu'éléments d'antenne (Al... A8) et un réseau d'alimentation selon l'une des revendications précédentes, dans lequel les lignes à microrubans (MS1, MS2) sont reliées aux éléments d'antenne (Al... A8).
  20. Antenne selon la revendication précédente pour les communications par satellite sur véhicules dans une bande de fréquences X, Ka ou Ku, dans lequel les éléments d'antenne (A1... A8) sont conçus pour fonctionner en émission et en réception.
EP15169109.4A 2014-08-29 2015-05-26 Réseau d'alimentation pour systèmes d'antennes Active EP2991159B1 (fr)

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EP (1) EP2991159B1 (fr)
CN (1) CN105390820B (fr)
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FR3090219B1 (fr) * 2018-12-18 2022-12-30 Thales Sa Combineur hybride e/h ultracompact notamment pour antenne mfb monoreflecteur
CN110190371B (zh) * 2019-05-29 2024-03-12 中电国基南方集团有限公司 一种波导功分器
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EP2991159A1 (fr) 2016-03-02
US20160064796A1 (en) 2016-03-03
CN105390820B (zh) 2021-04-16
DE102014112467B4 (de) 2017-03-30
DE102014112467A1 (de) 2016-03-03
CN105390820A (zh) 2016-03-09
US9761955B2 (en) 2017-09-12

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