EP2469783B1 - Récepteur de signaux radiofréquences FSK avec un démodulateur à haute sensibilité ainsi que procédé pour sa mise en action - Google Patents

Récepteur de signaux radiofréquences FSK avec un démodulateur à haute sensibilité ainsi que procédé pour sa mise en action Download PDF

Info

Publication number
EP2469783B1
EP2469783B1 EP10196893.1A EP10196893A EP2469783B1 EP 2469783 B1 EP2469783 B1 EP 2469783B1 EP 10196893 A EP10196893 A EP 10196893A EP 2469783 B1 EP2469783 B1 EP 2469783B1
Authority
EP
European Patent Office
Prior art keywords
signals
frequency
receiver
discrete fourier
sampled
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Active
Application number
EP10196893.1A
Other languages
German (de)
English (en)
French (fr)
Other versions
EP2469783A1 (fr
Inventor
Arnaud Casagrande
Jean-Luc Arend
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Swatch Group Research and Development SA
Original Assignee
Swatch Group Research and Development SA
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Swatch Group Research and Development SA filed Critical Swatch Group Research and Development SA
Priority to EP10196893.1A priority Critical patent/EP2469783B1/fr
Priority to TW100146599A priority patent/TWI513200B/zh
Priority to US13/331,720 priority patent/US8774748B2/en
Priority to CN201110439404.7A priority patent/CN102594752B/zh
Priority to KR1020110141181A priority patent/KR101299332B1/ko
Priority to JP2011282841A priority patent/JP5497729B2/ja
Publication of EP2469783A1 publication Critical patent/EP2469783A1/fr
Priority to HK13100605.2A priority patent/HK1173579A1/zh
Application granted granted Critical
Publication of EP2469783B1 publication Critical patent/EP2469783B1/fr
Active legal-status Critical Current
Anticipated expiration legal-status Critical

Links

Images

Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/10—Frequency-modulated carrier systems, i.e. using frequency-shift keying
    • H04L27/14—Demodulator circuits; Receiver circuits

Definitions

  • the invention relates to a high sensitivity demodulator FSK radio frequency signal receiver.
  • the invention also relates to a method for activating the high sensitivity demodulator FSK radiofrequency signal receiver.
  • a conventional transmitter or receiver uses a modulation of the FSK (Frequency Shift Keying) type.
  • the carrier frequency RF is high, for example of the order of 2.4 GHz, a fairly high bandwidth is chosen for the intermediate frequency, especially greater than or equal to 200 kHz.
  • the modulation frequency deviation in the modulated signals can be adapted according to this bandwidth. In this case, it can be used a frequency reference provided by a local oscillator, which may not be very accurate and therefore cheap.
  • the power of the thermal noise must be taken into account, which is proportional to this selected bandwidth.
  • a broadband transmission or reception system generally does not have excellent sensitivity.
  • the frequency of the oscillating signals provided by this oscillator can vary by about ⁇ 20 ppm.
  • the frequency error on the oscillating signals produced by the local oscillator can be thus about ⁇ 100 kHz.
  • low-pass or bandpass filtering is generally performed directly on the intermediate signals supplied by the mixer unit, this does not allow precise filtering subsequently to have a high-sensitivity receiver.
  • the frequency of the intermediate signals may be outside the frequency bands of narrowband band-pass filters. Under these conditions, all the data or commands of the radiofrequency signals received can not be taken after the demodulation stage, which is a drawback. It is therefore generally difficult to use inexpensive quartz if it is hoped to demodulate the data following narrow-band bandpass filtering.
  • the frequency error of the intermediate signals should be absolutely corrected.
  • PSK Phase Shift Keying
  • Requirement US2004 / 0190663 A1 describes the frequency synchronization in an FSK receiver based on the search for the maximum in a power function calculated on the basis of an FFT transform.
  • the receiver can receive a signal at a carrier frequency in a determined frequency range.
  • the captured signals are amplified and filtered before being frequency converted into mixers by in-phase and quadrature oscillating signals of a local oscillator.
  • In-phase and quadrature intermediate signals at the output of the mixers are filtered by low-pass filters before being sampled each in a respective sampler.
  • a set of N samples is stored in a memory buffer.
  • a discrete Fourier transform (DFT) is performed on the N stored samples and the result of the discrete Fourier transform is stored in an output buffer.
  • the frequency of the local oscillator is not adjusted, which prevents centering the frequency of the intermediate signals. Therefore, it can not be expected to perform a demodulation of high sensitivity data, which is a drawback.
  • DFT discrete Fourier transform
  • the patent application US 2003/0203729 A1 mainly describes frequency compensation in a GFSK radio frequency signal receiver.
  • the frequency of the radio frequency signals to be sensed can be between 2.4 and 2.4835 GHz be of the order of 2.4 GHz according to the Bluetooth network.
  • the frequency of the local oscillator must be adjusted to eliminate any frequency deviation from the frequency of the received signals.
  • a peak detector of the picked up signals is provided to determine a peak peak positive value and a peak peak negative value of captured RF signals.
  • the midpoint between the positive and negative values of the peaks represents the detected center frequency. This thus makes it possible to adjust the frequency of the oscillator in the AFC automatic frequency compensation loop to the desired frequency for demodulation of the data.
  • the determination of the frequency deviation is made at high frequency to be able to adjust the frequency of the oscillator, and nothing is planned to reduce the power consumption of this receiver, which is a drawback.
  • the object of the invention is therefore to provide a radio frequency signal receiver FSK, which is highly sensitive and easily configurable so as to be able to center the frequency of the intermediate signals before a high sensitivity demodulation operation while overcoming the aforementioned drawbacks of the state. of the technique.
  • the invention relates to a radio frequency signal receiver FSK, which comprises the characteristics mentioned in the independent claim 1.
  • An advantage of such a radio frequency signal receiver FSK according to the invention resides in the fact that a sampled intermediate signal processing circuit is used.
  • This processing circuit uses a discrete Fourier transform (DFT) to control how often each peak of power is above a certain threshold.
  • DFT discrete Fourier transform
  • This discrete Fourier transform is fast and carried out on a limited frequency band, for example of the order of 200 kHz centered on the central frequency of the intermediate signals.
  • This limited frequency band is based on the possible frequency error of the local oscillator, which can be provided with a cheap quartz.
  • FFT Fast Fourier Transform
  • FSK radiofrequency signals are preferably at a low rate. This makes it possible to carry out demodulation with high sensitivity easily, since with a low data or command rate, the power of the captured FSK signals is concentrated around the modulation frequency deviation.
  • the demodulation stage includes a first narrowband digital filter for filtering the sampled intermediate signals having a positive frequency offset, and a second narrowband digital filter for filtering the sampled intermediate signals having zero or negative frequency deviation.
  • the output signals of the digital filters each first pass through an energy detector before subtracting the signals from the two digital filters to provide data signals or commands.
  • the high sensitivity demodulation stage comprises a first DFT demodulator for demodulating the sampled intermediate signals having a positive frequency deviation, and a second DFT demodulator for demodulating the sampled intermediate signals having a zero or negative frequency deviation.
  • the output signals of the DFT demodulators are subsequently subtracted to provide data signals or commands.
  • the invention also relates to a method for operating the radio frequency signal receiver FSK, which comprises the characteristics defined in the independent claim 9.
  • An advantage of the method according to the invention lies in the fact that after at least one acquisition phase of a certain number of points of the intermediate signals by the sampler, at least one discrete Fourier transform, for example 1 bit on a limited frequency band.
  • the result (s) of the discrete Fourier transforms can be stored.
  • a control of the frequency of the amplitude peak or peaks above a determined threshold is performed in order to estimate the frequency error with respect to an expected frequency with a positive or negative signal modulation frequency deviation.
  • Frequency correction is subsequently performed in the local oscillator to adapt the frequency of the oscillating signals and to refocus the frequency of the intermediate signals before a high sensitivity demodulation.
  • a double acquisition by the sampler of the intermediate signals, and a double discrete Fourier transform of sampled intermediate signals are performed at different periods.
  • a storage of the two results of the discrete Fourier transform is performed.
  • a search algorithm with n important vectors then makes it possible to compare the amplitude peaks above a determined threshold of the two stored results to determine any parasitic peak of disturbing signals received.
  • the frequency of the oscillating signals is corrected to be able to refocus the center frequency of the intermediate signals.
  • a high sensitivity demodulation of the sampled intermediate signals can be performed.
  • radio frequency signal receiver FSK can advantageously be used, for example, in data transmission systems or short-range commands.
  • the high-sensitivity FSK radio frequency signal receiver 1 is shown in a simplified manner at figures 1 and 2 .
  • This radio frequency signal receiver FSK operates according to an asynchronous approach.
  • the receiver is configured to receive FSK radio frequency signals, which are preferably low data rate, for example of the order of 1 kbit / s. It is thus possible with the high-sensitivity radio frequency signal receiver 1 to have a sensitivity greater than 17 dB with respect to a FSK radio frequency signal receiver with a high data rate, for example at 100 kbit / s.
  • ⁇ f / Dp 1 ⁇ 2.
  • a corresponding frequency deviation ⁇ f of 500 Hz requires a very high spectral purity of the synthesizers of a transmitter and a receiver, so a very low noise of phase. This is necessary to demodulate with a satisfactory signal-to-noise ratio.
  • the use of a higher ⁇ f / Dp ratio circumvents this problem.
  • the radio frequency signal receiver FSK 1 is therefore able to advantageously capture FSK radiofrequency signals with a low data rate or commands.
  • the power of the sensed signals is generally concentrated at the modulation frequency deviation ⁇ f (positive and negative) with respect to the carrier frequency f 0 of the signals.
  • a "1" modulation state is defined by the addition of the frequency carrier f 0 and the modulation frequency deviation ⁇ f, which gives f 0 + ⁇ f
  • a "0" modulation state is defined by the modulation frequency deviation ⁇ f subtracted from the carrier frequency f 0 , this which gives f 0 - ⁇ f.
  • the state "0" modulation is defined as the carrier frequency f 0, even if the modulation data to f 0 + f and .DELTA.f 0 - ⁇ f is preferred.
  • the radio frequency signal receiver FSK 1 comprises an antenna 2 for receiving FSK signals, whose carrier frequency can be for example of the order of 2.4 GHz.
  • the FSK signals picked up by the antenna 2 are amplified in a LNA 3 low-noise amplifier.
  • This LNA 3 low-noise amplifier may also comprise a not shown band-pass filter.
  • the amplified and filtered RF FSK signals are frequency-converted in a mixer 4 by oscillating signals S O provided by a local oscillator 5, to provide intermediate intermediate or intermediate frequency signals f (IF).
  • the intermediate frequency may preferably be of the order of 400 kHz, but it can also be expected that this intermediate frequency is zero following a direct conversion baseband by the mixer 4.
  • These intermediate signals INT are filtered in a broad bandpass filter or polyphase 8 before again passing through a traditional amplifier limiter 9.
  • the bandwidth of the filter 8 can be fixed for example to 600 kHz in the case of an intermediate frequency of the order of 400 kHz.
  • This bandwidth of the filter 8 is set to take account of the frequency error of the oscillating signals provided by the local oscillator, or also of the received FSK radio frequency signals.
  • the frequency error of the oscillating signals may be of the order of ⁇ 100 kHz, as the oscillating signals S O are generated by an inexpensive quartz resonator ( ⁇ 20 ppm) not shown.
  • the intermediate signals INT filtered and amplified by the limiter 9, are subsequently sampled in a sampler 10, which is clocked by a clock signal CLK.
  • This clock signal may have a frequency, for example equal to 1.625 MHz.
  • This clock signal CLK comes from a series of unrepresented dividers, which are connected to a 26 MHz crystal resonator of the local oscillator 5.
  • the intermediate signals are thus sampled, in order to accumulate a number N of points to be processed in a processing circuit or control 11. It can be expected to provide 2048 points to be processed by the processing circuit.
  • the processing circuit 11 operates a discrete Fourier transform (DFT) to determine the frequency of the largest sampled intermediate signals, i.e. with the largest amplitude above a certain threshold.
  • DFT discrete Fourier transform
  • the result of the discrete Fourier transform can be transmitted to a selector 12 at the output of the processing circuit 11.
  • This selector 12 may comprise a memory unit for storing the discrete Fourier transform operated.
  • the discrete Fourier transform following a first acquisition can also be stored in the processing circuit 11.
  • the discrete Fourier transform in the processing circuit 11 is advantageously operated on a frequency band between 300 kHz and 500 kHz with 200 bands at 1 kHz for example.
  • the number of bands can of course be increased according to the desired frequency resolution.
  • a power peak above a determined threshold is shown.
  • a frequency error is noted with respect to an expected frequency of the intermediate signals.
  • ⁇ f it should be represented two power peaks above the determined threshold.
  • FFT Fast Fourier Transform
  • the discrete Fourier transform control circuit 11 may be 1 bit. This DFT convolves the intermediate signals sampled with 200 sine and cosine vectors representative of the 200 frequency bands to be analyzed. The results are further squared and summed to calculate the corresponding 200 power amplitude vectors. Only the N largest vectors above a configurable threshold are retained and stored in the selector 12. The number N of vector can be equal to 4.
  • the selector 12 controls the frequency error with respect to the expected central frequency of the intermediate signals, taking into account the positive and negative modulation modulation of the ⁇ f data. .
  • a command signal Err is thus transmitted to the local oscillator 5, to enable it to adapt the frequency of the oscillating signals S O.
  • the correction of the frequency of the oscillating signals thus makes it possible to refocus the frequency of the intermediate signals INT supplied at the output of the mixer 4. This operation of adapting the frequency of the intermediate signals is necessary in order to be able to carry out a high sensitivity demodulation via of the HS high sensitivity demodulation stage 13 described below.
  • the selector 12 which is combined with the DFT control circuit 11, makes it possible to put into operation a search algorithm with n important vectors derived from the processing circuit 11.
  • a 4-vector search algorithm this is sufficient to be able to select at least one important vector for adapting the frequency of the oscillating signals S O of the local oscillator 5.
  • the use of this algorithm is mainly used to eliminate the disturbing parasitic signals, which have been picked up in plus FSK radio frequency signals. These may be, for example, signals emitted for the door lock control of a car near the receiver.
  • a series of acquisitions of the sampled intermediate signals up to the time t n and corresponding discrete Fourier transforms is performed.
  • the selector 12 thus takes into account the two results of the discrete Fourier transform, which are not directly successive in time at t n-2 and t n .
  • An acquisition interval and additional DFT treatment is still provided between the two results to be controlled.
  • the two discrete Fourier transform results are compared, in order to eliminate disturbing parasitic signals.
  • the "good" FSK radiofrequency signals, picked up by the receiver, are identified in the frequency domain by amplitude or power peaks at different frequencies above a determined threshold. At least two amplitude peaks representing the modulation frequencies in the intermediate signals are normally provided above a determined threshold, if, during the acquisition phases, the data alternate between state "1" and the state "0". Following the two discrete Fourier transforms at t n-2 and t n , these amplitude peaks appear spaced apart by a very precise frequency interval, which is in principle only exceptionally the case for disturbing parasitic signals.
  • an emitter transmits a series of "1" for a first acquisition at time t n-2 by the receiver, which gives only a detected amplitude peak (f (IF) + ⁇ f) for good signals picked up.
  • the transmitter can transmit a series of "0" for a second acquisition at time t n by the receiver, which gives another peak amplitude detected (f (IF) - ⁇ f).
  • the difference in frequency between the two peaks of the right signals is precisely twice the FSK frequency deviation of the transmitter. This makes it possible to correct the frequency of the local oscillator with an absolute error.
  • the amplitude peaks of the sampled parasitic signals appear in principle only once at the same frequency. to the two discrete Fourier transforms, and the frequency difference between them does not correspond to the modulation frequency deviation. As a result, it is easy to eliminate these parasitic signals in the selector 12.
  • the local oscillator 5 mainly comprises a well-known sigma-delta frequency synthesizer 6, which comprises a 26 MHz quartz resonator, for example, not shown, to provide a reference signal in the phase locked loop of the synthesizer.
  • Oscillating signals S O are output from a well-known VCO voltage-controlled oscillator.
  • the frequency synthesizer 6 is also controlled by a frequency programming signal. This programming signal comes from an adder 7, which performs the addition of a basic frequency signal f 0 + f (IF), which is used at each initialization of the receiver, and a control signal Err relating to the frequency error, which is determined by the combination of the processing circuit 11 and the selector 12.
  • the demodulation stage HS 13 makes it possible to carry out a high sensitivity demodulation once the frequency of the intermediate signals has been well adapted.
  • This HS demodulation stage 13 comprises a first narrowband digital filter 14 for filtering the sampled intermediate signals having a positive frequency deviation f (IF) + ⁇ f, and a second narrowband digital filter 15 for filtering the sampled intermediate signals having a zero or negative frequency deviation f (IF) - ⁇ f.
  • the bandwidth of each digital filter can be of the order of 2 kHz.
  • the filtered signals at the output of the first digital filter 14 pass through a first energy detector 16, while the filtered signals at the output of the second digital filter 15 pass through a second energy detector 17.
  • a subtracter 18 is also provided at the output of the detectors 16, 17, so that the signals at the output of the second energy detector 17 are subtracted from the signals at the output of the first energy detector 16.
  • D OUT data signals or commands are provided at the output of the subtracter with a sequence composed of 1 and -1.
  • the high sensitivity demodulation stage HS 13 comprises a first DFT demodulator 24 for demodulating the sampled intermediate signals having a positive frequency deviation f (IF) + ⁇ f, and a second DFT demodulator 25 for demodulating the sampled intermediate signals having a zero or negative frequency deviation f (IF) - ⁇ f.
  • the two DFT demodulators perform a well-known sliding discrete Fourier transform with a reduced number of bands per unit in the 2 kHz frequency range for example.
  • the output signals of the second DFT demodulator 25 are subtracted in a subtractor 18 from the output signals of the first DFT demodulator 24 to provide D OUT data signals or commands.
  • the figure 4 represents a flowchart of the method of actuating the high-sensitivity FSK radiofrequency signal receiver according to the invention.
  • a first phase of the method consists in controlling the frequency of the intermediate signals following the frequency conversion in the FSK radiofrequency signal mixer by the oscillating signals. Following this control, a frequency correction can be imposed on the local oscillator to refocus the frequency of the intermediate signals before demodulating the high sensitivity data.
  • a first acquisition in step 30 of the FSK radiofrequency signals picked up by the receiver until the supply of the intermediate signals sampled on 2048 points is first performed over a period of the order of 1.26 ms.
  • the acquisition time can of course be set larger to allow a finer centering resolution.
  • a first discrete Fourier transform in step 31 is performed on the sampled intermediate signals to provide a first result of the transform normally to the selector, which stores this first result at time t n-2 .
  • the duration of operation of this discrete Fourier transform can be about 2.52 ms.
  • the DFT acquisition and processing process is repeated in a loop following a control in step 32
  • the first and second results of two discrete Fourier transforms, with a DFT acquisition and processing interval between the two results, are checked in the selector in step 32.
  • a comparison of the maximum amplitude peaks above a determined threshold following the two discrete Fourier transforms it is also used for this in the selector a search algorithm with n vectors, preferably 4 important vectors.
  • the spurious signals can be eliminated, to allow the selector to provide a control signal to the local oscillator in step 33 for correction of the frequency of the oscillating signals. If no amplitude peak above the determined threshold is detected, the DFT acquisition and processing process is repeated in steps 30 to 32.
  • step 34 demodulate the data in the high sensitivity demodulation stage.
  • the intermediate signals sampled at the frequency f (IF) + ⁇ f are filtered to provide first power signals P (f1) to the subtractor, and the intermediate signals sampled at the frequency f (IF). - ⁇ f for providing second power signals P (f2) to the subtracter. So a subtraction power signals are operated in step 35 to provide D OUT data signals.
  • step HS it is still possible following the demodulation step HS to perform a control on the power signals P (f1) and P (f2) in step 36.
  • the addition of these two signals of power P (f1) and P (f2) is greater than a defined threshold, it is determined the coherence of the data received in the radio frequency signals FSK in step 37.
  • the addition of the power signals is not greater than said defined threshold, a recovery of the initial frequency of oscillating signals of the local oscillator in step 38 is carried out before making a new acquisition of FSK radiofrequency signals in step 30.
  • the consistency of the data examined in step 37 essentially concerns the reliability of the modulated or non-modulated data picked up by the FSK radio frequency signal receiver, in order to eliminate any parasitic noise. If the consistency of the data is confirmed, a high sensitivity demodulation is again carried out in step 34. On the other hand, if there is no data coherence, a recovery of the initial frequency of the data is also performed. oscillation signals of the local oscillator in step 38 before making a new acquisition of FSK radio frequency signals in step 30.
  • FIG. 5a there is shown a simplified time chart of signals from a transmitter and signals picked up by the radio frequency signal receiver FSK according to the invention.
  • FIG. 5b there is shown a simplified graph of the power of the intermediate signals sampled in the frequency domain following at least two discrete Fourier transforms spaced in time.
  • a succession of acquisition phases defined by A and discrete Fourier transform defined by Tr for example sampled intermediate signals is carried out in the transmitter and the receiver.
  • the microprocessor of the transmitter controls the transmission by an antenna of the FSK radiofrequency signal transmitter.
  • the transmitter first transmits a 10-bit sequence at state "1" or having a well-defined frequency deviation known to the receiver, defined by S1 at a low bit rate, for example of the order of 1.5 kbit / s. . This corresponds to a duration of the order of 6.66 ms.
  • the receiver makes a first effective acquisition of part of this sequence, normally for a duration of the order of 1.26 ms or greater.
  • This acquisition at the sampled intermediate signals must correspond to signals at a frequency of f (IF) + ⁇ f.
  • a first discrete Fourier transform of these sampled intermediate signals is carried out after a duration of the order of 2.52 ms at time t n-2 . At this moment, the result of this first discrete Fourier transform is stored in the selector.
  • An intermediate acquisition and discrete Fourier transform phase in the receiver follows the first discrete Fourier transform.
  • a second effective acquisition of part of this second sequence S0 begins.
  • This second acquisition at the sampled intermediate signals must correspond to signals at a frequency of f (IF) - ⁇ f or f (IF).
  • a second discrete Fourier transform of these sampled intermediate signals is performed and stored in the receiver selector.
  • the transmitter operates an effective data transmission defined by T. term of this transmission of data, the transmitter returns to a phase for example of reception where there is a succession of acquisition phases and discrete Fourier transform, as for the receiver.
  • the selector operates a n-vector search algorithm and compares the two discrete Fourier transform results stored and spaced in addition to a time interval of an intermediate DFT acquisition and processing phase.
  • the algorithm seeks to identify two candidates separated from the double frequency deviation ⁇ f corresponding to the signaling phase. This makes it possible to greatly reduce the probability of erroneous centering caused by disturbing parasitic signals spaced by a frequency f p , and to select the amplitude peaks above the determined threshold resulting from good captured FSK radiofrequency signals. Based on the selected amplitude peaks, the selector transmits a control signal to the local oscillator to correct the frequency of the oscillating signals defined by C.
  • a high sensitivity demodulation operation defined by D can begin as represented by the signals on the top line of the receiver signals.
  • the frequency of the oscillating signals is restored as initially, which is defined by C '.
  • a new succession of acquisition and discrete Fourier transform phases takes place in the FSK radio frequency signal receiver.
  • the receiver after the phase of correction of the frequency of the oscillating signals of the local oscillator, a delay is taken on the detection of a preamble of the signals picked up. If no correct preamble is detected, after a certain time as shown on the signals of the lower line of the receiver signals, the initial frequency of the forward oscillating signals is restored. that a new succession of acquisition phases and discrete Fourier transform takes place in the radio frequency signal receiver FSK.
  • the receiver could also have been configured to allow transmission of modulated data signals as receiving receipt by the same antenna in a low rate mode. It can also be performed several acquisitions and discrete Fourier transforms before performing a correction of the frequency oscillating signals of the local oscillator. It can further be provided that the frequency error detected between the transmitter and the receiver is used at a higher level by a communication system, for example to facilitate searching in the presence of strong disturbers or for the purpose of synchronization.
  • the discrete Fourier transform can be performed in two frequency bands and in a multi-bit process. In place of a sigma delta synthesizer in the local oscillator, it can also be used a fractional N synthesizer or DDS.
EP10196893.1A 2010-12-23 2010-12-23 Récepteur de signaux radiofréquences FSK avec un démodulateur à haute sensibilité ainsi que procédé pour sa mise en action Active EP2469783B1 (fr)

Priority Applications (7)

Application Number Priority Date Filing Date Title
EP10196893.1A EP2469783B1 (fr) 2010-12-23 2010-12-23 Récepteur de signaux radiofréquences FSK avec un démodulateur à haute sensibilité ainsi que procédé pour sa mise en action
TW100146599A TWI513200B (zh) 2010-12-23 2011-12-15 具有高靈敏度解調器的頻移鍵控（ｆｓｋ）射頻訊號接收器以及作動其之方法
US13/331,720 US8774748B2 (en) 2010-12-23 2011-12-20 Receiver for FSK radio frequency signals with high sensitivity demodulator and method for activating the same
KR1020110141181A KR101299332B1 (ko) 2010-12-23 2011-12-23 고감도 복조기를 포함하는 ｆｓｋ 무선 주파수 신호용 수신기 및 이를 구동시키기 위한 방법
CN201110439404.7A CN102594752B (zh) 2010-12-23 2011-12-23 Fsk射频信号接收器及激活所述接收器的方法
JP2011282841A JP5497729B2 (ja) 2010-12-23 2011-12-26 高感度復調器を備えるｆｓｋ無線周波数信号用受信機およびその作動方法
HK13100605.2A HK1173579A1 (zh) 2010-12-23 2013-01-15 射頻信號接收器及激活所述接收器的方法

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
EP10196893.1A EP2469783B1 (fr) 2010-12-23 2010-12-23 Récepteur de signaux radiofréquences FSK avec un démodulateur à haute sensibilité ainsi que procédé pour sa mise en action

Publications (2)

Publication Number Publication Date
EP2469783A1 EP2469783A1 (fr) 2012-06-27
EP2469783B1 true EP2469783B1 (fr) 2017-12-13

Family

ID=43981416

Family Applications (1)

Application Number Title Priority Date Filing Date
EP10196893.1A Active EP2469783B1 (fr) 2010-12-23 2010-12-23 Récepteur de signaux radiofréquences FSK avec un démodulateur à haute sensibilité ainsi que procédé pour sa mise en action

Country Status (7)

Country Link
US (1) US8774748B2 (zh)
EP (1) EP2469783B1 (zh)
JP (1) JP5497729B2 (zh)
KR (1) KR101299332B1 (zh)
CN (1) CN102594752B (zh)
HK (1) HK1173579A1 (zh)
TW (1) TWI513200B (zh)

Families Citing this family (30)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP5988863B2 (ja) * 2012-12-27 2016-09-07 パナソニック株式会社 受信装置及び復調方法
JP6175985B2 (ja) * 2013-08-26 2017-08-09 アイコム株式会社 復調方法、受信装置、及び通信システム
JP6270107B2 (ja) * 2013-09-30 2018-01-31 日本信号株式会社 自動列車制御装置
DE102014104524B4 (de) 2013-10-02 2017-07-06 Silicon Laboratories Inc. Empfänger mit der Fähigkeit zur Erfassung von Frequenzabweichungen und Verfahren dafür
EP2869483B1 (en) 2013-11-01 2018-10-24 The Swatch Group Research and Development Ltd. Signal receiver with a duty-cycle controller
JP6382130B2 (ja) * 2014-02-26 2018-08-29 国立研究開発法人産業技術総合研究所 無線受信装置及び無線受信方法
JP5989703B2 (ja) * 2014-03-27 2016-09-07 古河電気工業株式会社 送受信システム
KR101531041B1 (ko) * 2014-10-23 2015-06-24 콘티넨탈 오토모티브 시스템 주식회사 광대역 주파수 복조방법 및 그 장치
EP3101856B1 (en) * 2015-06-03 2019-12-25 ABB Schweiz AG Method to demodulate a signal component from a sampled input signal and field bus device
EP3171193A1 (fr) * 2015-11-18 2017-05-24 The Swatch Group Research and Development Ltd. Procede de localisation d'une balise
EP3242146B1 (fr) * 2016-05-04 2019-11-13 The Swatch Group Research and Development Ltd. Procédé et systéme de communication de signaux à haute sensibilité et à démodulation synchrone
US10548131B2 (en) * 2016-11-02 2020-01-28 Qualcomm Incorporated Wireless communication between wideband eNB and narrowband UE
CN106487525B (zh) * 2016-11-03 2019-04-05 北京机械设备研究所 基于125KHz无线唤醒信号的远程唤醒系统和方法
KR101856756B1 (ko) * 2016-11-07 2018-05-10 한국표준과학연구원 신호 발생기 및 신호 발생기를 포함하는 측정 시스템
RU2625644C1 (ru) * 2016-11-14 2017-07-17 Федеральное государственное казенное военное образовательное учреждение высшего образования "Академия Федеральной службы охраны Российской Федерации" (Академия ФСО России) Способ динамического поиска подвижных абонентов на разнородных сетях связи
US10503122B2 (en) 2017-04-14 2019-12-10 Innophase, Inc. Time to digital converter with increased range and sensitivity
EP3632067B1 (en) * 2018-08-20 2023-10-25 Waviot Integrated Systems, LLC Method and system for receiving telemetry messages over rf channel
US10622959B2 (en) 2018-09-07 2020-04-14 Innophase Inc. Multi-stage LNA with reduced mutual coupling
US11095296B2 (en) 2018-09-07 2021-08-17 Innophase, Inc. Phase modulator having fractional sample interval timing skew for frequency control input
JP7316587B2 (ja) * 2018-11-15 2023-07-28 パナソニックＩｐマネジメント株式会社 光ディスク装置
CN110521127B (zh) * 2018-12-12 2021-07-27 深圳市汇顶科技股份有限公司 用于射频收发器中峰值自适应采样解调的系统和方法
US10728851B1 (en) 2019-01-07 2020-07-28 Innophase Inc. System and method for low-power wireless beacon monitor
US11070196B2 (en) 2019-01-07 2021-07-20 Innophase Inc. Using a multi-tone signal to tune a multi-stage low-noise amplifier
US10797921B2 (en) * 2019-02-12 2020-10-06 Texas Instruments Incorporated Threshold computation circuit for S-FSK receiver, integrated circuit, and method associated therewith
CN110611630B (zh) * 2019-08-09 2020-07-17 西安电子科技大学 一种调谐射频架构的2-fsk唤醒接收器及其解调方法
CN110519192A (zh) * 2019-08-23 2019-11-29 苏州浪潮智能科技有限公司 一种fsk信号解调方法、装置、嵌入式系统及存储介质
CN111614589B (zh) * 2020-04-16 2023-07-18 上海磐启微电子有限公司 三角调频信号调制器、解调器以及无线通信系统
US11775199B2 (en) * 2021-01-20 2023-10-03 Micron Technology, Inc. Voltage resonance mitigation of memory dies
US11750235B2 (en) 2021-06-24 2023-09-05 Analog Devices International Unlimited Company Radio frequency receiver circuit
CN115801030B (zh) * 2022-10-13 2023-09-26 成都老鹰信息技术有限公司 一种载波自动搜索系统及其搜索方法

Family Cites Families (19)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4518922A (en) * 1983-01-17 1985-05-21 Harris Corporation Decision-directed, automatic frequency control technique for non-coherently demodulated M-ARY frequency shift keying
GB8719849D0 (en) * 1987-08-21 1987-09-30 British Telecomm Fsk discriminator
JP2808954B2 (ja) * 1991-11-13 1998-10-08 国際電信電話株式会社 無変調信号検出及び周波数引き込み装置
JP2812347B2 (ja) * 1992-02-17 1998-10-22 日本電気株式会社 再同期復調装置
JP3161117B2 (ja) * 1993-01-14 2001-04-25 松下電器産業株式会社 受信装置
CA2153515A1 (en) * 1994-09-15 1996-03-16 Richard F. Austin Subcarrier multiple access passive optical network
GB2300502B (en) * 1995-04-11 1998-05-27 Int Mobile Satellite Org An electronic circuit for and a method of decoding a signal
GB9523578D0 (en) * 1995-11-17 1996-01-17 Philips Electronics Nv Demodulator
JPH1023086A (ja) * 1996-07-01 1998-01-23 Advantest Corp 変調精度測定装置
US5748036A (en) * 1996-07-30 1998-05-05 United Microelectronics Corporation Non-coherent digital FSK demodulator
US6690662B1 (en) * 1998-09-18 2004-02-10 Airnet Communications Corporation Method and apparatus employing wireless in-band signaling for downlink transmission of commands and uplink transmission of status for a wireless system repeater
AU2001284691B2 (en) * 2000-08-01 2005-09-22 Itron, Inc. Frequency hopping spread spectrum system with high sensitivity tracking and synchronization for frequency unstable signals
US6934524B2 (en) * 2002-04-25 2005-08-23 Agere Systems Inc. Fine-stage automatic frequency compensation in post-detection short-range wireless applications
JP4198484B2 (ja) * 2003-02-14 2008-12-17 旭化成エレクトロニクス株式会社 復調器および方法、受信装置
US7203254B2 (en) * 2003-03-25 2007-04-10 Motorola, Inc. Method and system for synchronizing in a frequency shift keying receiver
DE602004009800T2 (de) * 2004-09-30 2008-08-28 Sony Deutschland Gmbh Frequenzumtastungs-Demodulator und Verfahren zurFrequenzumtastung
CA2600925C (en) * 2005-03-08 2011-05-31 Applied Research Associates, Inc. Ultra-narrowband rf system
CN101303744A (zh) * 2008-04-18 2008-11-12 上海坤锐电子科技有限公司 用于射频识别系统的信号增强器芯片及其信号增强器
EP2239860B1 (fr) * 2009-04-07 2012-08-15 The Swatch Group Research and Development Ltd. Récepteur de signaux à modulation fsk à grande sensbilité à faible débit

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
None *

Also Published As

Publication number Publication date
TW201242267A (en) 2012-10-16
TWI513200B (zh) 2015-12-11
HK1173579A1 (zh) 2013-05-16
CN102594752B (zh) 2014-08-13
JP5497729B2 (ja) 2014-05-21
US8774748B2 (en) 2014-07-08
JP2012134981A (ja) 2012-07-12
KR101299332B1 (ko) 2013-08-26
KR20120072346A (ko) 2012-07-03
CN102594752A (zh) 2012-07-18
US20120164966A1 (en) 2012-06-28
EP2469783A1 (fr) 2012-06-27

Similar Documents

Publication Publication Date Title
EP2469783B1 (fr) Récepteur de signaux radiofréquences FSK avec un démodulateur à haute sensibilité ainsi que procédé pour sa mise en action
EP0580216B1 (fr) Système et récepteur de signaux à répartition multiplexée de fréquences orthogonales muni d'un dispositif de synchronisation de fréquences
EP3190711B1 (fr) Récepteur rf à poursuite de fréquence
WO1992010043A1 (fr) Procede de recalage des oscillateurs locaux d'un recepteur et dispositif pour la mise en ×uvre du procede
FR2770700A1 (fr) Dispositif et procede pour synchroniser des oscillateurs dans un systeme de communication de donnees
EP2445138B1 (fr) Unité de traitement de données, et récepteur de signaux comprenant l'unité de traitement de données
EP2239860A1 (fr) Récepteur de signaux à modulation FSK à grande sensbilité à faible débit
EP2922262B1 (fr) Circuit électronique à démodulateur synchrone d'un signal à modulation de phase
EP3242146B1 (fr) Procédé et systéme de communication de signaux à haute sensibilité et à démodulation synchrone
EP3301838A1 (fr) Procédé et système de determination d'une distance entre un objet portable et une station de base
FR2859336A1 (fr) Ameliorations se rapportant au traitement d'un signal code par saut de frequence
EP0274958B1 (fr) Dispositif de compensation dans un récepteur radiofréquence de l'effet Doppler produit par le mouvement relatif d'un récepteur par rapport à un émetteur accordé sur la même fréquence
EP1206045B1 (fr) Procédé de correction de l'erreur de frequence
EP3163758B1 (fr) Dispositif récepteur de signaux radiofréquence, procédé de réglage pour un tel dispositif et programme d'ordinateur correspondant
EP0790729B1 (fr) Dispositif de correction de bruit de phase dans un récepteur numérique
FR2811495A1 (fr) Procede et dipositif pour proteger une voie de transmission entre une unite de base et une unite mobile
FR2663177A1 (fr) Dispositif de recuperation d'une onde porteuse muni d'un moyen d'inhibition de faux accrochages en frequence.
EP4125247B1 (fr) Dispositif pour la compensation d'un décalage fréquentiel
EP1513310A1 (fr) Procédé et dispositif de correction du décalage fréquentiel de la fréquence porteuse d'un signal modulé avec une modulation monoporteuse continue en quadrature.
CA3110838A1 (fr) Procede de datation de signaux de telemesure
EP0309306B1 (fr) Procédé de détection de faux accrochages du signal référence sur le signal à démoduler en démodulation numérique cohérente et dispositif mettant en oeuvre un tel procédé
EP1583248A1 (fr) Récepteur radiofréquence multibande avec dispostif de réduction de consommation d'énergie
FR2846814A1 (fr) Ameliorations se rapportant a la reduction des interferences pour la reception sans fil et ameliorations se rapportant au traitement d'un signal code par saut de frequence
FR2846825A1 (fr) Ameliorations se rapportant au traitement d'un signal code par saut de frequence
JP4173048B2 (ja) 自動周波数制御装置

Legal Events

Date Code Title Description
AK Designated contracting states

Kind code of ref document: A1

Designated state(s): AL AT BE BG CH CY CZ DE DK EE ES FI FR GB GR HR HU IE IS IT LI LT LU LV MC MK MT NL NO PL PT RO RS SE SI SK SM TR

AX Request for extension of the european patent

Extension state: BA ME

PUAI Public reference made under article 153(3) epc to a published international application that has entered the european phase

Free format text: ORIGINAL CODE: 0009012

17P Request for examination filed

Effective date: 20130102

17Q First examination report despatched

Effective date: 20150515

GRAP Despatch of communication of intention to grant a patent

Free format text: ORIGINAL CODE: EPIDOSNIGR1

INTG Intention to grant announced

Effective date: 20170828

GRAS Grant fee paid

Free format text: ORIGINAL CODE: EPIDOSNIGR3

GRAA (expected) grant

Free format text: ORIGINAL CODE: 0009210

AK Designated contracting states

Kind code of ref document: B1

Designated state(s): AL AT BE BG CH CY CZ DE DK EE ES FI FR GB GR HR HU IE IS IT LI LT LU LV MC MK MT NL NO PL PT RO RS SE SI SK SM TR

REG Reference to a national code

Ref country code: GB

Ref legal event code: FG4D

Free format text: NOT ENGLISH

REG Reference to a national code

Ref country code: AT

Ref legal event code: REF

Ref document number: 955340

Country of ref document: AT

Kind code of ref document: T

Effective date: 20171215

Ref country code: CH

Ref legal event code: EP

Ref country code: CH

Ref legal event code: NV

Representative=s name: ICB INGENIEURS CONSEILS EN BREVETS SA, CH

REG Reference to a national code

Ref country code: IE

Ref legal event code: FG4D

Free format text: LANGUAGE OF EP DOCUMENT: FRENCH

REG Reference to a national code

Ref country code: DE

Ref legal event code: R096

Ref document number: 602010047309

Country of ref document: DE

REG Reference to a national code

Ref country code: FR

Ref legal event code: PLFP

Year of fee payment: 8

REG Reference to a national code

Ref country code: NL

Ref legal event code: MP

Effective date: 20171213

REG Reference to a national code

Ref country code: LT

Ref legal event code: MG4D

PG25 Lapsed in a contracting state [announced via postgrant information from national office to epo]

Ref country code: LT

Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT

Effective date: 20171213

Ref country code: FI

Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT

Effective date: 20171213

Ref country code: NO

Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT

Effective date: 20180313

Ref country code: SE

Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT

Effective date: 20171213

REG Reference to a national code

Ref country code: AT

Ref legal event code: MK05

Ref document number: 955340

Country of ref document: AT

Kind code of ref document: T

Effective date: 20171213

PG25 Lapsed in a contracting state [announced via postgrant information from national office to epo]

Ref country code: RS

Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT

Effective date: 20171213

Ref country code: BG

Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT

Effective date: 20180313

Ref country code: LV

Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT

Effective date: 20171213

Ref country code: GR

Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT

Effective date: 20180314

Ref country code: HR

Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT

Effective date: 20171213

PG25 Lapsed in a contracting state [announced via postgrant information from national office to epo]

Ref country code: NL

Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT

Effective date: 20171213

PG25 Lapsed in a contracting state [announced via postgrant information from national office to epo]

Ref country code: ES

Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT

Effective date: 20171213

Ref country code: CZ

Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT

Effective date: 20171213

Ref country code: SK

Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT

Effective date: 20171213

Ref country code: CY

Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT

Effective date: 20171213

Ref country code: EE

Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT

Effective date: 20171213

PG25 Lapsed in a contracting state [announced via postgrant information from national office to epo]

Ref country code: PL

Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT

Effective date: 20171213

Ref country code: IS

Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT

Effective date: 20180413

Ref country code: RO

Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT

Effective date: 20171213

Ref country code: AT

Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT

Effective date: 20171213

Ref country code: IT

Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT

Effective date: 20171213

Ref country code: SM

Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT

Effective date: 20171213

REG Reference to a national code

Ref country code: DE

Ref legal event code: R097

Ref document number: 602010047309

Country of ref document: DE

REG Reference to a national code

Ref country code: IE

Ref legal event code: MM4A

PG25 Lapsed in a contracting state [announced via postgrant information from national office to epo]

Ref country code: MC

Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT

Effective date: 20171213

Ref country code: MT

Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT

Effective date: 20171213

Ref country code: LU

Free format text: LAPSE BECAUSE OF NON-PAYMENT OF DUE FEES

Effective date: 20171223

REG Reference to a national code

Ref country code: BE

Ref legal event code: MM

Effective date: 20171231

PLBE No opposition filed within time limit

Free format text: ORIGINAL CODE: 0009261

STAA Information on the status of an ep patent application or granted ep patent

Free format text: STATUS: NO OPPOSITION FILED WITHIN TIME LIMIT

PG25 Lapsed in a contracting state [announced via postgrant information from national office to epo]

Ref country code: IE

Free format text: LAPSE BECAUSE OF NON-PAYMENT OF DUE FEES

Effective date: 20171223

26N No opposition filed

Effective date: 20180914

GBPC Gb: european patent ceased through non-payment of renewal fee

Effective date: 20180313

PG25 Lapsed in a contracting state [announced via postgrant information from national office to epo]

Ref country code: DK

Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT

Effective date: 20171213

Ref country code: BE

Free format text: LAPSE BECAUSE OF NON-PAYMENT OF DUE FEES

Effective date: 20171231

PG25 Lapsed in a contracting state [announced via postgrant information from national office to epo]

Ref country code: GB

Free format text: LAPSE BECAUSE OF NON-PAYMENT OF DUE FEES

Effective date: 20180313

Ref country code: SI

Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT

Effective date: 20171213

PG25 Lapsed in a contracting state [announced via postgrant information from national office to epo]

Ref country code: HU

Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT; INVALID AB INITIO

Effective date: 20101223

PG25 Lapsed in a contracting state [announced via postgrant information from national office to epo]

Ref country code: MK

Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT

Effective date: 20171213

PG25 Lapsed in a contracting state [announced via postgrant information from national office to epo]

Ref country code: TR

Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT

Effective date: 20171213

PG25 Lapsed in a contracting state [announced via postgrant information from national office to epo]

Ref country code: PT

Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT

Effective date: 20171213

PG25 Lapsed in a contracting state [announced via postgrant information from national office to epo]

Ref country code: AL

Free format text: LAPSE BECAUSE OF FAILURE TO SUBMIT A TRANSLATION OF THE DESCRIPTION OR TO PAY THE FEE WITHIN THE PRESCRIBED TIME-LIMIT

Effective date: 20171213

PGFP Annual fee paid to national office [announced via postgrant information from national office to epo]

Ref country code: CH

Payment date: 20230101

Year of fee payment: 13

P01 Opt-out of the competence of the unified patent court (upc) registered

Effective date: 20230615

PGFP Annual fee paid to national office [announced via postgrant information from national office to epo]

Ref country code: FR

Payment date: 20231122

Year of fee payment: 14

Ref country code: DE

Payment date: 20231121

Year of fee payment: 14

PGFP Annual fee paid to national office [announced via postgrant information from national office to epo]

Ref country code: CH

Payment date: 20240101

Year of fee payment: 14