EP2365584A1 - Antennenvorrichtung mit einer Planarantenne und einem Breitbandreflektor sowie ein Herstellungsverfahren des Reflektors - Google Patents

Antennenvorrichtung mit einer Planarantenne und einem Breitbandreflektor sowie ein Herstellungsverfahren des Reflektors Download PDF

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Publication number
EP2365584A1
EP2365584A1 EP11157387A EP11157387A EP2365584A1 EP 2365584 A1 EP2365584 A1 EP 2365584A1 EP 11157387 A EP11157387 A EP 11157387A EP 11157387 A EP11157387 A EP 11157387A EP 2365584 A1 EP2365584 A1 EP 2365584A1
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EP
European Patent Office
Prior art keywords
antenna
conductive patterns
plane
reflector
support
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Granted
Application number
EP11157387A
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English (en)
French (fr)
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EP2365584B1 (de
Inventor
Michaël Grelier
Stéphane Mallegol
Michel Jousset
Xavier Begaud
Anne Claire Lepage
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Thales SA
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Thales SA
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
    • H01Q9/04—Resonant antennas
    • H01Q9/16—Resonant antennas with feed intermediate between the extremities of the antenna, e.g. centre-fed dipole
    • H01Q9/26—Resonant antennas with feed intermediate between the extremities of the antenna, e.g. centre-fed dipole with folded element or elements, the folded parts being spaced apart a small fraction of operating wavelength
    • H01Q9/27—Spiral antennas
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/48—Earthing means; Earth screens; Counterpoises
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q15/00—Devices for reflection, refraction, diffraction or polarisation of waves radiated from an antenna, e.g. quasi-optical devices
    • H01Q15/0006—Devices acting selectively as reflecting surface, as diffracting or as refracting device, e.g. frequency filtering or angular spatial filtering devices
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q15/00—Devices for reflection, refraction, diffraction or polarisation of waves radiated from an antenna, e.g. quasi-optical devices
    • H01Q15/14—Reflecting surfaces; Equivalent structures
    • H01Q15/148—Reflecting surfaces; Equivalent structures with means for varying the reflecting properties
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q19/00—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic
    • H01Q19/10—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using reflecting surfaces
    • H01Q19/104—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using reflecting surfaces using a substantially flat reflector for deflecting the radiated beam, e.g. periscopic antennas

Definitions

  • the invention applies to the field of planar antennas for very broadband telecommunication systems. It relates to an antenna reflector with artificial magnetic conductive type structure for a planar antenna. The invention also relates to an antenna device comprising a planar antenna and an antenna reflector, as well as a method of designing the antenna reflector.
  • the antennas must have a wide operating frequency band, for example of the order of the decade, that is to say a frequency band whose maximum frequency is at least ten times the minimum frequency.
  • the flat antennas, in particular the spiral antennas form part of these broadband antennas.
  • a spiral antenna generally consists of a dielectric support on which is etched a radiating element.
  • the radiating element comprises at least two spirally wound strands and the inner ends of which are supplied with current. Depending on the number of strands and the phase of the current in each strand, the electromagnetic radiation of the spiral antenna is different.
  • the width of the frequency band depends on the inner and outer diameters of the spiral.
  • a plane antenna has a symmetrical structure and thus radiates throughout the space, in particular in the two directions orthogonal to the plane of the antenna.
  • the planar antenna must necessarily include a support, at least to stiffen the antenna and power it. However, this generates disturbances related to the so-called rear radiation of the antenna.
  • the support can absorb some of the back radiation, thus leading to power losses.
  • the support may also reflect a portion of the back radiation, but interfering with radiation emitted in the opposite direction, referred to as forward radiation.
  • the medium can induce current and itself generate parasitic radiation, thus reducing the frequency band of operation.
  • An ideal support would be a support which absorbs nothing of the radiation received, but which reflects them integrally in phase over the whole width of the frequency band, and which does not generate parasitic radiation by induction. It would also have a minimum footprint, the implantation volume is thus limited.
  • a first solution aims to maximize the absorption of the back radiation by the support in order to reduce the radiation reflected in phase shift with the forward radiation.
  • the support then comprises a cavity made of an absorbent material, for example based on carbon or iron powder.
  • the overall size being a function of the depth of the cavity, it can be placed just behind the antenna.
  • the absorbing material also has the advantage of not inducing current and thus not generating parasitic radiation.
  • the power losses are important since all the back radiation is untapped.
  • the absorbent properties of a material depend on the frequency of the radiation.
  • the back radiation can not be absorbed over the entire operating frequency band.
  • the absorptive cavity supports are difficult to reproduce insofar as the electromagnetic properties vary from one sample of material to another.
  • the weight and the volume of the support increase rapidly when the frequency of the radiation to be absorbed decreases.
  • a second solution is to maximize the reflection of the back radiation, ensuring that the reflection is in phase.
  • a conductive plane having optimum reflection properties is disposed at a distance from the antenna equal to one quarter of the average wavelength of the radiation that it emits or receives. At such a distance, the reflected back radiation is in phase with the forward radiation.
  • the main disadvantage of this solution is that the distance can be optimally adjusted only for a single wavelength. The radiation emitted or received at wavelengths distant from this average wavelength may therefore be disturbed, effectively limiting the bandwidth of the antenna.
  • Another disadvantage of this solution is that a quarter of the wavelength quickly represents a distance important for the low frequencies, which generates an overall thickness for the relatively large antenna.
  • the conductive plane has important induction properties and reflection and diffraction phenomena occur at the edge of the antenna, thus generating parasitic radiation.
  • a CMA structure for Artificial Magnetic Conductor, is disposed under the plane of the antenna on the side of the rear radiation, so as to form an antenna reflector.
  • a conventional CMA structure comprises a dielectric support, electrical conductive patterns periodically disposed on a first surface of the dielectric support and a uniform electrical conductive plane (ground plane) on a second surface of the dielectric support. Each conductive pattern can be connected to the ground plane by vias, generally called “vias" in the Anglo-Saxon literature.
  • a CMA structure has the property of reflecting the electromagnetic waves in phase, which involves positioning it as close to the antenna as possible and which makes it possible to reduce the thickness of the antenna device comprising the antenna and the CMA structure.
  • a CMA structure may also have the property of prohibiting the propagation of electromagnetic waves in certain directions of the plane in which the conductive patterns are arranged, which prevents generating parasitic radiation. This is called electromagnetic band gap (EIB) structure.
  • EIB electromagnetic band gap
  • the properties of a BIE or CMA type structure occur only in a certain frequency band, called either BIE band or CMA band depending on the case considered. This frequency band, in particular its central frequency and its low and high cutoff frequencies, depend on the shape and dimensions of the conductive patterns, as well as the thickness of the dielectric support of the structure.
  • the bandwidth is very small, that is to say very much smaller than the octave, whether we consider the BIE band or the CMA band.
  • the congestion constraints make the current antennas having a BIE or CMA structure reflector do not make it possible to operate over a wide frequency band, greater than the decade.
  • An area where the electromagnetic radiation has the greatest amplitude can be determined from a predetermined threshold value, for example substantially equal to 25% of the maximum amplitude.
  • the invention also relates to an antenna reflector for a plane antenna and an antenna device comprising a plane antenna and an antenna reflector.
  • the planar antenna is adapted to be mounted on the antenna reflector so that the surface of the antenna support is substantially parallel to the surface of the ground plane, and the shape and dimensions of the conductive patterns are determined from so that each set locally forms a high impedance surface at the frequency radiated locally by the planar antenna.
  • the invention has the particular advantage that it makes it possible to extend the properties of a CMA structure to a wide frequency band, the band of interest of a reflector according to the invention being formed by an assembly of operating bands. in CMA mode.
  • the figure 1 represents an example of an antenna device.
  • the antenna device 1 comprises a spiral antenna 2 and an antenna reflector 3.
  • the spiral antenna 2 comprises a dielectric support 21 and two electrically conductive strands 22a and 22b of identical length and mutually wound around a central point O to form a spiral 23.
  • the strands 22a and 22b form the radiating elements of the spiral antenna 2.
  • the first strand 22a extends between an inner end B and an outer end D of the spiral 23.
  • the second strand 22b is extends between an inner end A and an outer end C of the spiral 23.
  • the spiral antenna 2 also comprises means for supplying the radiating elements, not shown.
  • the two strands 22a and 22b are powered by microwave signals in phase opposition at their inner ends A and B.
  • the dielectric support 21 is for example a printed circuit epoxy plate. It comprises an upper surface 24 and a lower surface 25 substantially flat and parallel.
  • the strands 22a and 22b can be fixed, printed or etched on the upper surface 24.
  • the antenna reflector 3 comprises a dielectric support 31, a ground plane 32 and sets of patterns Conductors 33.
  • the dielectric support 31 may also be an epoxy plate of the printed circuit type. It comprises an upper surface 34 and a lower surface 35 substantially flat and parallel.
  • the ground plane 32 and the conductive patterns 33 may for example be fixed, printed or etched on the lower surface 35 and the upper surface 34, respectively. In particular, any conventional technique for producing printed circuits can be used to produce the conductive patterns 33.
  • Each conductive pattern 33 can be electrically connected to the ground plane 32, for example via metallized holes, not shown, made in the dielectric support 31.
  • the spiral antenna 2 is mounted on the antenna reflector 3, the lower surface 25 of the dielectric support 21 of the spiral antenna 2 coming opposite the upper surface 34 of the dielectric support 31 of the antenna reflector 3.
  • the dielectric support 21 can bear directly on the conductive patterns 33.
  • the dielectric support 21 then performs an isolation function between the spiral antenna 2 and the antenna reflector 3. This insulation may nevertheless be provided by any other means.
  • the invention applies equally well to any type of plane antenna in general, and to any type of spiral antenna in particular. It applies in particular to equiangular spiral antennas, also called logarithmic spiral antennas, in which the width of the strands and the spacing between the strands increase as they move away from the center.
  • the wired antenna of the figure 1 has two electrically conductive strands.
  • the invention also applies to planar antennas comprising a different number of strands but also to other types of geometry such as the sinuous antenna.
  • the invention uses the operating properties of planar antennas.
  • the radiating element of such an antenna when excited, emits electromagnetic waves from a localized operating zone, related to the relative arrangement of the strands and the phase shift of the current flowing in the different strands.
  • This operating zone has the particularity of varying according to the frequency according to a law specific to each type of plane antenna.
  • the invention therefore uses the operating properties of planar antennas to adapt the structures based on artificial magnetic conductor (AMC) to local electromagnetic radiation.
  • AMC artificial magnetic conductor
  • the conductive patterns no longer have a periodic regular arrangement, but their geometric shape and their dimensions vary between different operating areas.
  • the geometric shape and the dimensions of the conductive patterns are determined for each operating zone so as to form in said zone a high impedance surface at the corresponding frequency.
  • R Z s - not Z s + not where n is the wave impedance.
  • the figure 2 illustrates possible steps of the method of designing an antenna reflector according to the invention for a planar antenna.
  • a spiral antenna like the one shown in FIG. figure 1 .
  • the method nevertheless applies to any type of plane antenna.
  • a first step 101 the radiation emitted by the spiral antenna 2 alone, that is to say without antenna reflector, is characterized. More precisely, amplitude and phase field distributions of the electromagnetic radiation emitted by the spiral antenna 2 are determined in the near-field zone in a plane substantially parallel to the plane of the spiral antenna 2.
  • the amplitude distributions are determined successively for at least two frequencies belonging to the operating frequency band of the spiral antenna 2.
  • the strands 22a and 22b of the spiral antenna 2 are fed at their inner ends A and B by currents with the same amplitudes, generally presenting a difference in phase of 180 °.
  • the electromagnetic radiation emitted by a spiral antenna has a maximum amplitude in a zone resembling a circular ring whose central diameter is the aforementioned diameter.
  • the Figures 3a and 3b represent the amplitude distribution of the electromagnetic radiation emitted by the spiral antenna 2 at a given operating frequency in a plane belonging to the near-field area parallel to the plane of the spiral antenna 2.
  • the rings 301 and 307, 302 and 305, 303, 304, and 306 have amplitudes equal to 3.10 -3 J / m 3 , 3.10 -6 J / m 3, 6.10 -6 J / m 3 , 5.10 -6, respectively. j / M 3 and 1.5.10 -6 J / m 3 .
  • the circular ring 301 thus corresponds to the zone where the electromagnetic radiation has a maximum amplitude at the given operating frequency.
  • the figure 3b represents the amplitude distribution of the electromagnetic radiation as a function of the distance, projected on the plane of the antenna, from the center O of the spiral 23.
  • the amplitude distribution is represented on the Figures 3a and 3b as a quantity of energy radiated per cubic meter (J / m 3 ).
  • any other magnitude can be used as long as it makes it possible to determine the power of the radiation distributed in a plane close to the spiral antenna 2. From this amplitude distribution, it is possible to determine the zone where the radiation at the highest amplitude, called the operating zone 310.
  • the operating zone may be defined by a minimum radius R min and a maximum radius R max corresponding to an amplitude threshold value S predetermined.
  • the value of the threshold S is chosen to be substantially equal to 25% of the maximum amplitude of the electromagnetic radiation, this value proving to give good results.
  • the operating zone is determined for at least two frequencies belonging to the operating frequency band of the spiral antenna. After determining the amplitude distribution of the radiation at a given first frequency, one or more amplitude distributions are determined at another or other given operating frequencies.
  • a second step 102 for each amplitude distribution, that is to say for each given operating frequency or for each operating zone, the shape and dimensions of a set of conductive patterns 33 are determined when they are arranged in the vicinity of the operating zone in question, the conductive patterns 33 of this set locally form a high impedance surface at the operating frequency considered.
  • each operating zone at a given frequency is opposite the high impedance surface at said frequency formed by the antenna.
  • corresponding set of conductive patterns 33 On the figure 1 two sets 331 and 332 of conductive patterns 33 are shown.
  • the shape and dimensions of the conductive patterns 33 of an assembly can be determined as soon as the operating zone at the frequency in question is determined. In other words, the order of the first and second steps of the process is of importance only with respect to a particular operating frequency.
  • the second step 102 may for example be performed by the following substeps.
  • a first sub-step conventional CMA structures are considered, that is to say whose conductive patterns are rectangles arranged in a regular matrix, therefore periodic, whose thickness of the dielectric support is substantially equal to that of the support dielectric 31 of the antenna reflector 3 according to the invention.
  • the dimensions (length and width) of the conductive patterns of the conventional CMA structure for forming a high impedance surface are determined. in the vicinity of the operating frequency considered.
  • the conductive patterns of the conventional CMA structures are conformed to the corresponding operating zone of the spiral antenna, each conductive pattern retaining substantially the same surface as that considered for the conventional topology. .
  • the conductive patterns therefore take an annular shape.
  • the figure 4 illustrates the result of this substep.
  • An assembly 333 of conductive patterns 33 is arranged at an annular periodicity on the upper surface 34 of the dielectric support 31 and covers the considered operating zone of the spiral antenna 2.
  • the figure 5 represents an example of such a phase diagram.
  • each operating frequency is associated, on the one hand, an operating zone, for example defined by a radius of the spiral antenna 2 and, on the other hand, a phase diagram of a set of corresponding conductive patterns 33. to a classic CMA structure.
  • a fourth sub-step we choose, from the phase diagram of the figure 5 at least two sets of conductive patterns 33 so as to cover the different operating zones of the spiral antenna 2 without overlapping the conductive patterns 33 between the different sets.
  • the arrangement of sets of conductive patterns may be substantially modified to avoid overlaps.
  • the conductive patterns 33 are arranged not in a periodic but pseudoperiodic manner.
  • the figure 6 represents, in top view, an example of antenna reflector 3 according to the invention adapted to a spiral antenna.
  • the antenna reflector 3 comprises five sets 331 to 335 of conductive patterns 33 whose surfaces are larger and larger as one moves away from the center of the antenna reflector 3. Each set 331 to 335 forms a high impedance surface at the frequency radiated locally by the spiral antenna. The high impedance character can thus be maintained over the entire surface of the antenna reflector 3, and therefore over the entire operating frequency band of the spiral antenna. Due to the evolution of the dimensions of the conductive patterns 33 of the different assemblies, the antenna reflector 3 can be called an artificial magnetic quasi-conductive structure.

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  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Aerials With Secondary Devices (AREA)
  • Variable-Direction Aerials And Aerial Arrays (AREA)
EP11157387.9A 2010-03-09 2011-03-08 Antennenvorrichtung mit einer Planarantenne und einem Breitbandreflektor sowie ein Herstellungsverfahren des Reflektors Active EP2365584B1 (de)

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
FR1000943A FR2957462B1 (fr) 2010-03-09 2010-03-09 Dispositif d'antenne comportant une antenne plane et un reflecteur d'antenne large bande et procede de realisation du reflecteur d'antenne

Publications (2)

Publication Number Publication Date
EP2365584A1 true EP2365584A1 (de) 2011-09-14
EP2365584B1 EP2365584B1 (de) 2018-07-11

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EP (1) EP2365584B1 (de)
ES (1) ES2687170T3 (de)
FR (1) FR2957462B1 (de)

Cited By (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20130249762A1 (en) * 2010-10-01 2013-09-26 Thales Broadband antenna reflector for a circular-polarized planar wire antenna and method for producing said antenna reflector
CN110199436A (zh) * 2016-08-29 2019-09-03 阿瑞利斯控股有限公司 多频带圆偏振天线
CN113675594A (zh) * 2021-07-06 2021-11-19 北京交通大学 一种高效率漏波天线

Families Citing this family (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN109904619B (zh) * 2019-01-25 2021-06-11 东南大学 平面等角螺旋线型宽带频率选择表面
CN116666990B (zh) * 2023-07-26 2023-10-31 南京理工大学 可重构超表面吸波器的特征模式设计方法及超表面吸波器

Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4905014A (en) * 1988-04-05 1990-02-27 Malibu Research Associates, Inc. Microwave phasing structures for electromagnetically emulating reflective surfaces and focusing elements of selected geometry
JP2007096868A (ja) * 2005-09-29 2007-04-12 Mitsubishi Electric Corp 反射板および該反射板を備えたリフレクタアンテナ
US20090079637A1 (en) * 2007-09-26 2009-03-26 Nippon Soken, Inc. Antenna apparatus for radio communication
FR2922687A1 (fr) * 2007-10-23 2009-04-24 Thales Sa Antenne compacte a large bande.

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4905014A (en) * 1988-04-05 1990-02-27 Malibu Research Associates, Inc. Microwave phasing structures for electromagnetically emulating reflective surfaces and focusing elements of selected geometry
JP2007096868A (ja) * 2005-09-29 2007-04-12 Mitsubishi Electric Corp 反射板および該反射板を備えたリフレクタアンテナ
US20090079637A1 (en) * 2007-09-26 2009-03-26 Nippon Soken, Inc. Antenna apparatus for radio communication
FR2922687A1 (fr) * 2007-10-23 2009-04-24 Thales Sa Antenne compacte a large bande.

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
HE X ET AL: "A broadband compound printed air-fed array antenna", METAMATERIALS, 2008 INTERNATIONAL WORKSHOP ON, IEEE, PISCATAWAY, NJ, USA, 9 November 2008 (2008-11-09), pages 263 - 266, XP031378593, ISBN: 978-1-4244-2608-9 *

Cited By (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20130249762A1 (en) * 2010-10-01 2013-09-26 Thales Broadband antenna reflector for a circular-polarized planar wire antenna and method for producing said antenna reflector
US9755317B2 (en) * 2010-10-01 2017-09-05 Thales Broadband antenna reflector for a circular-polarized planar wire antenna and method for producing said antenna reflector
CN110199436A (zh) * 2016-08-29 2019-09-03 阿瑞利斯控股有限公司 多频带圆偏振天线
CN110199436B (zh) * 2016-08-29 2022-05-27 阿瑞利斯控股有限公司 多频带圆偏振天线
CN113675594A (zh) * 2021-07-06 2021-11-19 北京交通大学 一种高效率漏波天线

Also Published As

Publication number Publication date
FR2957462B1 (fr) 2015-06-26
EP2365584B1 (de) 2018-07-11
FR2957462A1 (fr) 2011-09-16
ES2687170T3 (es) 2018-10-24

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