Classifications

• • H—ELECTRICITY
  • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
  • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
  • H02M3/00—Conversion of dc power input into dc power output
  • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
  • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
  • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
  • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
  • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
• • H—ELECTRICITY
  • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
  • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
  • H02M1/00—Details of apparatus for conversion
  • H02M1/36—Means for starting or stopping converters

Definitions

• the present invention relates to a voltage booster circuit.
• a particularly interesting application of the invention lies in the field of DCDC 12V / 42V DC / DC power converters fed by the on-board network of a motor vehicle (battery voltage of 12V) and supplying power to the bridges. of power for the control of the current of electrical machines with variable inductance.
• DCDC converters 12V / 42V are thus often used as voltage source for H-bridges, also called single-phase or multiphase "four-quadrant" bridges. These bridges are used in particular to control the electromagnetic valve actuator current ("camless" system in English).
• Such a DCDC converter is made using a voltage booster circuit.
• An example of a voltage booster circuit 1, also referred to as a "Boost" type circuit, is illustrated in FIG.
• Circuit 1 comprises
• a voltage source 2 such that the voltage of the battery of a motor vehicle having a first and a second terminal (here a + and ground terminal), an inductor 3 whose first terminal is connected to the + terminal of the voltage source 2,
• a current switch 6 such as a MOSFET field effect transistor connected between the second terminal of the inductor 3 and the ground
• a second current switch 7 (which may be a MOSFET transistor or an electromechanical component of the relay type) connected between the + terminal of the voltage source 2 and the first terminal of the inductor 3 (it will be noted that this second switch can also be connected between the second terminal of the capacitor 5 and the ground).
• the operation of the "Boost" circuit 1 can be divided into two distinct phases according to the state of the switch 6: a phase of accumulation of energy: when the switch 6 is closed (on state), this causes the increase of the current in the inductance 3 and thus the storage of a quantity of energy in the form of magnetic energy.
• the diode 4 is then blocked and the capacitor 5 is disconnected from the power supply.
• the switch 6 is open, the inductor 3 is then in series with the generator and its f.e.m. (electromotive force) is added to that of the generator (booster effect).
• the current flowing through the inductor then passes through the diode 4 and the capacitor 5. This results in a transfer of the energy accumulated in the inductor 3 to the capacitor 5.
• the chemical capacitors have the disadvantage of generating large leakage currents which can be troublesome in an application. particularly powered by the battery of a motor vehicle. Leakage currents can cause a deep discharge of the battery, if the device stays off for a long time. This is the case for example of a converter connected to the 12V battery of a vehicle in "parking" mode. It may then be necessary to disconnect the capacitors to reduce the leakage currents.
• an electromagnetic valve system requires a converter to generate not only a power supply network adapted to the valve actuators, in this case it is a 42V network, from the onboard network, but also and especially for decoupling the 12V edge network from the 42V auxiliary network.
• control of the actuators generates a very low frequency of harmonic frequency.
• a capacitive bank of high value is therefore necessary, which has leakage currents incompatible with the specifications in "parking" mode.
• a known solution to solve this problem related to leakage currents is to use a switch 7 for disconnecting these capacitors.
• opening the switch in "parking" mode avoids any current leakage and therefore any risk of battery discharge.
• Circuit 1 can not control the current when the output voltage is lower than the input voltage. This case is encountered at each power-up (closing of the switch 7) when the output voltage Vs is zero because the capacitor tank 5 is discharged. The charge of the capacitor 5 generates a current that is not controllable by the circuit 1. The current draw is limited only by the line resistors. The charging time is defined by the size of the capacitors and these line resistors. Upon power-up, the output capacitor 5 is suddenly charged until the output voltage reaches an equilibrium value close to the input voltage.
• the inrush current can reach values that exceed the specifications of the components traversed by this current, in particular those of the switch 7 which allows the powering up.
• the current draw causes the destruction or wear of the contacts under the effect of the electric arc.
• the arc can cause the melting of the metals in contact and emit projections.
• the current draw can cause its destruction or premature aging by violent local heating, especially when the component has a low heat capacity.
• the inrush current can further cause other inconveniences such as the collapse of the voltage source if the internal resistance thereof is too great. Note that, even if there is no power switch 7, can be transposed the same disadvantages on any other switch on the loop through the inrush current.
• FIG. 2 A first example of a limiting circuit 10 is illustrated in FIG. 2.
• the circuit 10 is identical to the circuit 1 of FIG. 1 (the common components have the same reference numerals) with the difference that it comprises a transistor 8 mounted in series between the second terminal of the capacitor 5 and the ground.
• This transistor 8 may be a bipolar transistor or a field effect transistor of the MOSFET or JFET type.
• the solution is to control the charging current of the capacitor 5 by an operation in linear mode of the transistor 8.
• This transistor can also have the function of switch (saturated mode) to isolate or connect the capacitor 5 to ground after the limitation has been activated. For high capacitance values, the number of transistors can be large, especially if the delay given to the pre-charge is short.
• the circuit 20 is identical to the circuit 1 of FIG. 1 (the common components have the same reference numbers) except that it comprises a switch 9 connected in series between the second terminal of the capacitor 5 and the ground as well as a resistor 11 connected in parallel with the switch 9. The inrush current is then limited by the resistor 11.
• the switch 9 is used to isolate or connect the capacitor to ground.
• the delay to start ie the time between the moment when the driver turns the ignition key and the moment when the system must be ready
• a relatively short delay of the order of 300 ms in total.
• many other actions other than the precharging of the capacitor must be performed (diagnosis, reset, powering up, etc.): therefore, there is little time reserved for preloading The capacitor 5.
• One or other of the solutions of Figures 2 or 3 have the disadvantage of limiting the current by heat dissipation.
• the present invention aims to provide a voltage booster circuit economically to achieve a rapid pre-charge of the capacitive element while reducing the space occupied by the components forming said circuit.
• the invention proposes a voltage booster circuit comprising:
• a voltage source comprising a first and a second terminal, at least one inductor whose first terminal is connected to said first terminal of said voltage source,
• At least one capacitor whose first terminal is connected to the cathode of said diode
• At least one current switch connected between said second terminal of said inductor and said second terminal of said voltage source
• Capacitor means any type of capacitive load: it may be a single capacitor but also a capacitive bank having a plurality of capacitors connected in series or in parallel.
• inductance covers a single inductance but also a plurality of inductors connected in series or in parallel.
• the proposed configuration has the advantage of not limiting the current by heat dissipation by using a structure that allows the current control.
• the addition of means to allow the current to flow from the second terminal of the capacitor (its negative pole in the case of a chemical capacitor) to the first terminal of the voltage source (the positive terminal of the battery in the case of 'a battery power supply of the vehicle) allows control of the load current of the capacitive bank.
• These means are for example formed by a diode.
• this solution does not dissipate additional heat unlike a limiting resistor or transistor current control in linear mode.
• the circuit according to the invention eliminates the use of power components inducing significant additional cost.
• this configuration does not change the operation of the voltage booster and allows the load current to be controlled by a conventional PWM regardless of the state of charge of the capacitive bank.
• the second switch disconnects (and reconnects) the capacitive element from the ground.
• the system according to the invention may also have one or more of the features below, considered individually or in any technically possible combination.
• said means for allowing the current to flow from said second terminal of said capacitor to said first terminal of said voltage source are formed by a se- a diode condode whose anode is connected to said second terminal of said capacitor and the cathode is connected to said first terminal of said voltage source.
• the invention finds a particularly advantageous application in the case where said at least one capacitor is a chemical capacitor.
• the circuit according to the invention comprises a second capacitor connected between the anode of said at least one diode and said second terminal of said voltage source.
• the circuit according to the invention comprises:
• n inductances Lbi with i varying from 1 to n and n being a natural integer greater than or equal to 2, each of the inductors Lbi having its first terminal connected to said first terminal of said voltage source, - N diodes Dbi, with i varying from 1 to n, each of the diodes Dbi having its anode connected to the second terminal of said inductor Lbi,
• n current switches Mbi with i varying from 1 to n, each of the switches Mbi being connected between said second terminal of said inductor Lbi and said second terminal of said voltage source and each of the switches Mbi being controlled so that it is conducting while the other switches are open, said at least one capacitor having its first terminal connected to the cathode of each of said diodes Dbi.
• said voltage source is formed by the battery of a motor vehicle.
• the circuit according to the invention ensures the conversion of a DC voltage of 12V into a DC voltage of 42V.
• the subject of the present invention is also the use of the circuit according to the invention for supplying an H-bridge for the control of the current in an electrical control device, the voltage at the terminals of the at least one capacitor forming the voltage of the 'food.
• the electrical member is included in an actuator provided with an actuated part, said electrical member controlling said actuated part in displacement.
• said actuator is an actuator for electromagnetic valves.
• FIG. 1 is a schematic representation of the electronic structure of a voltage booster circuit illustrating the state of the art
• FIG. 2 and 3 each illustrate a voltage booster circuit incorporating a current limiting circuit according to the state of the art
• FIG. 4 represents a voltage booster circuit according to the invention
• FIGS. 5 and 6 illustrate the current limiter operation of the voltage booster circuit according to the invention as represented in FIG. 4;
• FIG. 7 represents the evolution of the potential Vs as a function of time during the pre-charge phase of the capacitor;
• FIG. 8 represents a voltage booster circuit according to a second embodiment of the invention.
• FIG. 9 represents a voltage booster circuit according to a third embodiment of the invention.
• Figure 4 shows a circuit voltage elevator 100 -according to the invention
• the circuit 100 comprises.:
• a source of voltage S such that the voltage of the battery of a motor vehicle having a first and a second terminal (here a terminal + BAT and ground) delivering an input voltage Ve, an inductance Lb whose first terminal is connected to the terminal + BAT of the voltage source S,
• a diode Db whose anode is connected to the second terminal of the inductor 3; a capacitor Cb of the chemical capacitor type, whose first terminal (positive pole) is connected to the cathode of the diode Db (note that this capacitor Cb is generally not only and is often formed by a capacitive bank),
• a current switch Mb such as a MOSFET field effect transistor connected between the second terminal of the inductance Lb and the ground
• a second current switch M (which may be a MOSFET transistor or an electromechanical component of the relay type) connected between the second terminal (negative pole) of the capacitor Cb and the ground,
• the switch Mb is controlled by a PWM type control having a duty cycle ⁇ with a switching period T.
• the switch M When pre-charging the capacitor Cb with inrush current limiting, the switch M is open so that the second terminal (negative pole) of the capacitor Cb is not connected to ground but to the battery .
• this solution does not dissipate additional heat unlike a limiting resistor or transistor current control in linear mode.
• the switch M is open to obtain a pre-charge without inrush current (i.e. with controlled current) of the capacitor Cb.
• Vc across the capacitor Cb is equal to Ve (or slightly higher to avoid any inrush current)
• the potential Vs (potential of the point S corresponding to the positive pole of the capacitor Cb with respect to the ground) is not continuous during the pre-charge phase of the capacitor Cb.
• FIG. 7 illustrates this phenomenon by representing the voltage Vs as a function of time.
• the potential Vs is cut (chopped) at the frequency of the MLI (of the order of 70 kHz in the case of the application relating to the electromagnetic valves).
• the switch Mb leads, diodes Db and D are blocked which sets the potential Vs at a voltage that varies between 0 and Vc.
• the diodes Db and D conduct which sets the potential Vs to Ve + Vfd + Vc where Vfd represents the voltage drop across the diode D.
• FIG. 8 thus represents a voltage booster circuit 200 according to a second embodiment of the invention making it possible to overcome the problem of discontinuity of Vs.
• the circuit 200 is identical to the circuit 100 of FIG. 4 with the difference that it comprises an additional capacitor C connected between the anode of the diode Db and the ground. The value of the voltage across this capacitor is therefore equal to the value of the potential Vs.
• This capacitor C is a capacitor with a low leakage current and a low value (capacitors of the "film” or ceramic type of small capacity can be used).
• the capacitor C is connected between the ground and the output S to maintain the potential Vs when the switch Mb leads. This capacitor C is permanently connected so it is initially charged to the battery voltage (at near voltage drops).
• the switch Mb leads, the potential Vs is maintained at the load voltage of the capacitor C.
• the capacitor C supplies the current of a possible load connected to the output.
• the switch Mb is open, the diodes Db and D conduct and the current charges not only this capacitor C but also the capacitive bank Cb.
• the voltage across C follows the voltage imposed by the capacitive bank Cb. Their sizing obviously depends on the load connected at the output during startup.
• FIG. 9 represents a voltage booster circuit 300 according to a third embodiment of the invention also making it possible to overcome the Vs discontinuity problem.
• the circuit 300 is a multicell circuit; in other words, this circuit 300 comprises n cells each constituted by a triplet (Lbi, Dbi, Mbi) of inductance-diode-switch (with i varying from 1 to n, n being a natural integer greater than 1) .
• n is equal to 2.
• Each of the inductors Lbi has its first terminal connected to the terminal
• Each of the diodes Dbi has its anode connected to the second terminal of the inductor Lbi.
• Each of the switches Mbi is connected between the second terminal of the inductor Lbi and the ground.
• the capacitor Cb to be pre-charged has its first terminal (positive pole) connected to the cathode of each of the diodes Dbi.
• the circuit 300 comprises:
• the advantage of a multicellular configuration with respect to a single cell is that it makes it possible to reduce the current ripple considerably (to obtain an identical ripple with a single-cell system, it would be necessary to have an inductance having a very large value) and to distribute the power.
• the phase shift between the cells makes it possible to guarantee that at least one of the diodes Dbi is conducting at each instant. Therefore, the potential Vs is maintained at the value at Ve + Vfd + Vc where Vfd represents the potential drop across the diode D.
• the switch Mb1 is closed (therefore the switch Mb2 is open) and the diode Db2 is conductive.
• the respectively hatched and bold arrows indicate the two possible paths of the current depending on whether one is in the magnetization phase of the inductance Lb 1 or pre-charge of the capacitor Cb.
• the invention has been more particularly described in the case of using a diode for connecting the foot of the capacitor to the + BAT terminal but other means allowing the current to flow from the second terminal of the capacitor to the + BAT terminal can also be used; it is thus possible to use a switch in series between the negative pole of the capacitor and the + BAT terminal, this switch closing when the switch Mb is opened.
• the embodiments described implement MOSFET transistors used as switches, but other types of transistors (IGBT for example) can also be used without departing from the scope of the invention.

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• Engineering & Computer Science (AREA)
• Power Engineering (AREA)
• Dc-Dc Converters (AREA)

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• 2007
  • 2007-11-20 FR FR0708144A patent/FR2923962B1/fr not_active Expired - Fee Related
• 2008
  • 2008-11-20 BR BRPI0820580-9A patent/BRPI0820580A2/pt not_active IP Right Cessation
  • 2008-11-20 JP JP2010534515A patent/JP2011504088A/ja active Pending
  • 2008-11-20 WO PCT/FR2008/001622 patent/WO2009101269A1/fr active Application Filing
  • 2008-11-20 KR KR1020107011998A patent/KR20100092948A/ko not_active Application Discontinuation
  • 2008-11-20 US US12/743,266 patent/US20100315048A1/en not_active Abandoned
  • 2008-11-20 CN CN2008801164552A patent/CN101953059A/zh active Pending
  • 2008-11-20 EP EP08872316A patent/EP2220752A1/fr not_active Withdrawn

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