EP2137788A1 - Système de guide d'ondes comprenant un guide d'ondes différentiel - Google Patents

Système de guide d'ondes comprenant un guide d'ondes différentiel

Info

Publication number
EP2137788A1
EP2137788A1 EP08715898A EP08715898A EP2137788A1 EP 2137788 A1 EP2137788 A1 EP 2137788A1 EP 08715898 A EP08715898 A EP 08715898A EP 08715898 A EP08715898 A EP 08715898A EP 2137788 A1 EP2137788 A1 EP 2137788A1
Authority
EP
European Patent Office
Prior art keywords
waveguide
waveguide system
ohms
differential
range
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP08715898A
Other languages
German (de)
English (en)
Inventor
Martin Peschke
Thomas Reichel
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Rohde and Schwarz GmbH and Co KG
Original Assignee
Rohde and Schwarz GmbH and Co KG
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Rohde and Schwarz GmbH and Co KG filed Critical Rohde and Schwarz GmbH and Co KG
Publication of EP2137788A1 publication Critical patent/EP2137788A1/fr
Withdrawn legal-status Critical Current

Links

Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P3/00—Waveguides; Transmission lines of the waveguide type
    • H01P3/02—Waveguides; Transmission lines of the waveguide type with two longitudinal conductors
    • H01P3/06—Coaxial lines
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
    • G01R1/00—Details of instruments or arrangements of the types included in groups G01R5/00 - G01R13/00 and G01R31/00
    • G01R1/20—Modifications of basic electric elements for use in electric measuring instruments; Structural combinations of such elements with such instruments
    • G01R1/24—Transmission-line, e.g. waveguide, measuring sections, e.g. slotted section
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
    • G01R1/00—Details of instruments or arrangements of the types included in groups G01R5/00 - G01R13/00 and G01R31/00
    • G01R1/02—General constructional details
    • G01R1/06—Measuring leads; Measuring probes
    • G01R1/067—Measuring probes
    • G01R1/06766—Input circuits therefor

Definitions

  • the invention relates to a waveguide system with a differential waveguide.
  • Such waveguide systems are required, for example, for transmitting a measurement signal from a probe to a measuring device, for example a spectrum analyzer, a network analyzer or an oscilloscope.
  • a waveguide system with a coaxial conductor is known, for example, from EP 1 605 588 A2.
  • the preceding from this document waveguide is not a differential waveguide, but a differential signal is transmitted via two separate coaxial lines and then fed to an operational amplifier as an input amplifier.
  • At the front end of each coaxial line is an input network and at the rear end of each coaxial line facing the operational amplifier there is a terminating network.
  • the networks are formed by ohmic resistors and capacitors.
  • Waveguide according to EP 1 605 588 A2 is that a relatively large design is present and the handling of the two cables by the user is cumbersome and impractical.
  • Already 1 mm difference in length leads to a time shift of the differential signals against each other by about 5 ps.
  • this leads to significant signal distortion and conversion from DC to differential mode and vice versa.
  • a differential waveguide is used whose signal conductors are coupled to one another in the waveguide and are preferably not necessarily separated from a common ground conductor.
  • the divider network is divided into front network elements located at the front end of the waveguide and rear network elements located at the rear end of the waveguide.
  • the front network elements preferably have transverse elements which extend in the direction of the first or second signal conductor in the direction of the common ground conductor and / or between the two signal conductors.
  • differential waveguide has the advantage over the smaller design compared to the use of two decoupled and separately grounded waveguides. This advantage becomes particularly clear when no coaxial waveguides but strip conductors are used. Since there the waveguides can not be completely shielded from each other, large safety margins between the waveguides must be maintained if two separate waveguides are used to avoid coupling. When using a differential Waveguide, however, the coupling is just desired and necessary. A special safety distance does not have to be maintained. On the contrary, the waveguides must be positioned relatively close together.
  • equal lengths automatically result for the signal conductors of the waveguide.
  • the two signal conductors are also subject to the same thermal expansion due to their spatially adjacent arrangement, which is not the case with individual conductors, in particular, when one of the two conductors comes close to a heat source, for example a power component.
  • a particular advantage lies in the fact that a common mass conductor is present, and not two individual masses, which must first be connected to each other.
  • the problem of the low-inductance connection of two individual masses therefore does not even occur in the differential waveguide according to the invention.
  • differential waveguides can be designed so that the unwanted common mode experiences a very high attenuation.
  • unwanted common mode noise can already be absorbed in the divider.
  • low-frequency common-mode noise for example a 50 Hz or 60 Hz ripple signal of the power supply network, are not first coupled into the waveguide but are also absorbed before the waveguide.
  • the differential waveguide has a resistive coating, i. the first signal conductor and / or the second signal conductor and / or the ground conductor has a non-zero ohmic resistance. This helps to attenuate unwanted multiple reflections stronger and thus suppress.
  • a double coaxial line e.g. in the form of two coaxial cables or a coaxial cable with two inner conductors, which may be twisted, for example, but preferably with training by means of a flexible or rigid conductor strip, especially in coplanar technology (grounded coplanar), grounded coplanar, microstripline -Technique and / or triplate technique.
  • Fig. 2 shows a basic embodiment of the waveguide system according to the invention
  • Fig. 3 is an equivalent circuit diagram of an infinety-smallest portion of the differential waveguide used in the invention.
  • Fig. 4 characteristic impedance resistors ZDM, common mode ZCM, even mode Zeven, and odd
  • Fig. 6 shows the voltage transfer function of the compensated divider of Fig. 5 with a differential waveguide
  • Fig. 7 shows a first embodiment of the differential waveguide used for the waveguide system according to the invention in coupled
  • FIG. 8 shows a second exemplary embodiment of the differential waveguide in triplate technology used for the waveguide system according to the invention in a sectional representation
  • FIG. 9 shows a third exemplary embodiment of the differential waveguide in coplanar technology used for the waveguide system according to the invention in a perspective view and FIG
  • FIG. 10 shows a fourth exemplary embodiment of the differential waveguide in grounded coplanar technology used for the waveguide system according to the invention in a sectional illustration.
  • differential waveguides In order to transmit differential signals over longer distances, differential waveguides are used according to the invention. They consist i.A. from a ground line and two signal lines.
  • the impedances Zl or Z2 iA are complex quantities if the characteristic impedances Zeven and Zodd are complex quantities.
  • the terminating network A can be seen directly at the input T1 of a differential, in particular lossy, line if, in accordance with FIG. 1, it has both the common mode and the counter mode with the corresponding complex Characteristic impedance is completed.
  • the differential waveguide and termination network described above; can now, as shown in Fig. 2, expand to a balanced divider network with the division factor l: k for the push-pull mode. In this case, two series resistors 10, 11 of size (k1) Z1 are added to both inputs P + and P- of the differential waveguide WL.
  • divider elements 12, 13 of size Z3 and 14, 15 of size (kl) Z3 can be added.
  • the resulting network is a compensated divider with a smooth frequency response with respect to the nodes P + and P- for push-pull mode. This becomes clear when between the points P + and P- the termination network A is used directly instead of the waveguide WL.
  • Out- of the divider is the same voltage as at the input P +, P- of the waveguide WL, since it is a reflection-free terminated waveguide. In the case of a lossy waveguide, its attenuation must still be considered in the division ratio.
  • Fig. 5 shows an embodiment of the inventive waveguide system WS, which contains a differential waveguide according to Fig. 3 and has been optimized on the basis of the above considerations.
  • the waveguide system WS has a differential waveguide WL with a first signal conductor Sl and a second signal conductor S2.
  • the signal conductors Sl and S2 are coupled together and galvanically isolated in the embodiment of a common ground conductor ML.
  • in the 5 embodiment is a coaxial, differential waveguide, wherein the signal conductors Sl and S2 are arranged in the vicinity of the central axis, but somewhat radially symmetrically offset from the central axis.
  • the ground conductor ML thus completely surrounds the two signal conductors S1 and S2 in the radial direction, so that the signal conductors S1 and S2 are completely shielded to the outside.
  • the two signal conductors Sl and S2 are arranged so close to one another that results in an electromagnetic coupling of the two signal conductors Sl and S2.
  • An infinitesimal piece of the waveguide shown in Fig. 5 can therefore be described with the equivalent circuit diagram of FIG.
  • the line is a total of, for example, 50 mm long.
  • a divider network is provided with front network elements VN arranged at a front end of waveguide WL in the signal flow direction and rear network elements HN arranged in signal flow direction at the rear end of waveguide WL.
  • the divider network serves with its rear network elements HN on the one hand to the end of the waveguide WL. Due to the complex characteristic impedance Zeven, Zodd a combination of resistive and reactive components is necessary. On the other hand, it represents a compensation network. With suitable dimensioning, a differential input voltage present between the input terminals In + and In is converted in a fixed divider ratio, which is essentially independent of the frequency, into an output voltage present between the output terminals Out + and Out-. ", Mill , Vout * -Vouf
  • Such a frequency-independent divider ratio is necessary in particular for probes for oscilloscopes.
  • the front network elements VN include a first cross member R4 extending from the first signal conductor Sl to the ground conductor ML, and a second cross member R4 'extending from the second signal conductor S2 to the common ground conductor ML.
  • Transverse element R4 and the second transverse element R4 ' are preferably formed as first and second ohmic resistor R4, R4', wherein the resistance of the first and second ohmic resistor R4, R4 'preferably in the range of 1 kOhm to 10 kOhm, preferably in the range of 4 , 5 kohms to 5.5 kohms. A particularly preferred value found by simulation is 5.0 kohms.
  • Network element or a group of network elements which is in the signal path between one of the input terminals In + or In- and the output terminals Out + or Out- connected and has no connection to the circuit ground M.
  • the term cross-member is to be understood in the context of this patent application that it is not located in this signal path, but a network element or a group of network elements, via which one of the signal paths with the circuit ground M or the other signal path is directly or indirectly connected.
  • the front network elements VN comprise first longitudinal elements Rl, Cl, R3, which connect the first input terminal In + to the first signal conductor Sl. Further, further longitudinal elements Rl ', Cl', R3 'are present, which connect the second input terminal IN with the second signal conductor S2.
  • the first longitudinal elements preferably consist of a series connection of a third ohmic resistor Rl with a parallel circuit of a fourth ohmic resistor R3 and a first capacitor Cl.
  • the second longitudinal elements preferably consist of a series connection of a fifth ohmic resistor Rl 'with a parallel circuit of a sixth ohmic resistor R3' and a second capacitor Cl '.
  • the resistance value of the third ohmic resistor Rl and the fifth ohmic resistor Rl ' is preferably in the range of 50 ohms to 200 ohms, preferably in the range of 70 ohms to 150 ohms. Simulation has shown that the value of 100 ohms is particularly suitable.
  • the resistance value of the fourth ohmic resistor R3 and the sixth ohmic resistor R3 ' is preferably in the range of 10 kOhm to 100 kOhm, preferably in the range of 30 kOhm to 60 kOhm.
  • the value of 45 kOhm is particularly advantageous.
  • the capacitance value of the first capacitor Cl and the second capacitor Cl ' is preferably in the range of 0.1 pF to 5 pF, preferably in the range of 0.5 pF to 1 pF.
  • a value of 0.64 pF has proved to be particularly suitable by simulation.
  • first capacitor Cl and the fourth resistor R3 are connected to the first signal conductor Sl of the differential waveguide WL and to the first resistor Rl. Accordingly, the second capacitor Cl 'and the sixth resistor R3' are then connected to the second signal conductor S2 of the differential waveguide WL and to the second resistor R4 '.
  • the rear network elements HN preferably consist of a series circuit of a third capacitor C2 and a seventh ohmic resistor R2 and a fourth capacitor C2 'and an eighth ohmic resistor R2' and a ninth resistor R5.
  • the first signal line Sl of the waveguide WL is connected to a common node K via the series connection of the third capacitor C2 and the seventh ohmic resistor R2, while via the series connection of the fourth capacitor C2 'and the eighth ohmic resistor R2', the second signal line S2 of the waveguide WL is connected to the common node K.
  • the common node K is then connected to the circuit ground M via the ninth ohmic resistor R5.
  • the capacitance of the third capacitor C2 and the fourth capacitor C2 ' is preferably in the range from 0.5 pF to 15 pF, particularly preferably in the range from 1 pF to 5 pF. Simulation has shown that a value of 1.5 pF leads to a particularly good result.
  • the values for R2, R2 'and R5 may differ from the theoretically determined by parasitic effects in order to achieve a better fit for frequencies ⁇ 1 GHz at which Zeven and Zodd have not yet reached their final value. However, their value is still mostly in the range of some 10 ohms or slightly above 100 ohms. R5 can also be used as a direct ground connection with 0 ohms.
  • the resistance of the seventh ohmic resistor R2 and the eighth ohmic resistor R2 ' is preferably in the range of 10 ohms to 250 ohms, more preferably in the range of 75 ohms to 150 ohms.
  • a value of about 125 ohms has proven to be particularly suitable.
  • the resistance value of the ninth ohmic resistor R5 is also preferably in the range of 1 ohm to 100 ohms, with a range of 10 ohms to 30 ohms being particularly preferred. Again, a value of 20.5 ohms has proven to be particularly suitable.
  • Embodiment arranged such that on the one hand the third capacitor C2 to the first signal conductor Sl of the differential waveguide WL and to the first output terminal Out + and on the other hand, the fourth Capacitor C2 'is connected to the second signal conductor S2 and the second output terminal Out-.
  • the ohmic resistors R2 and R2 ' are connected to the common node K.
  • the differential voltage gain is defined here as
  • the resulting almost frequency-independent divider ratio can be described very roughly as follows: At low input frequencies or at DC voltage between the input terminals In + and In, the duty cycle is determined by the ratio
  • the duty cycle is essentially determined by the ratio of the reactances of the capacitors Cl and Cl 'to C2 and C2'.
  • the duty cycle is therefore determined in the high frequency range by the ratio of the resistors Rl and Rl 'to the parallel circuit of R4 and R2 or R4' and R2 ', which is characterized by the low resistance value of R2 and R2'.
  • the above explanation is simplistic and is for illustrative purposes only.
  • the inventive waveguide system thus has a compensated, differential divider network, which has a high input resistance and a low input capacitance and still by a
  • Waveguide can be extended over a spatially large area. Such a waveguide system is advantageous for many applications in which space conditions require the bridging of a large distance, while electrical requirements require the smallest possible extent.
  • waveguides formed in stripline technology are preferably used. Possible embodiments are shown in FIGS. 7 to 10. For the purpose of illustration, the electrical field E and the magnetic flux B are also shown in FIGS. 7 to 10.
  • the substrate 20 is formed of a flexible material, it results a particularly good handleability of the differential waveguide.
  • Fig. 8 shows the formation of the waveguide WL in triplate technique.
  • two dielectric substrates 30 and 31 are present, both of which are provided on their outer surface with a continuous metal coating 32 and 33, respectively. These metal layers are respectively connected to the ground 34 and form the ground conductor ML.
  • the first signal line Sl and the second signal line S2 are arranged as thin conductive strips 35 and 36 between the substrates 30 and 31, the regions 37 in this layer being sandwiched between the two substrates 30 and 31 by a dielectric filler, e.g. a plastic resin, can be filled.
  • a dielectric filler e.g. a plastic resin
  • the waveguide WL in coplanar technology in a perspective representation.
  • the first signal lines Sl and the second signal line S2 are formed as thin metal strips 41 and 42 on the dielectric substrate 40.
  • a metal layer 43 and 44 On both sides of the signal line Sl and S2 is a metal layer 43 and 44, which are each connected to the ground potential 45. These two metal layers 43 and 44 therefore form the ground conductors ML.
  • a ring core 46 made of a magnetic, preferably ferrimagnetic material is present in the vicinity of one end of the waveguide WL, which surrounds the waveguide WL.
  • common mode noise can be absorbed, because in common mode through the waveguide WL running waves in which the currents in the signal conductors Sl and S2 are not directed as in push-pull mode against each other but in the same flow direction, generate in the ring core 46, an induction, so that the common mode wave is absorbed.
  • the push-pull shaft can pass unhindered through the toroidal core.
  • the ring core 46 may also be arranged within the housing of a measuring device, from which the
  • Waveguide WL is led out, so that the ring core 46 is not visible to the outside and does not affect the handling.
  • Fig. 10 shows another embodiment of the waveguide in grounded coplanar technology (grounded coplanar).
  • the two signal lines S1 and S2 are applied as thin strip lines 51 and 52, and besides the strip lines 51 and 52 are the ground surfaces 53 and 54.
  • the difference is therein in that an additional ground surface 56 is present on the underside of the substrate 50.
  • compared to the embodiment of FIG. 9 results in a better shielding down.
  • the optimal shielding is achieved with the triplate technique of FIG.
  • Embodiments limited. In addition to the exemplary embodiments of the differential waveguides WL shown in FIGS. 5 and 7 to 10, a number of other embodiments are also conceivable.
  • the divider network must not exactly dimensioned with the above values. It is conceivable that other value combinations and other circuit topologies lead to the same or comparable results.
  • the resistor R3 or R3 'in FIG. 5 could also be arranged parallel to Rl and R2 or Rl' and R2 'as shown in FIG. 2, instead of only parallel to Cl or Cl'.
  • the network is nevertheless a compensated divider, since R3 or R3 'is so large that the parallel connection of Cl and R3 or Cl' and R2 'at high frequencies at which Rl or Rl' acts, exclusively by Cl or Cl 'is dominated.

Landscapes

  • Physics & Mathematics (AREA)
  • General Physics & Mathematics (AREA)
  • Non-Reversible Transmitting Devices (AREA)

Abstract

L'invention concerne un système de guide d'ondes (WS) qui comprend un guide d'ondes (W) différentiel comportant au moins un premier et un deuxième conducteur de signaux (S1, S2) qui sont couplés l'un à l'autre dans le guide d'ondes (W), ainsi qu'un réseau séparateur comportant des éléments de réseau avant (VN) disposés à une extrémité avant du guide d'ondes (W), dans le sens de circulation des signaux, et des éléments de réseau arrière (HN) disposés à une extrémité arrière du guide d'ondes (W), dans le sens de circulation des signaux. Les éléments de réseau avant (VN) comprennent un premier élément transversal (R4) qui s'étend dans le sens du premier conducteur de signaux (S1) en direction du conducteur de masse (ML) et un deuxième élément transversal (R4') qui s'étend dans le sens du deuxième conducteur de signaux (S2) en direction du conducteur de masse (ML). Dans une variante, l'élément transversal peut être disposé entre les conducteurs de signaux (S1, S2).
EP08715898A 2007-04-03 2008-02-20 Système de guide d'ondes comprenant un guide d'ondes différentiel Withdrawn EP2137788A1 (fr)

Applications Claiming Priority (3)

Application Number Priority Date Filing Date Title
DE102007016063 2007-04-03
DE102007027155A DE102007027155A1 (de) 2007-04-03 2007-06-13 Wellenleiter-System mit differenziellem Wellenleiter
PCT/EP2008/001328 WO2008119417A1 (fr) 2007-04-03 2008-02-20 Système de guide d'ondes comprenant un guide d'ondes différentiel

Publications (1)

Publication Number Publication Date
EP2137788A1 true EP2137788A1 (fr) 2009-12-30

Family

ID=39768036

Family Applications (1)

Application Number Title Priority Date Filing Date
EP08715898A Withdrawn EP2137788A1 (fr) 2007-04-03 2008-02-20 Système de guide d'ondes comprenant un guide d'ondes différentiel

Country Status (4)

Country Link
US (1) US8076989B2 (fr)
EP (1) EP2137788A1 (fr)
DE (1) DE102007027155A1 (fr)
WO (1) WO2008119417A1 (fr)

Families Citing this family (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2012186796A (ja) 2011-02-18 2012-09-27 Sony Corp 信号伝送装置及び電子機器
JP5690428B1 (ja) * 2014-05-21 2015-03-25 株式会社フジクラ プリント配線板
US10326200B2 (en) * 2017-10-18 2019-06-18 General Electric Company High impedance RF MEMS transmission devices and method of making the same
US11041880B2 (en) 2017-12-01 2021-06-22 Tektronix, Inc. Contactless coupling between test and measurement system and a device under test
WO2022217046A1 (fr) * 2021-04-08 2022-10-13 Tektronix, Inc. Atténuateur de commutation de précision, à largeur de bande élevée

Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
FR2126840A5 (fr) * 1971-02-11 1972-10-06 Westinghouse Electric Corp
US6097262A (en) * 1998-04-27 2000-08-01 Nortel Networks Corporation Transmission line impedance matching apparatus
US20040108921A1 (en) * 2002-12-10 2004-06-10 Eastman Kodak Company Parallel plate wave-guide structure in a layered medium for transmitting complementary signals
US6822463B1 (en) * 2001-12-21 2004-11-23 Lecroy Corporation Active differential test probe with a transmission line input structure

Family Cites Families (11)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US2280950A (en) * 1941-05-13 1942-04-28 Westinghouse Electric & Mfg Co Pilot wire system with means for neutralizing induced voltages
US3778759A (en) * 1971-12-27 1973-12-11 Texas Instruments Inc Static filter for long line data systems
US5517487A (en) * 1993-07-19 1996-05-14 Modicon, Inc. System for increasing the capacity of existing local area networks that use shielded twisted wire pair medium
DE19534309C1 (de) * 1995-09-15 1997-03-27 Siemens Ag Anordnung zum Übertragen von Signalen über Triplate-Leitungen
DE19654329A1 (de) * 1996-12-24 1998-06-25 Bosch Gmbh Robert Schaltungsanordnung zur störungsfreien Auswertung von Signalen
FR2790096B1 (fr) * 1999-02-18 2001-04-13 St Microelectronics Sa Structure etalon elementaire a faibles pertes pour l'etalonnage d'une sonde de circuit integre
DE19907675A1 (de) * 1999-02-23 2000-09-14 Kreitmair Steck Wolfgang Kabelschirm aus Faserverbundwerkstoffen mit hohem Anteil an elektrisch leitfähigen Fasern zur elektromagnetischen Abschirmung
US6373348B1 (en) * 2000-08-11 2002-04-16 Tektronix, Inc. High speed differential attenuator using a low temperature co-fired ceramic substrate
US6856126B2 (en) * 2003-01-21 2005-02-15 Agilent Technologies, Inc. Differential voltage probe
US7256575B2 (en) 2004-06-01 2007-08-14 Tektronix, Inc. Wide bandwidth attenuator input circuit for a measurement probe
US7164994B2 (en) * 2005-02-04 2007-01-16 Tektronix, Inc. Differential termination attenuator network for a measurement probe having an internal termination voltage generator

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
FR2126840A5 (fr) * 1971-02-11 1972-10-06 Westinghouse Electric Corp
US6097262A (en) * 1998-04-27 2000-08-01 Nortel Networks Corporation Transmission line impedance matching apparatus
US6822463B1 (en) * 2001-12-21 2004-11-23 Lecroy Corporation Active differential test probe with a transmission line input structure
US20040108921A1 (en) * 2002-12-10 2004-06-10 Eastman Kodak Company Parallel plate wave-guide structure in a layered medium for transmitting complementary signals

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
See also references of WO2008119417A1 *

Also Published As

Publication number Publication date
DE102007027155A1 (de) 2008-10-23
US20100301965A1 (en) 2010-12-02
WO2008119417A1 (fr) 2008-10-09
US8076989B2 (en) 2011-12-13

Similar Documents

Publication Publication Date Title
DE3715083C2 (de) Verstärkeranordnung mit parallel arbeitenden Signalverstärkern
EP1337001B1 (fr) Dispositif pour la transmission sans contact des signaux électriques et/ou énergie
DE102010040290A1 (de) Richtkoppler
DE102015118829A1 (de) Gleichtakt-Unterdrücker auf der Grundlage von Differential-Übertragungsleitung
DE102012018651B4 (de) Leistungs-Kombinator/-Teiler
DE102013213981A1 (de) Spule für Schalteinrichtung mit hoher Hochfrequenzleistung
WO2008119417A1 (fr) Système de guide d'ondes comprenant un guide d'ondes différentiel
DE2837817A1 (de) Vorspannungsschaltung
WO2013017397A1 (fr) Coupleur directif séparé de manière galvanique
EP0862796B1 (fr) Dispositif pour la transmission de signaux entre des elements mobiles
DE102005005751B4 (de) Testvorrichtung mit reflexionsarmer Signalverteilung
DE10316047A1 (de) Richtkoppler in koplanarer Wellenleitertechnik
DE2807813C2 (de) Schaltungsanordnung zur Erreichung von Leistungsanpassung bei rauschangepaBten Hochfrequenz-Verstärkern
EP2438645B1 (fr) Coupleur vers avant à conducteurs plats
WO2013143537A1 (fr) Coupleur directif à faible couplage électrique
EP2068391A2 (fr) Dispositif doté d'une ligne à bande croisée
DE1005146B (de) Breitbandrichtungskoppler
DE2744862A1 (de) Hochfrequenztransformator
DE102012202097A1 (de) Koppelstruktur zum kreuzen von übertragungsleitungen
EP0518310B1 (fr) Circuit de combinaison ou de distribution de signaux de puissance à hautes fréquences
EP0054645B1 (fr) Commutateur à diode PIN
DE2757115C2 (de) Modenkoppler
DE2425722A1 (de) Breitbandige abzweigeinrichtung fuer hochfrequenzsignale des vhf/uhf-bereichs
EP2617097B1 (fr) Combineur de signaux haute fréquence
EP1913606B1 (fr) Transformateur de ligne pour l'adaptation d'impedance

Legal Events

Date Code Title Description
PUAI Public reference made under article 153(3) epc to a published international application that has entered the european phase

Free format text: ORIGINAL CODE: 0009012

17P Request for examination filed

Effective date: 20090212

AK Designated contracting states

Kind code of ref document: A1

Designated state(s): AT BE BG CH CY CZ DE DK EE ES FI FR GB GR HR HU IE IS IT LI LT LU LV MC MT NL NO PL PT RO SE SI SK TR

17Q First examination report despatched

Effective date: 20100126

DAX Request for extension of the european patent (deleted)
STAA Information on the status of an ep patent application or granted ep patent

Free format text: STATUS: THE APPLICATION IS DEEMED TO BE WITHDRAWN

18D Application deemed to be withdrawn

Effective date: 20150128