EP2111730B1 - Procédé de commande d'un circuit en demi-pont, et circuit en demi-pont correspondant - Google Patents
Procédé de commande d'un circuit en demi-pont, et circuit en demi-pont correspondant Download PDFInfo
- Publication number
- EP2111730B1 EP2111730B1 EP07704044A EP07704044A EP2111730B1 EP 2111730 B1 EP2111730 B1 EP 2111730B1 EP 07704044 A EP07704044 A EP 07704044A EP 07704044 A EP07704044 A EP 07704044A EP 2111730 B1 EP2111730 B1 EP 2111730B1
- Authority
- EP
- European Patent Office
- Prior art keywords
- time
- circuit
- lamps
- circuit arrangement
- timer
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Not-in-force
Links
- 238000000034 method Methods 0.000 title description 3
- 230000007935 neutral effect Effects 0.000 claims abstract 4
- 239000003990 capacitor Substances 0.000 claims description 15
- 230000001052 transient effect Effects 0.000 claims description 4
- 238000004804 winding Methods 0.000 description 9
- 101100190527 Arabidopsis thaliana PIN5 gene Proteins 0.000 description 4
- 238000010304 firing Methods 0.000 description 4
- 238000009738 saturating Methods 0.000 description 4
- 101100190530 Arabidopsis thaliana PIN8 gene Proteins 0.000 description 3
- 102000007315 Telomeric Repeat Binding Protein 1 Human genes 0.000 description 3
- 108010033711 Telomeric Repeat Binding Protein 1 Proteins 0.000 description 3
- 238000010586 diagram Methods 0.000 description 3
- 108010037490 Peptidyl-Prolyl Cis-Trans Isomerase NIMA-Interacting 4 Proteins 0.000 description 2
- 102100031653 Peptidyl-prolyl cis-trans isomerase NIMA-interacting 4 Human genes 0.000 description 2
- 241000158147 Sator Species 0.000 description 2
- 239000002800 charge carrier Substances 0.000 description 2
- 101100190528 Arabidopsis thaliana PIN6 gene Proteins 0.000 description 1
- 101100190529 Arabidopsis thaliana PIN7 gene Proteins 0.000 description 1
- 108010059419 NIMA-Interacting Peptidylprolyl Isomerase Proteins 0.000 description 1
- 101150087393 PIN3 gene Proteins 0.000 description 1
- 101150011456 PIN8 gene Proteins 0.000 description 1
- 102100026114 Peptidyl-prolyl cis-trans isomerase NIMA-interacting 1 Human genes 0.000 description 1
- 230000004913 activation Effects 0.000 description 1
- 230000033228 biological regulation Effects 0.000 description 1
- 238000001816 cooling Methods 0.000 description 1
- 230000001419 dependent effect Effects 0.000 description 1
- 238000001514 detection method Methods 0.000 description 1
- 230000000694 effects Effects 0.000 description 1
- 230000006698 induction Effects 0.000 description 1
- 230000001939 inductive effect Effects 0.000 description 1
- 238000005457 optimization Methods 0.000 description 1
- 230000001960 triggered effect Effects 0.000 description 1
Images
Classifications
-
- H—ELECTRICITY
- H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
- H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
- H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
- H05B41/14—Circuit arrangements
- H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
- H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
- H05B41/282—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices
- H05B41/2825—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices by means of a bridge converter in the final stage
- H05B41/2827—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices by means of a bridge converter in the final stage using specially adapted components in the load circuit, e.g. feed-back transformers, piezoelectric transformers; using specially adapted load circuit configurations
Definitions
- the present invention relates to a circuit arrangement for operating lamps.
- the invention mainly relates to the operation of low pressure gas discharge lamps. Apart from aspects concerning the preheating, the invention is also applicable to control gear for LEDs.
- the circuit arrangement includes a stop device, which can prevent the switching on of the electronic switches of the half-bridge inverter and releases only during an on-time.
- the on-time depends on a lamp parameter, which can close a loop.
- a disadvantage of this circuit is that the ignition burst for the lamp depends on the tolerances of the load circuit components.
- the object of the present invention is therefore a method for controlling a half-bridge circuit in which a firing burst for the discharge lamp is relatively independent of the tolerances of the load circuit components. Also, the ignition burst with relatively magnetically strong saturating lamp inductor should be generated. In addition, a corresponding half-bridge circuit is to be provided.
- an active on-time of the switches of the half-bridge circuit is fixed during an operating phase at the operating frequency specified. This requires no regulation of the lamp current or the lamp power during operation.
- the preheat frequency is such that the active on-time of the switches of the half-bridge circuit in the preheat phase is less than a quarter of the resonant period while the operating frequency is so low that the active on-time is greater than a quarter of the resonant period minus a storage time the half-bridge switch is.
- a minimum frequency or time range can be specified, in the passage through an effective preheating and a safe ignition is possible.
- the defined period of time during which the frequency is lowered continuously should be between 1 ms and 100 ms. This time is sufficient to ensure a safe ignition.
- a symmetrical Zündleerlaufstrombegrenzung occurs.
- the load circuit current it is advantageous to limit the load circuit current to a temperature-dependent limit value.
- the temperature dependence of the saturation induction of the lamp inductor can also be taken into account.
- the half-bridge circuit has bipolar half-bridge switches with basic series capacitors in the control circuits.
- the storage time of the bipolar transistors can be further reduced.
- the half-bridge circuit is to be improved to the effect that regardless of the tolerances of the load circuit components always a defined ignition burst is possible. It is always the goal to obtain the least possible losses so that little or no cooling measures are required.
- Fig. 1 shows the voltage on the Last Vietnamesekondensator, which is usually connected in parallel with the lamp to be operated.
- the idling curve U CL results as a function of the frequency.
- the maximum of this curve is at the resonant frequency f res .
- There the highest voltage is to be observed on the load circuit capacitor.
- the lamp ignites at an ignition voltage U z , which is slightly below the voltage maximum. This ignition voltage U z is achieved at a firing frequency f flammable.
- the s is typically between 0.4 s and 2
- the lamp is heated to a preheat frequency f preheating, the ignition significantly higher than the ignition frequency f lies.
- f preheat the voltage across the lamp is well below the ignition voltage U z .
- the lamp After preheating the lamp can be ignited in the ideal case, characterized in that the frequency of the preheating frequency f preheat is reduced to a fixed ignition frequency f flammable. Due to tolerances of the load circuit components, however, the course of the load circuit capacitor voltage can change so that at the fixed predetermined frequency, the ignition voltage U z is not reached or unnecessarily high. The lamp would not ignite in this case, or it would take place too high a component load at too high a voltage.
- the load circuit frequency continuously preheating by the preheat frequency f on the resonant frequency f res (typically 50 to 60 kHz) to the operating frequency f for operation to reduce (typically 40 to 50 kHz).
- the open circuit voltage (lamp has not yet ignited) increases according to arrow P1. She reaches at a previously unknown or undefined frequency, the ignition voltage U z . Now the voltage on the load circuit capacitor drops to the operating voltage U CB and the load circuit frequency is further reduced until finally the operating point AP at the operating frequency f operation is reached, as shown in Fig. 1 indicated by arrow P2. It will therefore come regardless of the component tolerances to a firing burst, so that the lamp is safely put into operation without being exposed to high voltages.
- the preheat frequency f preheat is selected so that the on-time is on-preheat ⁇ 1 ⁇ 4 T res , where T res represents the idle period.
- a state machine then increases the active time t on-betrier> 1 ⁇ 4 T res - t s, so that the frequency drops to the operating frequency f becrieb.
- t s entsprich the storage time of the collector current in the use of bipolar transistors.
- a one-time t on is in Fig. 4 and corresponds to that time in which the base current I B of a bipolar transistor of the half-bridge circuit is greater than 0 during a half-period.
- FIG Fig. 2 A half-bridge circuit for exemplifying the invention is shown in FIG Fig. 2 played.
- the half-bridge switches Q1 and Q2 are designed as bipolar transistors.
- the two switches Q1 and Q2 are connected in series, with the intermediate circuit voltage having the poles VZW_PLUS and VZW_MINUS being applied to the series circuit.
- Base and emitter of the switch Q1 are connected through a resistor R11.
- the base of the switch Q1 is connected in parallel with a first winding of a transformer TR1 to the node N1 via a parallel connection of a resistor R42 with an RC series circuit R3, C29.
- the emitter of the switch Q2 is connected through a resistor R6 to the negative terminal VZW_MINUS and a resistor R12 bridges the base and the emitter of the switch Q2.
- the base of the switch Q2 is connected to the negative terminal VZW_MINUS via a parallel connection of a resistor R43 with an RC series circuit R4, C30 in series with a second winding of the transformer TR1.
- Capacitors C29 and C30 cause the base current to lead. In addition, they serve to reduce the storage time, as related below Fig. 4 is explained.
- a capacitor C8 is connected in parallel to the diode D9 and acts as a trapezoidal capacitor.
- the transformer TR1 has a third winding through which a stop function is controlled.
- This third winding is coupled to the AC terminals of a full-bridge rectifier formed by diodes D1, D2, D3 and D4.
- the DC connections of this rectifier are parallel to an electronic switch V2.
- the third winding, the Rectifier and the switch V2 form a stop device.
- the switch V2 is a MOSFET transistor, which is connected to the source terminal to the reference potential VCC_MINUS.
- the switch V2 short-circuits the third winding of the transformer TR1 via the rectifier.
- the control inputs of the electronic switches Q1 and Q2 are short-circuited via the transformer TR1, so that the two switches are turned off.
- the switch V2 is controlled by a timer U1.
- This timer is realized by a CMOS-IC 555.
- the circuit U1 provides the stop signal to PIN3.
- the signal In order to achieve the correct polarity for driving the switch V2, the signal must be inverted. This is achieved by the inverter U2-D.
- the supply terminals VCC_PLUS and VCC_MINUS are provided, which are connected to PIN8 and PIN1 of the circuit.
- the connection point between the resistor R1 and the capacitor C1 is connected to both PIN6 and PIN7 of the circuit U1 to give the timer the appropriate time constant.
- PIN4 of the circuit U1 forms a reset input and must be high-ohmic with the positive operating voltage be connected via R2, so that the desired functionality of the circuit U1 sets.
- PIN2 of the circuit U1 forms a trigger input and is first connected via a resistor R25 to the positive supply terminal VCC_PLUS. To trigger the timer, PIN2 requires a negative pulse. This is supplied by a comparator U3-A, which can be realized for example by the component LM293. The trigger pulse is delivered directly to PIN2 of the circuit U1.
- the inverting input of the comparator U3-A is connected via a resistor R28 to VCC_PLUS and via a resistor R29 to VCC_MINUS.
- the non-inverting input of the comparator U3-A is fed by the DC output of a full-bridge rectifier GL1.
- the secondary winding of a current transformer or transformer TR3 is connected to the AC voltage input of this full-bridge rectifier GL1.
- the primary winding of the transformer TR3 is between the load circuit and the terminal Il1 (see also Fig. 2 ).
- the DC output of the full-bridge rectifier Gl1 is terminated in a low-resistance manner with a series connection of the resistors R30 and R31.
- the non-inverting input of the comparator U3-A is a voltage that is proportional to the rectified load current.
- the voltage at the inverting input of the comparator U3-A is temporarily higher than the voltage at the non-inverting input. This results as a comparator signal, a negative trigger pulse.
- the components U3-A, R28, R29, R30, R31, GL and TR3 thus form a triggering device based on current zero crossing detection.
- the timer is triggered and switches off the transistor V2 for the on-time, whereby the activation of the switches Q1 and Q2 is enabled.
- the output signal of a further comparator U3-B is connected to PIN4 of the circuit U1. Its inverting input is between resistors R30 and R31. The non-inverting input is connected between a series connection of resistors R26 and R27, which in turn is connected between the supply terminals VCC_PLUS and VCC_MINUS. So if the rectified load current exceeds a certain value, the timer is reset and thus the respective half-bridge switch is actively switched off.
- the duration of the preheating time (typically 0.4 to 2 s) and the duration of the transitional period from the preheat frequency f preheat to the operating frequency f operation (preferably 1 ms to 100 ms, so that charge carriers can build up in the lamp for the ignition) is over PIN5 of the circuit U1 is set.
- the switching time from the preheating phase to the operating phase is determined by an RC element consisting of a series connection of a resistor R24 with a capacitor C2.
- the capacitor C2 is between PIN5 and the negative supply terminal VCC_MINUS.
- the duration of the preheat time is determined with the RC series circuit R23, C3, which is located between the two supply terminals VCC_MINUS and VCC_PLUS.
- a node N2 between the two devices R23 and C3 is connected to the input of inverter U2-B and a diode D6 to the resistor R24 and thus to PIN5 of the circuit U1.
- Diode D6 dynamically switches resistor R24 parallel to C2 during the preheat phase to ensure the desired timing.
- the comparator can be constructed from a current mirror. This is also known as the "emitter-controlled differential comparator”.
- the goal is to operate the lamp with as few losses as possible. This also means achieving as low-loss switching as possible. This is possible in inductive operation of the lamp.
- the voltage is pulled to 0 and the current switched in this state.
- the current during switching should be as low as possible. Therefore, the respective bipolar transistor Q1, Q2 is turned on in the current zero crossing, which is due to the base current I B in Fig. 4 is indicated.
- This current profile of the base current I B is established in the case of an ideal current transformer TR1, wherein the base current I B in phase with the current I C in the load circuit.
- the base current I B is switched off by the timer or the switch V2. Due to a charge carrier excess in the bipolar transistor results in a storage time t s , so that the respective bipolar transistor only turns off at time t 1 actually.
- a base series capacitor C29 is connected to the base of the bipolar transistor Q1 and a base series capacitor C30 is connected to the base of the bipolar transistor Q2.
- the base current increases faster after switching on, which is indicated by the dashed line I B 'in Fig. 4 is indicated.
- the shortened storage time t s ' can also simultaneously increase the on-time, starting from t 0 to t on '. In this way, the losses in the bipolar transistors Q1 and Q2 can be further reduced.
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Circuit Arrangements For Discharge Lamps (AREA)
- Inverter Devices (AREA)
- Dc-Dc Converters (AREA)
Claims (6)
- Montage pour faire fonctionner des lampes, qui a les caractéristiques suivantes :- un dispositif en demi-pont, qui comporte un commutateur ( Q1) électronique supérieur et un commutateur ( Q2 ) électronique inférieur, qui sont montés en série, qui ont respectivement une borne de commande et qui forment un point ( N1 ) médian en leur point de liaison,- au point ( N1 ) médian est raccordé un circuit de charge, dans lequel passe un courant ( IL1 ) de circuit de charge,- le circuit de charge comporte un réseau de réactance ayant une fréquence de résonance, auquel une lampe peut être raccordée,- le circuit de charge est proportionné de manière à ce que, dans un fonctionnement normal pour une lampe raccordée après l'ouverture de l'un des commutateurs ( Q1, Q2 ) électroniques, la tension à respectivement l'autre des commutateurs ( Q1, Q2 ) électroniques devienne nulle après un temps d'oscillation,- le montage comprend un dispositif de réaction, qui couple une grandeur de réaction du circuit de charge aux bornes de commande des commutateurs ( Q1, Q2 ) électroniques, de manière à ce que les commutateurs ( Q1, Q2 ) électroniques soient fermés en alternance,- le montage comprend un dispositif d'arrêt, qui est couplé aux bornes de commande des commutateurs ( Q1, Q2 ) électroniques et qui a une entrée à laquelle peut être appliqué un signal d'arrêt, le dispositif d'arrêt empêchant une fermeture des commutateurs ( Q1, Q2 ) électroniques tant que le signal d'arrêt a un état arrêt,- le montage comprend une minuterie, qui est couplée à l'entrée du dispositif d'arrêt et qui procure le signal d'arrêt, qui peut prendre un état marche et un état arrêt,- le montage comprend un dispositif de déclenchement, qui émet respectivement après écoulement du temps d'oscillation un signal de déclenchement en direction de la minuterie, toutefois au plus tard lorsque le courant ( ILS ) du circuit de charge devient égal à zéro,- la minuterie met le signal d'arrêt dans l'état marche pendant la durée d'un temps ( ton ) de marche,caractérisé en ce que- il est prescrit par la minuterie par une commande d'écoulement du temps d'abord un temps ( ton ) de marche, pendant le temps de préchauffage des électrodes des lampes, qui est plus petit qu'un quart de la durée de la fréquence de résonance du réseau de réactance et, après la durée de préchauffage des électrodes des lampes, ce temps de marche est augmenté continuellement jusqu'à correspondre au moins à un quart de la durée de la période de la fréquence de résonance du réseau de réactance.
- Montage suivant la revendication 1,
caractérisé en ce que
il y a un dispositif à valeur de seuil qui compare le courant ( IL1 ) du circuit de charge à une valeur limite de courant pouvant être prescrite et qui, lorsque cette valeur limite de courant est atteinte, envoie à la minuterie un signal de remise à zéro et met le dispositif d'arrêt dans l'état d'arrêt. - Montage suivant la revendication 1 ou 2,
caractérisé en ce que
le temps ( ton ) de marche est augmenté de la valeur minimum pendant le préchauffage à la valeur maximum en fonctionnement de la lampe d'une manière continue de 1 jusqu'à 100 ms. - Montage suivant l'une des revendications 1 à 3,
caractérisé en ce que
le temps ( ton ) de marche est prescrit de manière fixe à la fréquence de fonctionnement pendant la phase de fonctionnement des lampes. - Montage suivant la revendication 4,
caractérisé en ce que
pour des commutateurs bipolaires en demi-pont, le temps ( ton ) de marche dans la phase de fonctionnement des lampes est plus grand qu'un quart de la durée de la période du réseau de réactance diminué d'un temps ts de rémanence. - Montage suivant l'une des revendications 1 à 5,
caractérisé en ce que
les commutateurs( Q1, Q2 ) bipolaires en demi-pont ont des condensateurs ( C29, C30 ) série de base dans les circuits de commande.
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
PCT/EP2007/050576 WO2008089839A1 (fr) | 2007-01-22 | 2007-01-22 | Procédé de commande d'un circuit en demi-pont, et circuit en demi-pont correspondant |
Publications (2)
Publication Number | Publication Date |
---|---|
EP2111730A1 EP2111730A1 (fr) | 2009-10-28 |
EP2111730B1 true EP2111730B1 (fr) | 2010-11-24 |
Family
ID=38477193
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
EP07704044A Not-in-force EP2111730B1 (fr) | 2007-01-22 | 2007-01-22 | Procédé de commande d'un circuit en demi-pont, et circuit en demi-pont correspondant |
Country Status (5)
Country | Link |
---|---|
US (1) | US8212495B2 (fr) |
EP (1) | EP2111730B1 (fr) |
AT (1) | ATE489836T1 (fr) |
DE (1) | DE502007005800D1 (fr) |
WO (1) | WO2008089839A1 (fr) |
Cited By (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
DE102020130728A1 (de) | 2020-11-20 | 2022-05-25 | Osram Gmbh | Ansteuerbeschaltung für den steuereingang eines leistungstransistors eines getakteten wandlers und anwendung der ansteuerbeschaltung |
DE102021208416A1 (de) | 2021-08-03 | 2023-02-09 | Osram Gmbh | Resonant betriebener getakteter isolierender leistungswandler und verfahren zum tiefen dimmen eines derartigen leistungswandlers |
Families Citing this family (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
CN102843124B (zh) * | 2011-06-20 | 2015-03-11 | 昂宝电子(上海)有限公司 | 通过调节基极电流来驱动双极结型晶体管的系统和方法 |
US8937437B2 (en) * | 2013-06-13 | 2015-01-20 | Osram Syvlania Inc. | Ballast with anti-striation circuit |
Family Cites Families (10)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US5382882A (en) * | 1993-04-20 | 1995-01-17 | General Electric Company | Power supply circuit for a gas discharge lamp |
DE19613077C2 (de) * | 1996-04-02 | 1999-10-14 | Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh | Schaltungsanordnung zum Betreiben von elektrischen Lampen, insb. freischwingender Halbbrückenwandler |
US6072710A (en) * | 1998-12-28 | 2000-06-06 | Philips Electronics North America Corporation | Regulated self-oscillating resonant converter with current feedback |
ITMI991131A1 (it) * | 1999-05-21 | 2000-11-21 | St Microelectronics Srl | Architettura di pilotaggio a semi-ponte (half-bridge) autooscillante a frequenza variabile in particolare per carichi elettrici |
CN1363202A (zh) * | 2000-02-10 | 2002-08-07 | 皇家菲利浦电子有限公司 | 配有ntc电阻的保护电路 |
DE10220471A1 (de) * | 2002-05-07 | 2003-11-20 | Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh | Schaltungsanordnung zum Betrieb von Entladungslampen |
DE102004028798A1 (de) * | 2004-06-15 | 2006-01-05 | Patent-Treuhand-Gesellschaft für elektrische Glühlampen mbH | Schaltung mit Abschalteinrichtung zum Betrieb von Lichtquellen |
DE102005007346A1 (de) * | 2005-02-17 | 2006-08-31 | Patent-Treuhand-Gesellschaft für elektrische Glühlampen mbH | Schaltungsanordnung und Verfahren zum Betreiben von Gasentladungslampen |
DE102005007348A1 (de) | 2005-02-17 | 2006-08-31 | Zumtobel Staff Gmbh | Strahlerleuchte mit variabler Lichtabstrahlcharakteristik |
US7436127B2 (en) * | 2005-11-03 | 2008-10-14 | International Rectifier Corporation | Ballast control circuit |
-
2007
- 2007-01-22 DE DE502007005800T patent/DE502007005800D1/de active Active
- 2007-01-22 US US12/524,087 patent/US8212495B2/en not_active Expired - Fee Related
- 2007-01-22 WO PCT/EP2007/050576 patent/WO2008089839A1/fr active Application Filing
- 2007-01-22 AT AT07704044T patent/ATE489836T1/de active
- 2007-01-22 EP EP07704044A patent/EP2111730B1/fr not_active Not-in-force
Cited By (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
DE102020130728A1 (de) | 2020-11-20 | 2022-05-25 | Osram Gmbh | Ansteuerbeschaltung für den steuereingang eines leistungstransistors eines getakteten wandlers und anwendung der ansteuerbeschaltung |
DE102021208416A1 (de) | 2021-08-03 | 2023-02-09 | Osram Gmbh | Resonant betriebener getakteter isolierender leistungswandler und verfahren zum tiefen dimmen eines derartigen leistungswandlers |
Also Published As
Publication number | Publication date |
---|---|
EP2111730A1 (fr) | 2009-10-28 |
US20100102755A1 (en) | 2010-04-29 |
DE502007005800D1 (de) | 2011-01-05 |
US8212495B2 (en) | 2012-07-03 |
WO2008089839A1 (fr) | 2008-07-31 |
ATE489836T1 (de) | 2010-12-15 |
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