EP2111730B1 - Method for controlling a half-bridge circuit and corresponding half-bridge circuit - Google Patents
Method for controlling a half-bridge circuit and corresponding half-bridge circuit Download PDFInfo
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- EP2111730B1 EP2111730B1 EP07704044A EP07704044A EP2111730B1 EP 2111730 B1 EP2111730 B1 EP 2111730B1 EP 07704044 A EP07704044 A EP 07704044A EP 07704044 A EP07704044 A EP 07704044A EP 2111730 B1 EP2111730 B1 EP 2111730B1
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- 230000007935 neutral effect Effects 0.000 claims abstract 4
- 239000003990 capacitor Substances 0.000 claims description 15
- 230000001052 transient effect Effects 0.000 claims description 4
- 238000004804 winding Methods 0.000 description 9
- 101100190527 Arabidopsis thaliana PIN5 gene Proteins 0.000 description 4
- 238000010304 firing Methods 0.000 description 4
- 238000009738 saturating Methods 0.000 description 4
- 101100190530 Arabidopsis thaliana PIN8 gene Proteins 0.000 description 3
- 102000007315 Telomeric Repeat Binding Protein 1 Human genes 0.000 description 3
- 108010033711 Telomeric Repeat Binding Protein 1 Proteins 0.000 description 3
- 238000010586 diagram Methods 0.000 description 3
- 108010037490 Peptidyl-Prolyl Cis-Trans Isomerase NIMA-Interacting 4 Proteins 0.000 description 2
- 102100031653 Peptidyl-prolyl cis-trans isomerase NIMA-interacting 4 Human genes 0.000 description 2
- 241000158147 Sator Species 0.000 description 2
- 239000002800 charge carrier Substances 0.000 description 2
- 101100190528 Arabidopsis thaliana PIN6 gene Proteins 0.000 description 1
- 101100190529 Arabidopsis thaliana PIN7 gene Proteins 0.000 description 1
- 108010059419 NIMA-Interacting Peptidylprolyl Isomerase Proteins 0.000 description 1
- 101150087393 PIN3 gene Proteins 0.000 description 1
- 101150011456 PIN8 gene Proteins 0.000 description 1
- 102100026114 Peptidyl-prolyl cis-trans isomerase NIMA-interacting 1 Human genes 0.000 description 1
- 230000004913 activation Effects 0.000 description 1
- 230000033228 biological regulation Effects 0.000 description 1
- 238000001816 cooling Methods 0.000 description 1
- 230000001419 dependent effect Effects 0.000 description 1
- 238000001514 detection method Methods 0.000 description 1
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- 230000006698 induction Effects 0.000 description 1
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- 238000005457 optimization Methods 0.000 description 1
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Classifications
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- H—ELECTRICITY
- H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
- H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
- H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
- H05B41/14—Circuit arrangements
- H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
- H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
- H05B41/282—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices
- H05B41/2825—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices by means of a bridge converter in the final stage
- H05B41/2827—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices by means of a bridge converter in the final stage using specially adapted components in the load circuit, e.g. feed-back transformers, piezoelectric transformers; using specially adapted load circuit configurations
Definitions
- the present invention relates to a circuit arrangement for operating lamps.
- the invention mainly relates to the operation of low pressure gas discharge lamps. Apart from aspects concerning the preheating, the invention is also applicable to control gear for LEDs.
- the circuit arrangement includes a stop device, which can prevent the switching on of the electronic switches of the half-bridge inverter and releases only during an on-time.
- the on-time depends on a lamp parameter, which can close a loop.
- a disadvantage of this circuit is that the ignition burst for the lamp depends on the tolerances of the load circuit components.
- the object of the present invention is therefore a method for controlling a half-bridge circuit in which a firing burst for the discharge lamp is relatively independent of the tolerances of the load circuit components. Also, the ignition burst with relatively magnetically strong saturating lamp inductor should be generated. In addition, a corresponding half-bridge circuit is to be provided.
- an active on-time of the switches of the half-bridge circuit is fixed during an operating phase at the operating frequency specified. This requires no regulation of the lamp current or the lamp power during operation.
- the preheat frequency is such that the active on-time of the switches of the half-bridge circuit in the preheat phase is less than a quarter of the resonant period while the operating frequency is so low that the active on-time is greater than a quarter of the resonant period minus a storage time the half-bridge switch is.
- a minimum frequency or time range can be specified, in the passage through an effective preheating and a safe ignition is possible.
- the defined period of time during which the frequency is lowered continuously should be between 1 ms and 100 ms. This time is sufficient to ensure a safe ignition.
- a symmetrical Zündleerlaufstrombegrenzung occurs.
- the load circuit current it is advantageous to limit the load circuit current to a temperature-dependent limit value.
- the temperature dependence of the saturation induction of the lamp inductor can also be taken into account.
- the half-bridge circuit has bipolar half-bridge switches with basic series capacitors in the control circuits.
- the storage time of the bipolar transistors can be further reduced.
- the half-bridge circuit is to be improved to the effect that regardless of the tolerances of the load circuit components always a defined ignition burst is possible. It is always the goal to obtain the least possible losses so that little or no cooling measures are required.
- Fig. 1 shows the voltage on the Last Vietnamesekondensator, which is usually connected in parallel with the lamp to be operated.
- the idling curve U CL results as a function of the frequency.
- the maximum of this curve is at the resonant frequency f res .
- There the highest voltage is to be observed on the load circuit capacitor.
- the lamp ignites at an ignition voltage U z , which is slightly below the voltage maximum. This ignition voltage U z is achieved at a firing frequency f flammable.
- the s is typically between 0.4 s and 2
- the lamp is heated to a preheat frequency f preheating, the ignition significantly higher than the ignition frequency f lies.
- f preheat the voltage across the lamp is well below the ignition voltage U z .
- the lamp After preheating the lamp can be ignited in the ideal case, characterized in that the frequency of the preheating frequency f preheat is reduced to a fixed ignition frequency f flammable. Due to tolerances of the load circuit components, however, the course of the load circuit capacitor voltage can change so that at the fixed predetermined frequency, the ignition voltage U z is not reached or unnecessarily high. The lamp would not ignite in this case, or it would take place too high a component load at too high a voltage.
- the load circuit frequency continuously preheating by the preheat frequency f on the resonant frequency f res (typically 50 to 60 kHz) to the operating frequency f for operation to reduce (typically 40 to 50 kHz).
- the open circuit voltage (lamp has not yet ignited) increases according to arrow P1. She reaches at a previously unknown or undefined frequency, the ignition voltage U z . Now the voltage on the load circuit capacitor drops to the operating voltage U CB and the load circuit frequency is further reduced until finally the operating point AP at the operating frequency f operation is reached, as shown in Fig. 1 indicated by arrow P2. It will therefore come regardless of the component tolerances to a firing burst, so that the lamp is safely put into operation without being exposed to high voltages.
- the preheat frequency f preheat is selected so that the on-time is on-preheat ⁇ 1 ⁇ 4 T res , where T res represents the idle period.
- a state machine then increases the active time t on-betrier> 1 ⁇ 4 T res - t s, so that the frequency drops to the operating frequency f becrieb.
- t s entsprich the storage time of the collector current in the use of bipolar transistors.
- a one-time t on is in Fig. 4 and corresponds to that time in which the base current I B of a bipolar transistor of the half-bridge circuit is greater than 0 during a half-period.
- FIG Fig. 2 A half-bridge circuit for exemplifying the invention is shown in FIG Fig. 2 played.
- the half-bridge switches Q1 and Q2 are designed as bipolar transistors.
- the two switches Q1 and Q2 are connected in series, with the intermediate circuit voltage having the poles VZW_PLUS and VZW_MINUS being applied to the series circuit.
- Base and emitter of the switch Q1 are connected through a resistor R11.
- the base of the switch Q1 is connected in parallel with a first winding of a transformer TR1 to the node N1 via a parallel connection of a resistor R42 with an RC series circuit R3, C29.
- the emitter of the switch Q2 is connected through a resistor R6 to the negative terminal VZW_MINUS and a resistor R12 bridges the base and the emitter of the switch Q2.
- the base of the switch Q2 is connected to the negative terminal VZW_MINUS via a parallel connection of a resistor R43 with an RC series circuit R4, C30 in series with a second winding of the transformer TR1.
- Capacitors C29 and C30 cause the base current to lead. In addition, they serve to reduce the storage time, as related below Fig. 4 is explained.
- a capacitor C8 is connected in parallel to the diode D9 and acts as a trapezoidal capacitor.
- the transformer TR1 has a third winding through which a stop function is controlled.
- This third winding is coupled to the AC terminals of a full-bridge rectifier formed by diodes D1, D2, D3 and D4.
- the DC connections of this rectifier are parallel to an electronic switch V2.
- the third winding, the Rectifier and the switch V2 form a stop device.
- the switch V2 is a MOSFET transistor, which is connected to the source terminal to the reference potential VCC_MINUS.
- the switch V2 short-circuits the third winding of the transformer TR1 via the rectifier.
- the control inputs of the electronic switches Q1 and Q2 are short-circuited via the transformer TR1, so that the two switches are turned off.
- the switch V2 is controlled by a timer U1.
- This timer is realized by a CMOS-IC 555.
- the circuit U1 provides the stop signal to PIN3.
- the signal In order to achieve the correct polarity for driving the switch V2, the signal must be inverted. This is achieved by the inverter U2-D.
- the supply terminals VCC_PLUS and VCC_MINUS are provided, which are connected to PIN8 and PIN1 of the circuit.
- the connection point between the resistor R1 and the capacitor C1 is connected to both PIN6 and PIN7 of the circuit U1 to give the timer the appropriate time constant.
- PIN4 of the circuit U1 forms a reset input and must be high-ohmic with the positive operating voltage be connected via R2, so that the desired functionality of the circuit U1 sets.
- PIN2 of the circuit U1 forms a trigger input and is first connected via a resistor R25 to the positive supply terminal VCC_PLUS. To trigger the timer, PIN2 requires a negative pulse. This is supplied by a comparator U3-A, which can be realized for example by the component LM293. The trigger pulse is delivered directly to PIN2 of the circuit U1.
- the inverting input of the comparator U3-A is connected via a resistor R28 to VCC_PLUS and via a resistor R29 to VCC_MINUS.
- the non-inverting input of the comparator U3-A is fed by the DC output of a full-bridge rectifier GL1.
- the secondary winding of a current transformer or transformer TR3 is connected to the AC voltage input of this full-bridge rectifier GL1.
- the primary winding of the transformer TR3 is between the load circuit and the terminal Il1 (see also Fig. 2 ).
- the DC output of the full-bridge rectifier Gl1 is terminated in a low-resistance manner with a series connection of the resistors R30 and R31.
- the non-inverting input of the comparator U3-A is a voltage that is proportional to the rectified load current.
- the voltage at the inverting input of the comparator U3-A is temporarily higher than the voltage at the non-inverting input. This results as a comparator signal, a negative trigger pulse.
- the components U3-A, R28, R29, R30, R31, GL and TR3 thus form a triggering device based on current zero crossing detection.
- the timer is triggered and switches off the transistor V2 for the on-time, whereby the activation of the switches Q1 and Q2 is enabled.
- the output signal of a further comparator U3-B is connected to PIN4 of the circuit U1. Its inverting input is between resistors R30 and R31. The non-inverting input is connected between a series connection of resistors R26 and R27, which in turn is connected between the supply terminals VCC_PLUS and VCC_MINUS. So if the rectified load current exceeds a certain value, the timer is reset and thus the respective half-bridge switch is actively switched off.
- the duration of the preheating time (typically 0.4 to 2 s) and the duration of the transitional period from the preheat frequency f preheat to the operating frequency f operation (preferably 1 ms to 100 ms, so that charge carriers can build up in the lamp for the ignition) is over PIN5 of the circuit U1 is set.
- the switching time from the preheating phase to the operating phase is determined by an RC element consisting of a series connection of a resistor R24 with a capacitor C2.
- the capacitor C2 is between PIN5 and the negative supply terminal VCC_MINUS.
- the duration of the preheat time is determined with the RC series circuit R23, C3, which is located between the two supply terminals VCC_MINUS and VCC_PLUS.
- a node N2 between the two devices R23 and C3 is connected to the input of inverter U2-B and a diode D6 to the resistor R24 and thus to PIN5 of the circuit U1.
- Diode D6 dynamically switches resistor R24 parallel to C2 during the preheat phase to ensure the desired timing.
- the comparator can be constructed from a current mirror. This is also known as the "emitter-controlled differential comparator”.
- the goal is to operate the lamp with as few losses as possible. This also means achieving as low-loss switching as possible. This is possible in inductive operation of the lamp.
- the voltage is pulled to 0 and the current switched in this state.
- the current during switching should be as low as possible. Therefore, the respective bipolar transistor Q1, Q2 is turned on in the current zero crossing, which is due to the base current I B in Fig. 4 is indicated.
- This current profile of the base current I B is established in the case of an ideal current transformer TR1, wherein the base current I B in phase with the current I C in the load circuit.
- the base current I B is switched off by the timer or the switch V2. Due to a charge carrier excess in the bipolar transistor results in a storage time t s , so that the respective bipolar transistor only turns off at time t 1 actually.
- a base series capacitor C29 is connected to the base of the bipolar transistor Q1 and a base series capacitor C30 is connected to the base of the bipolar transistor Q2.
- the base current increases faster after switching on, which is indicated by the dashed line I B 'in Fig. 4 is indicated.
- the shortened storage time t s ' can also simultaneously increase the on-time, starting from t 0 to t on '. In this way, the losses in the bipolar transistors Q1 and Q2 can be further reduced.
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- Engineering & Computer Science (AREA)
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- Circuit Arrangements For Discharge Lamps (AREA)
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- Dc-Dc Converters (AREA)
Abstract
Description
Die vorliegende Erfindung betrifft eine Schaltungsanordnung zum Betreiben von Lampen. Die Erfindung bezieht sich hauptsächlich auf den Betrieb von Niederdruck-Gasentladungslampen. Bis auf Aspekte, die die Vorheizung betreffen, ist die Erfindung auch auf Betriebsgeräte für LEDs anwendbar.The present invention relates to a circuit arrangement for operating lamps. The invention mainly relates to the operation of low pressure gas discharge lamps. Apart from aspects concerning the preheating, the invention is also applicable to control gear for LEDs.
Aus der gattungsgemäßen Druckschrift
Die Aufgabe der vorliegenden Erfindung besteht somit darin, ein Verfahren zum Steuern einer Halbbrückenschaltung bereitzustellen, bei dem ein Zündburst für die Entladungslampe verhältnismäßig unabhängig von den Toleranzen der Lastkreisbauteile ist. Auch soll der Zündburst mit relativ magnetisch stark sättigender Lampendrossel generierbar sein. Darüber hinaus soll eine entsprechende Halbbrückenschaltung bereitgestellt werden.The object of the present invention is therefore a method for controlling a half-bridge circuit in which a firing burst for the discharge lamp is relatively independent of the tolerances of the load circuit components. Also, the ignition burst with relatively magnetically strong saturating lamp inductor should be generated. In addition, a corresponding half-bridge circuit is to be provided.
Erfindungsgemäß wird diese Aufgabe gelöst durch eine Schaltungsanordnung zum Betreiben von Lampen mit folgenden Merkmalen:
- Halbbrückenanordnung, die einen oberen und einen unteren elektronischen Schalter aufweist, die in Serie geschaltet sind, jeweils einen Steueranschluss aufweisen und an ihrem Verbindungspunkt einen Mittelpunkt bilden,
- am Mittelpunkt ist ein Lastkreis angeschlossen, in den ein Lastkreisstrom fließt,
- der Lastkreis enthält ein Reaktanznetzwerk mit einer Resonanzfrequenz, an das eine Lampe anschließbar ist,
- der Lastkreis ist so bemessen, dass in einem Normalbetrieb für eine angeschlossene Lampe nach dem Öffnen eines der elektronischen Schalter die Spannung am jeweils anderen der elektronischen Schalter nach einer Umschwing-Zeit zu Null wird,
- die Schaltungsanordnung umfasst eine Rückkoppeleinrichtung, die eine Rückkoppelgröße aus dem Lastkreis derart mit den Steueranschlüssen der elektronischen Schalter koppelt, dass die elektronischen Schalter abwechselnd eingeschaltet werden,
- die Schaltanordnung umfasst eine Stopp-Einrichtung, die mit den Steueranschlüssen der elektronischen Schalter gekoppelt ist und einen Eingang aufweist, an den ein Stoppsignal anlegbar ist, wobei die Stopp-Einrichtung ein Einschalten der elektronischen Schalter verhindert, solange das Stoppsignal einen Aus-Zustand aufweist,
- die Schaltungsanordnung einen Timer aufweist, der mit dem Eingang der Stopp-Einrichtung gekoppelt ist und das Stoppsignal bereitstellt, das einen Ein-Zustand und einen Aus-Zustand annehmen kann,
- die Schaltungsanordnung umfasst eine Triggereinrichtung, die jeweils nach Ablauf der Umschwing-Zeit ein Triggersignal an den Timer abgibt, spätestens jedoch, wenn der Lastkreisstrom zu Null wird,
- der Timer schaltet das Stoppsignal in den Ein-Zustand für die Dauer einer Ein-Zeit, wobei
- durch eine Ablaufsteuerung zunächst eine Ein-Zeit während der Vorheizzeit der Elektroden der Lampen durch den Timer vorgegeben ist, die kleiner als ein Viertel der Periodendauer der Resonanzfrequenz des Reaktanznetzwerkes ist und nach der Vorheizzeit der Elektroden der Lampen diese Ein-Zeit kontinuierlich erhöht wird, bis sie mindestens einem Viertel der Periodendauer der Resonanzfrequenz des Reaktanznetzwerkes entspricht. Unter Ein-Zeit ist hier eine Einschaltzeit der Schalter zu verstehen.
- Half-bridge arrangement comprising an upper and a lower electronic switch, which are connected in series, each having a control terminal and form a center point at its connection point,
- at the center a load circuit is connected, into which a load circuit current flows,
- the load circuit contains a reactance network with a resonance frequency to which a lamp can be connected,
- the load circuit is dimensioned such that in normal operation for a connected lamp after opening one of the electronic switches, the voltage at the other of the electronic switches becomes zero after a transient time,
- the circuit arrangement comprises a feedback device which couples a feedback quantity from the load circuit to the control terminals of the electronic switches such that the electronic switches are switched on alternately,
- the switching arrangement comprises a stop device which is coupled to the control terminals of the electronic switches and has an input to which a stop signal can be applied, wherein the stop device prevents switching on the electronic switch, as long as the stop signal has an off state,
- the circuitry comprises a timer coupled to the input of the stop device and providing the stop signal that may assume an on state and an off state,
- the circuit arrangement comprises a trigger device, which in each case emits a trigger signal to the timer after the end of the transient time, at the latest, however, when the load circuit current becomes zero,
- the timer switches the stop signal to the on state for the duration of an on time, wherein
- by a sequence control initially a on-time during the preheating time of the electrodes of the lamps is predetermined by the timer, which is less than a quarter of the period of the resonance frequency of the reactance network and after the preheating time of the electrodes of the lamps, this on-time is continuously increased until it corresponds to at least a quarter of the period of the resonance frequency of the reactance network. On-time is here an on-time of the switch to understand.
In vorteilhafter Weise ist damit eine stabile Erzeugung von quasi resonanten Zündbursts mit geringer Toleranzabhängigkeit und ohne spezielles Timing bei magnetisch sättigender Lampendrossel möglich. Außerdem ist eine thermische Optimierung der Gesamtschaltung erreichbar.Advantageously, a stable generation of quasi-resonant firing bursts with low tolerance dependency and without special timing in magnetically saturating lamp inductor is thus possible. In addition, a thermal optimization of the overall circuit can be achieved.
Entsprechend einer besonderen Ausführungsform ist eine aktive Ein-Zeit der Schalter der Halbbrückenschaltung während einer Betriebsphase bei der Betriebsfrequenz fest vorgegeben. Damit bedarf es keiner Regelung des Lampenstroms bzw. der Lampenleistung im Betrieb.According to a particular embodiment, an active on-time of the switches of the half-bridge circuit is fixed during an operating phase at the operating frequency specified. This requires no regulation of the lamp current or the lamp power during operation.
Vorzugsweise ist die Vorheizfrequenz so hoch, dass die aktive Ein-Zeit der Schalter der Halbbrückenschaltung in der Vorheizphase kleiner als ein Viertel der Resonanzperiode ist, während die Betriebsfrequenz so niedrig ist, dass die aktive Ein-Zeit größer als ein Viertel der Resonanzperiode abzüglich einer Speicherzeit der Halbbrückenschalter ist. Damit kann ein minimaler Frequenz- bzw. Zeitbereich vorgegeben werden, bei dessen Durchlaufen ein wirksames Vorheizen und ein sicheres Zünden möglich ist.Preferably, the preheat frequency is such that the active on-time of the switches of the half-bridge circuit in the preheat phase is less than a quarter of the resonant period while the operating frequency is so low that the active on-time is greater than a quarter of the resonant period minus a storage time the half-bridge switch is. Thus, a minimum frequency or time range can be specified, in the passage through an effective preheating and a safe ignition is possible.
Die definierte Zeitdauer, während der die Frequenz kontinuierlich abgesenkt wird, sollte zwischen 1 ms und 100 ms liegen. Diese Zeit ist ausreichend, damit ein sicheres Zünden gewährleistet ist.The defined period of time during which the frequency is lowered continuously should be between 1 ms and 100 ms. This time is sufficient to ensure a safe ignition.
Entsprechend einer weiteren bevorzugten Ausführungsform erfolgt eine symmetrische Zündleerlaufstrombegrenzung. Damit ist eine automatische Anpassung der Zündfrequenz an Lastkreistoleranzen und eine sättigende Lampendrossel möglich. Insbesondere ist es vorteilhaft, den Lastkreisstrom auf einen temperaturabhängigen Grenzwert zu begrenzen. Dadurch kann auch die Temperaturabhängigkeit der Sättigungsinduktion der Lampendrossel berücksichtigt werden.According to a further preferred embodiment, a symmetrical Zündleerlaufstrombegrenzung occurs. For an automatic adjustment of the ignition frequency to load circle tolerances and a saturating lamp inductor is possible. In particular, it is advantageous to limit the load circuit current to a temperature-dependent limit value. As a result, the temperature dependence of the saturation induction of the lamp inductor can also be taken into account.
Ferner ist es vorteilhaft, wenn die Halbbrückenschaltung bipolare Halbbrückenschalter mit Basisserienkondensatoren in den Steuerkreisen aufweist. Damit kann die Speicherzeit der Bipolartransistoren weiter reduziert werden.Furthermore, it is advantageous if the half-bridge circuit has bipolar half-bridge switches with basic series capacitors in the control circuits. Thus, the storage time of the bipolar transistors can be further reduced.
Die vorliegende Erfindung wird nun anhand der beigefügten Zeichnungen näher erläutert, in denen zeigen:
- Fig. 1
- einen Verlauf der Spannung am Resonanzkreiskonden- sator in Abhängigkeit von der Frequenz;
- Fig. 2
- ein Schaltungsdiagramm eines Teils einer Halbbrü- ckenschaltung;
- Fig. 3
- ein Schaltungsdiagramm von Ansteuerkomponenten für die Halbbrückenschaltung von
Fig. 2 und - Fig. 4
- ein Strom/Spannungsdiagramm des Lastkreises.
- Fig. 1
- a profile of the voltage at Resonanzkreiskonden- sator as a function of frequency;
- Fig. 2
- a circuit diagram of a part of a half-bridge circuit;
- Fig. 3
- a circuit diagram of driving components for the half-bridge circuit of
Fig. 2 and - Fig. 4
- a current / voltage diagram of the load circuit.
Das nachfolgend näher geschilderte Ausführungsbeispiel stellt eine bevorzugte Ausführungsform der vorliegenden Erfindung dar.The embodiment described in more detail below represents a preferred embodiment of the present invention.
Wie eingangs erwähnt, soll die Halbbrückenschaltung dahingehend verbessert werden, dass unabhängig von den Toleranzen der Lastkreisbauteile stets ein definierter Zündburst möglich ist. Dabei ist es auch immer das Ziel, möglichst geringe Verluste zu erhalten, damit keine oder nur geringe Kühlmaßnahmen erforderlich sind.As mentioned above, the half-bridge circuit is to be improved to the effect that regardless of the tolerances of the load circuit components always a defined ignition burst is possible. It is always the goal to obtain the least possible losses so that little or no cooling measures are required.
In der Vorheizphase, die typischerweise zwischen 0,4 s und 2 s liegt, wird die Lampe mit einer Vorheizfrequenz fvorheiz geheizt, die deutlich höher als die Zündfrequenz fzünd liegt. Bei dieser Vorheizfrequenz fvorheiz liegt die Spannung an der Lampe deutlich unter der Zündspannung Uz.In the preheating phase, the s is typically between 0.4 s and 2, the lamp is heated to a preheat frequency f preheating, the ignition significantly higher than the ignition frequency f lies. At this preheating frequency f preheat the voltage across the lamp is well below the ignition voltage U z .
Während des Betriebs der Lampe stellt sich an dem Lastkreiskondensator die Spannung UCB ein. Ihr Verlauf ist in
Nach dem Vorheizen kann die Lampe im Idealfall dadurch gezündet werden, dass die Frequenz von der Vorheizfrequenz fvorheiz auf eine feste Zündfrequenz fzünd reduziert wird. Aufgrund von Toleranzen der Lastkreisbauteile kann sich jedoch der Verlauf der Lastkreiskondensatorspannung so ändern, dass bei der fest vorgegebenen Frequenz die Zündspannung Uz nicht erreicht ist oder unnötig hoch liegt. Die Lampe würde in diesem Fall nicht zünden bzw. es würde eine zu hohe Bauteilebelastung bei zu hoher Spannung erfolgen.After preheating the lamp can be ignited in the ideal case, characterized in that the frequency of the preheating frequency f preheat is reduced to a fixed ignition frequency f flammable. Due to tolerances of the load circuit components, however, the course of the load circuit capacitor voltage can change so that at the fixed predetermined frequency, the ignition voltage U z is not reached or unnecessarily high. The lamp would not ignite in this case, or it would take place too high a component load at too high a voltage.
Erfindungsgemäß ist daher vorgesehen, die Lastkreisfrequenz kontinuierlich von der Vorheizfrequenz fvorheiz über die Resonanzfrequenz fres (typischerweise 50 bis 60 kHz) zur Betriebsfrequenz fbetrieb (typischerweise 40 bis 50kHz) zu reduzieren. Dabei steigt die Leerlaufspannung (Lampe hat noch nicht gezündet) gemäß Pfeil P1 an. Sie erreicht bei einer zuvor nicht bekannten oder nicht festgelegten Frequenz die Zündspannung Uz. Nun sinkt die Spannung an dem Lastkreiskondensator auf die Betriebsspannung UCB und die Lastkreisfrequenz wird weiter reduziert, bis schließlich der Arbeitspunkt AP bei der Betriebsfrequenz fbetrieb erreicht ist, wie dies in
Um zu gewährleisten, dass die Lampe zunächst wirksam vorgeheizt, dann gezündet und schließlich wunschgemäß betrieben wird, wird die Vorheizfrequenz fvorheiz so gewählt, dass die aktive Einschaltzeit ton-vorheiz < ¼ Tres ist, wobei Tres die Leerlaufresonanzperiode darstellt. Eine Ablaufsteuereinheit erhöht dann die aktive Einschaltzeit ton-betrier > ¼ Tres - ts , so dass die Frequenz auf die Betriebsfrequenz fbecrieb sinkt. Dabei entsprich ts der Speicherzeit des Kollektorstroms beim Einsatz von Bipolartransistoren. Eine Ein-Zeit ton ist in
Eine Halbbrückenschaltung zur beispielhaften Realisierung der Erfindung ist in
Parallel zur Emitter-Kollektor-Strecke des Schalters Q1 liegt eine Diode D9 in Flussrichtung und ebenso eine Diode D10 parallel zur Emitter-Kollektor-Strecke des Schalters Q2. Diese Dioden D9 und D10 dienen als Freilaufdioden der Schalter Q1 und Q2. Ein Kondensator C8 liegt parallel zu der Diode D9 und wirkt als Trapezkondensator.Parallel to the emitter-collector path of the switch Q1 is a diode D9 in the flow direction and also a diode D10 parallel to the emitter-collector path of the switch Q2. These diodes D9 and D10 serve as free-wheeling diodes of the switches Q1 and Q2. A capacitor C8 is connected in parallel to the diode D9 and acts as a trapezoidal capacitor.
Zusätzlich zu den zwei bereits beschriebenen Wicklungen besitzt der Transformator TR1 eine dritte Wicklung, über die eine Stoppfunktion gesteuert wird. Diese dritte Wicklung ist mit den Wechselspannungs-Anschlüssen eines Vollbrückengleichrichters gekoppelt, der von den Dioden D1, D2, D3 und D4 gebildet wird. Die Gleichspannungs-Anschlüsse dieses Gleichrichters liegen parallel zu einem elektronischen Schalter V2. Die dritte Wicklung, der Gleichrichter und der Schalter V2 bilden eine Stoppeinrichtung. Bei dem Schalter V2 handelt es sich um einen MOSFET-Transistor, der mit dem Sourceanschluss mit dem Bezugspotenzial VCC_MINUS verbunden ist. Sobald am Gate des Schalters V2 ein Stoppsignal anliegt, das einem Aus-Zustand entspricht, schließt der Schalter V2 über den Gleichrichter die dritte Wicklung des Transformators TR1 kurz. Damit werden über den Transformator TR1 auch die Steuereingänge der elektronischen Schalter Q1 und Q2 kurzgeschlossen, so dass die beiden Schalter ausgeschaltet werden.In addition to the two windings already described, the transformer TR1 has a third winding through which a stop function is controlled. This third winding is coupled to the AC terminals of a full-bridge rectifier formed by diodes D1, D2, D3 and D4. The DC connections of this rectifier are parallel to an electronic switch V2. The third winding, the Rectifier and the switch V2 form a stop device. The switch V2 is a MOSFET transistor, which is connected to the source terminal to the reference potential VCC_MINUS. As soon as a stop signal is present at the gate of the switch V2, which corresponds to an off state, the switch V2 short-circuits the third winding of the transformer TR1 via the rectifier. Thus, the control inputs of the electronic switches Q1 and Q2 are short-circuited via the transformer TR1, so that the two switches are turned off.
Gesteuert wird der Schalter V2 von einem Timer U1. In dem Beispiel von
Zur Energieversorgung des Schaltkreises U1 sind die Versorgungsklemmen VCC_PLUS und VCC_MINUS vorgesehen, die an PIN8 und PIN1 des Schaltkreises angeschlossen sind.To supply power to the circuit U1, the supply terminals VCC_PLUS and VCC_MINUS are provided, which are connected to PIN8 and PIN1 of the circuit.
Die Serienschaltung eines Widerstands R1 und eines Kondensators C1, die zwischen die beiden Versorgungsklemmen VCC_PLUS und VCC_MINUS geschaltet ist, führt zu einer Zeitkonstanten, die die Ein-Zeit ton bestimmt. Der Verbindungspunkt zwischen dem Widerstand R1 und dem Kondensator C1 ist sowohl mit PIN6 als auch mit PIN7 der Schaltung U1 verbunden, um dem Timer die entsprechende Zeitkonstante vorzugeben. PIN4 der Schaltung U1 bildet einen Reset-Eingang und muss mit der positiven Betriebsspannung hochohmig über R2 verbunden werden, damit sich die gewünschte Funktionalität der Schaltung U1 einstellt.The series connection of a resistor R1 and a capacitor C1, which is connected between the two supply terminals VCC_PLUS and VCC_MINUS, leads to a time constant which determines the on-time t on . The connection point between the resistor R1 and the capacitor C1 is connected to both PIN6 and PIN7 of the circuit U1 to give the timer the appropriate time constant. PIN4 of the circuit U1 forms a reset input and must be high-ohmic with the positive operating voltage be connected via R2, so that the desired functionality of the circuit U1 sets.
PIN2 der Schaltung U1 bildet einen Triggereingang und ist zunächst über einen Widerstand R25 mit der positiven Versorgungsklemme VCC_PLUS verbunden. Zum Auslösen des Timers ist an PIN2 ein negativer Impuls nötig. Dieser wird von einem Komparator U3-A geliefert, der beispielsweise durch das Bauteil LM293 realisiert sein kann. Der Triggerimpuls wird direkt an PIN2 der Schaltung U1 geliefert. Der invertierende Eingang der Komparators U3-A ist über einen Widerstand R28 mit VCC_PLUS und über einen Widerstand R29 mit VCC_MINUS verbunden.PIN2 of the circuit U1 forms a trigger input and is first connected via a resistor R25 to the positive supply terminal VCC_PLUS. To trigger the timer, PIN2 requires a negative pulse. This is supplied by a comparator U3-A, which can be realized for example by the component LM293. The trigger pulse is delivered directly to PIN2 of the circuit U1. The inverting input of the comparator U3-A is connected via a resistor R28 to VCC_PLUS and via a resistor R29 to VCC_MINUS.
Der nicht invertierende Eingang des Komparators U3-A wird vom Gleichspannungsausgang eines Vollbrückengleichrichters GL1 gespeist. An den Wechselspannungseingang dieses Vollbrückengleichrichters GL1 ist die Sekundärwicklung eines Stromübertragers bzw. Transformators TR3 geschaltet. Die Primärwicklung des Transformators TR3 liegt zwischen dem Lastkreis und der Klemme Il1 (vergleiche auch
Ferner ist der Gleichspannungsausgang des Vollbrückengleichrichters Gl1 niederohmig mit einer Serienschaltung der Widerstände R30 und R31 abgeschlossen. Damit liegt am nicht invertierenden Eingang des Komparators U3-A eine Spannung an, die proportional zum gleichgerichteten Laststrom ist. Beim Nulldurchgang des Laststroms ist die Spannung am invertierenden Eingang des Komparators U3-A kurzzeitig größer als die Spannung am nicht invertierenden Eingang. Dadurch ergibt sich als Komparatorsignal ein negativer Triggerimpuls. Die Bauelemente U3-A, R28, R29, R30, R31, GL und TR3 bilden somit eine Triggereineinrichtung auf Basis einer Stromnulldurchgangsdetektion. Sobald der Laststrom einen Nulldurchgang aufweist, wird der Timer getriggert und schaltet für die Ein-Zeit den Transistor V2 ab, wodurch die Ansteuerung der Schalter Q1 und Q2 freigegeben wird.Furthermore, the DC output of the full-bridge rectifier Gl1 is terminated in a low-resistance manner with a series connection of the resistors R30 and R31. Thus, at the non-inverting input of the comparator U3-A is a voltage that is proportional to the rectified load current. At the zero crossing of the load current, the voltage at the inverting input of the comparator U3-A is temporarily higher than the voltage at the non-inverting input. This results as a comparator signal, a negative trigger pulse. The components U3-A, R28, R29, R30, R31, GL and TR3 thus form a triggering device based on current zero crossing detection. As soon as the load current has a zero crossing, the timer is triggered and switches off the transistor V2 for the on-time, whereby the activation of the switches Q1 and Q2 is enabled.
Zum Rücksetzen des Timers wird an PIN4 der Schaltung U1 das Ausgangssignal eines weiteren Komparators U3-B geschaltet. Sein invertierender Eingang liegt zwischen den Widerständen R30 und R31. Der nicht invertierende Eingang liegt zwischen einer Serienschaltung von Widerständen R26 und R27, die ihrerseits zwischen die Versorgungsklemmen VCC_PLUS und VCC_MINUS geschaltet ist. Wenn also der gleichgerichtete Laststrom einen gewissen Wert überschreitet, wird der Timer zurückgesetzt und damit der jeweilige Halbbrückenschalter aktiv ausgeschaltet.To reset the timer, the output signal of a further comparator U3-B is connected to PIN4 of the circuit U1. Its inverting input is between resistors R30 and R31. The non-inverting input is connected between a series connection of resistors R26 and R27, which in turn is connected between the supply terminals VCC_PLUS and VCC_MINUS. So if the rectified load current exceeds a certain value, the timer is reset and thus the respective half-bridge switch is actively switched off.
Die Dauer der Vorheizzeit (typischerweise 0,4 bis 2 s) und die Dauer der Übergangszeit von der Vorheizfrequenz fvorheiz zu der Betriebsfrequenz fbetrieb (vorzugsweise 1 ms bis 100 ms, damit sich für die Zündung Ladungsträger in der Lampe aufbauen können) wird über PIN5 der Schaltung U1 eingestellt. Die Umschaltzeit von der Vorheizphase in die Betriebsphase wird durch ein RC-Glied bestehend aus einer Serienschaltung eines Widerstands R24 mit einem Kondensator C2 bestimmt. Der Kondensator C2 liegt zwischen PIN5 und der negativen Versorgungsklemme VCC_MINUS. Die Dauer der Vorheizzeit hingegen wird mit der RC-Serienschaltung R23, C3, die zwischen den beiden Versorgungsklemmen VCC_MINUS und VCC_PLUS liegt, bestimmt. Ein Knoten N2 zwischen den beiden Bauelementen R23 und C3 liegt am Eingang von Inverter U2-B und eine Diode D6 an dem Widerstand R24 und somit an PIN5 der Schaltung U1. Die Diode D6 schaltet den Widerstand R24 nur während der Vorheizphase dynamisch parallel zu C2, um das gewünschte Timing sicherzustellen.The duration of the preheating time (typically 0.4 to 2 s) and the duration of the transitional period from the preheat frequency f preheat to the operating frequency f operation (preferably 1 ms to 100 ms, so that charge carriers can build up in the lamp for the ignition) is over PIN5 of the circuit U1 is set. The switching time from the preheating phase to the operating phase is determined by an RC element consisting of a series connection of a resistor R24 with a capacitor C2. The capacitor C2 is between PIN5 and the negative supply terminal VCC_MINUS. The duration of the preheat time, however, is determined with the RC series circuit R23, C3, which is located between the two supply terminals VCC_MINUS and VCC_PLUS. A node N2 between the two devices R23 and C3 is connected to the input of inverter U2-B and a diode D6 to the resistor R24 and thus to PIN5 of the circuit U1. Diode D6 dynamically switches resistor R24 parallel to C2 during the preheat phase to ensure the desired timing.
Durch die Halbbrückenschaltung gemäß den
wobei W1TR3 und W2TR3 die Windungszahlen des Transformators TR3 darstellen.By the half-bridge circuit according to the
where W 1TR3 and W 2TR3 represent the numbers of turns of the transformer TR3.
In der Triggerschaltung des Timers kann der Komparator aus einem Stromspiegel aufgebaut sein. Dieser ist auch unter der Bezeichnung "Emitter gesteuerter Differenzialkomparator" bekannt.In the trigger circuit of the timer, the comparator can be constructed from a current mirror. This is also known as the "emitter-controlled differential comparator".
Wie erwähnt, ist es Ziel, die Lampe mit möglichst wenig Verlusten zu betreiben. Hierzu zählt auch, ein möglichst verlustarmes Schalten zu erreichen. Dies ist im induktiven Betrieb der Lampe möglich. Die Spannung wird hierzu auf 0 gezogen und der Strom in diesem Zustand geschaltet. Gleichzeitig sollte der Strom beim Schalten möglichst gering sein. Daher wird der jeweilige Bipolartransistor Q1, Q2 im Strom Nulldurchgang eingeschaltet, was durch den Basisstrom IB in
Um diese Speicherzeit zu verkürzen, wird, wie erwähnt, ein Basisserienkondensator C29 an die Basis des Bipolartransistors Q1 und ein Basisserienkondensator C30 an die Basis des Bipolartransistors Q2 geschaltet. Hierdurch steigt der Basisstrom nach dem Einschalten rascher an, was durch die Strichpunktlinie IB' in
Claims (6)
- Circuit arrangement for operation of lamps having the following features:- a half-bridge arrangement which has an upper and a lower electronic switch (Q1, Q2), which are connected in series, each have a control connection and form a neutral point (N1) at their connection point,- a load circuit in which a load circuit current (IL1) flows is connected to the neutral point (N1),- the load circuit contains a reactance network having a resonant frequency, to which a lamp can be connected,- the load circuit is designed such that, during normal operation for a connected lamp after the opening of one of the electronic switches (Q1, Q2), the voltage on the respective other one of the electronic switches (Q1, Q2) tends to zero after a transient time,- the circuit arrangement comprises a feedback device which couples a feedback variable from the load circuit to the control connections of the electronic switches (Q1, Q2), such that the electronic switches (Q1, Q2) are switched on alternately,- the switching arrangement comprises a stop device, which is coupled to the control connections of the electronic switches (Q1, Q2) and has an input to which a stop signal can be applied, with the stop device preventing the electronic switches (Q1, Q2) from being switched on as long as the stop signal is in an off state,- the circuit arrangement comprises a timer, which is coupled to the input of the stop device and produces the stop signal, which can assume an on state and an off state,- the circuit arrangement comprises a trigger device which in each case emits a trigger signal to the timer after the transient time has elapsed, but at the latest when the load circuit current (ILS) is tending to zero,- the timer switches the stop signal to the on state for the duration of an on-time (ton),characterized in that- a sequence controller first of all presets an on-time (ton) during the preheating time of the electrodes of the lamps, by means of the timer, which time is shorter than one quarter of the period duration of the resonant frequency of the reactance network and, after the preheating time of the electrodes of the lamps, this on-time is continuously increased until it corresponds at least to one quarter of the period duration of the resonant frequency of the reactance network.
- Circuit arrangement according to Claim 1, characterized in that a threshold value device is provided, which compares the load circuit current (IL1) with a predeterminable current limit value, and, when this current limit value is reached, emits a reset signal to the timer and switches the stop device to the off state.
- Circuit arrangement according to Claim 1 or 2, characterized in that the on-time (ton) is increased continuously in 1 to 100 ms from the minimum value during the preheating time to the maximum value during operation of the lamps.
- Circuit arrangement according to Claims 1 to 3, characterized in that the on-time (ton) is predetermined to be fixed at the operating frequency during the operating phase of the lamps.
- Circuit arrangement according to Claim 4, characterized in that, in the case of bipolar half-bridge switches, the on-time (ton) in the operating phase of the lamps is greater than one quarter of the period duration of the reactance network minus a storage time ts.
- Circuit arrangement according to Claims 1 to 5, characterized in that the bipolar half-bridge switches (Q1, Q2) have base series capacitors (C29, C30) in the control loops.
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
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PCT/EP2007/050576 WO2008089839A1 (en) | 2007-01-22 | 2007-01-22 | Method for controlling a half-bridge circuit and corresponding half-bridge circuit |
Publications (2)
Publication Number | Publication Date |
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EP2111730A1 EP2111730A1 (en) | 2009-10-28 |
EP2111730B1 true EP2111730B1 (en) | 2010-11-24 |
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Application Number | Title | Priority Date | Filing Date |
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EP07704044A Not-in-force EP2111730B1 (en) | 2007-01-22 | 2007-01-22 | Method for controlling a half-bridge circuit and corresponding half-bridge circuit |
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Country | Link |
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US (1) | US8212495B2 (en) |
EP (1) | EP2111730B1 (en) |
AT (1) | ATE489836T1 (en) |
DE (1) | DE502007005800D1 (en) |
WO (1) | WO2008089839A1 (en) |
Cited By (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
DE102020130728A1 (en) | 2020-11-20 | 2022-05-25 | Osram Gmbh | CONTROL CIRCUIT FOR THE CONTROL INPUT OF A POWER TRANSISTOR OF A CLOCKED CONVERTER AND APPLICATION OF THE CONTROL CIRCUIT |
DE102021208416A1 (en) | 2021-08-03 | 2023-02-09 | Osram Gmbh | RESONANTLY OPERATED SWITCHED ISOLATION POWER CONVERTER AND METHOD OF DEEP DIMMING SUCH POWER CONVERTER |
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CN102843124B (en) | 2011-06-20 | 2015-03-11 | 昂宝电子(上海)有限公司 | System and method for driving bipolar junction transistor through adjustment of base current |
US8937437B2 (en) * | 2013-06-13 | 2015-01-20 | Osram Syvlania Inc. | Ballast with anti-striation circuit |
Family Cites Families (10)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US5382882A (en) * | 1993-04-20 | 1995-01-17 | General Electric Company | Power supply circuit for a gas discharge lamp |
DE19613077C2 (en) * | 1996-04-02 | 1999-10-14 | Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh | Circuit arrangement for operating electric lamps, especially free-swinging half-bridge converters |
US6072710A (en) * | 1998-12-28 | 2000-06-06 | Philips Electronics North America Corporation | Regulated self-oscillating resonant converter with current feedback |
ITMI991131A1 (en) * | 1999-05-21 | 2000-11-21 | St Microelectronics Srl | HALF-BRIDGE SEMI-BRIDGE PILOTING ARCHITECTURE AT VARIABLE FREQUENCY, IN PARTICULAR FOR ELECTRIC LOADS |
CN1363202A (en) * | 2000-02-10 | 2002-08-07 | 皇家菲利浦电子有限公司 | Protection circuit with NTC resistance |
DE10220471A1 (en) * | 2002-05-07 | 2003-11-20 | Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh | Circuit arrangement for operating discharge lamps |
DE102004028798A1 (en) * | 2004-06-15 | 2006-01-05 | Patent-Treuhand-Gesellschaft für elektrische Glühlampen mbH | Circuit with switch-off device for operation of light sources |
DE102005007348A1 (en) | 2005-02-17 | 2006-08-31 | Zumtobel Staff Gmbh | Spotlight with variable light emission characteristic |
DE102005007346A1 (en) * | 2005-02-17 | 2006-08-31 | Patent-Treuhand-Gesellschaft für elektrische Glühlampen mbH | Circuit arrangement and method for operating gas discharge lamps |
US7436127B2 (en) * | 2005-11-03 | 2008-10-14 | International Rectifier Corporation | Ballast control circuit |
-
2007
- 2007-01-22 WO PCT/EP2007/050576 patent/WO2008089839A1/en active Application Filing
- 2007-01-22 US US12/524,087 patent/US8212495B2/en not_active Expired - Fee Related
- 2007-01-22 AT AT07704044T patent/ATE489836T1/en active
- 2007-01-22 EP EP07704044A patent/EP2111730B1/en not_active Not-in-force
- 2007-01-22 DE DE502007005800T patent/DE502007005800D1/en active Active
Cited By (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
DE102020130728A1 (en) | 2020-11-20 | 2022-05-25 | Osram Gmbh | CONTROL CIRCUIT FOR THE CONTROL INPUT OF A POWER TRANSISTOR OF A CLOCKED CONVERTER AND APPLICATION OF THE CONTROL CIRCUIT |
DE102021208416A1 (en) | 2021-08-03 | 2023-02-09 | Osram Gmbh | RESONANTLY OPERATED SWITCHED ISOLATION POWER CONVERTER AND METHOD OF DEEP DIMMING SUCH POWER CONVERTER |
Also Published As
Publication number | Publication date |
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WO2008089839A1 (en) | 2008-07-31 |
EP2111730A1 (en) | 2009-10-28 |
US8212495B2 (en) | 2012-07-03 |
US20100102755A1 (en) | 2010-04-29 |
ATE489836T1 (en) | 2010-12-15 |
DE502007005800D1 (en) | 2011-01-05 |
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