Classifications

• • H—ELECTRICITY
  • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
  • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
  • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
  • H05B41/14—Circuit arrangements
  • H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
  • H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
  • H05B41/282—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices
  • H05B41/2825—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices by means of a bridge converter in the final stage
  • H05B41/2827—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices by means of a bridge converter in the final stage using specially adapted components in the load circuit, e.g. feed-back transformers, piezoelectric transformers; using specially adapted load circuit configurations

Definitions

• the present invention relates to a Wegungsanord ⁇ tion for operating lamps.
• the invention mainly relates to the operation of low pressure gas discharge lamps. Apart from aspects concerning the preheating, the invention is also applicable to control gear for LEDs.
• the circuit arrangement includes a stop device, which can prevent the switching on of the electronic switches of the half-bridge inverter and releases only during an on-time.
• the on-time depends on a lamp parameter, which can close a loop.
• a disadvantage of this circuit is that the ignition burst for the lamp depends on the tolerances of the load circuit components.
• the object of the present invention is therefore a method for controlling a half-bridge circuit in which a firing burst for the discharge lamp is relatively independent of the tolerances of the load circuit components.
• the ignition burst should also be generatable with a relatively magnetically strongly saturating lamp choke.
• a corresponding half-bridge circuit is to be provided.
• Half-bridge arrangement comprising an upper and a lower electronic switch connected in series, each having a control terminal and forming a center point at its connection point, - a load circuit is connected to the center, into which a load circuit current flows,
• the load circuit contains a reactance network with a resonance frequency to which a lamp can be connected,
• the load circuit is dimensioned such that in a normal operation for a connected lamp after opening one of the electronic switches the voltage at the other of the electronic switches becomes zero after a transient time
• the circuit arrangement comprises a feedback device which couples a feedback quantity from the load circuit to the control terminals of the electronic switches in such a way that the electronic switches are switched on alternately,
• the switching arrangement comprises a stop device which is coupled to the control terminals of the electronic switches and has an input to which a stop Signal is applied, the stop means prevents switching on the electronic switch, as long as the stop signal has an off state,
• the circuit has a timer which is coupled to the input of the stop device and the
• the circuit arrangement comprises a triggering device which emits a trigger signal to the timer at the end of the transient time, at the latest, however, when the load circuit current becomes zero,
• Timer is given, which is less than a quarter of the period of the resonant frequency of the reactance network and after the preheating of the electrodes of the lamps, this on-time is continuously increased until it corresponds to at least a quarter of the period of Resonfre ⁇ frequency of the reactance network.
• On-time is here an on-time of the switch to understand.
• an active on-time of the switches of the half-bridge circuit is fixed during an operating phase at the operating frequency specified. This requires no regulation of the lamp current or the lamp power during operation.
• the preheating frequency is so high that the active on-time of the switches of the half-bridge circuit in the preheat phase is less than a quarter of the Resonanzpe ⁇ period, while the operating frequency is so low that the active on-time greater than a quarter of Reso ⁇ minus a storage time of the half-bridge switch.
• a minimum frequency or time range can be specified, in the passage through an effective preheating and a safe ignition is possible.
• the defined period of time during which the frequency is lowered continu ously ⁇ should be between 1 ms and 100 ms. This time is sufficient to ensure a safe ignition.
• a symmetrical ignition idle current limiting takes place.
• the load circuit ⁇ power a temperature-dependent limit.
• the temperature dependence of the saturation induction of the lamp inductor considered ⁇ to.
• the half-bridge circuit has bipolar half-bridge switches with basic series capacitors in the control circuits.
• the storage time of the bipolar transistors can be further reduced.
• Fig. 2 is a circuit diagram of a part of a half-bridge circuit
• FIG. 3 is a circuit diagram of drive components for the half-bridge circuit of FIG. 2 and FIG.
• Fig. 4 is a current / voltage diagram of the load circuit.
• the half-bridge circuit to be as ⁇ going round improved so that always a defined Zündburst is independent of the To- tolerances, the load circuit components possible. It is always the goal to obtain the least possible losses so that little or no cooling measures are required.
• Fig. 1 shows the voltage across the load circuit capacitor, which is usually connected in parallel to the lamp to be operated.
• the idling curve U CL results as a function of the frequency.
• the maximum of this curve is at the resonant frequency f res .
• the lamp ignites at an ignition voltage U z , which is slightly below the voltage maximum. This ignition voltage U z is achieved at a firing frequency f flammable.
• the s is typically between 0.4 s and 2
• the lamp is heated to a preheat frequency f preheating, the ignition significantly higher than the ignition frequency f lies.
• the clamping ⁇ voltage is located on the lamp significantly below the ignition voltage U z.
• the voltage U CB is established at the load ⁇ circle capacitor. Their course is shown in dashed lines in Fig. 1.
• the lamp is finally operated at the operating frequency f operation . This results in an operating point AP.
• the lamp After preheating the lamp can be ignited in the ideal case, characterized in that the frequency of the Vorholicfre acid sequence f preheating is reduced to a fixed ignition frequency f flammable. Due to tolerances of the load circuit components, however, the course of the load circuit capacitor voltage can change so that at the fixed predetermined frequency, the ignition voltage U z is not reached or unnecessarily high. The lamp would not ignite in this case, or it would take place too high a component load at too high a voltage.
• the open-circuit voltage (lamp has not yet ignited) increases according to arrow Pl. She reaches at a previously unknown or undefined frequency, the ignition voltage U z . Now the voltage drops across the load circuit capacitor to the operating voltage U CB and the load circuit frequency is further reduced until closing the working point AP lent at the operating frequency f for operation achieved as angedeu ⁇ tet in FIG. 1 by arrow P2. Irrespective of the component tolerances, a firing burst will thus occur, so that the lamp is safely put into operation without being exposed to high voltages.
• the preheat frequency is f preheat chosen so that the active time t on preheating ⁇ 1 AT res, wherein T res represents the open circuit resonant period.
• a sequence control unit ⁇ then increases the active time t on operational> 1 AT res - t s, such that the frequency ⁇ to the operating frequency concerning i eb decreases.
• entsprich t s the storage time of the Kol ⁇ lecturer stream in the use of bipolar transistors.
• a one-time t on is shown in Fig. 4 and corresponds to the ⁇ foli time in which the base current I B of a bipolar transistor of the half-bridge circuit during one half cycle is greater than 0.
• a half-bridge circuit for exemplifying the invention is shown in FIG.
• the half-bridge switches Q1 and Q2 are designed as bipolar transistors.
• the two switches Ql and Q2 are serially connected ver ⁇ , wherein the series circuit of the DC link voltage is applied to the poles and VZW_PLUS VZW_MINUS.
• Between the two switches Ql and Q2 results in the node Nl, wherein between the emitter of the switch Ql and the node Nl a resistor R5 is connected.
• Base and emitter of the switch Ql are connected via a resistor ⁇ RIl.
• the base of the switch Ql is connected in parallel with a first winding of a transformer TRI to the node N1 via a parallel connection of a resistor R42 with an RC series circuit R3, C29.
• the emitter of the switch Q2 is connected via a resistor R6 to the negative terminal VZW_MINUS and a resistor R12 bridges the base and the emitter of the switch Q2.
• the base of the switch Q2 is connected to the negative terminal VZW_MINUS via a parallel connection of a resistor R43 with an RC series circuit R4, C30 in series with a second winding of the transformer TRI.
• Capacitors C29 and C30 cause the base current to lead. In addition, they serve to reduce the storage time, as will be explained below in connection with FIG. 4.
• a diode D9 Parallel to the emitter-collector path of the switch Ql is a diode D9 in the flow direction and also a diode D10 parallel to the emitter-collector path of the switch Q2 ⁇ .
• These diodes D9 and DLO serve as Freilaufdio ⁇ the switch Ql and Q2.
• a capacitor C8 is connected in parallel to the diode D9 and acts as a trapezoidal capacitor.
• the transformer TRI has a third winding through which a stop function is controlled.
• This third Wick ⁇ system is coupled to the AC terminals of a bridge rectifier VoIl- formed by the diodes Dl, D2, D3 and D4.
• the DC voltage connections of this rectifier are parallel to an electronic switch V2.
• the third winding, the Rectifier and the switch V2 form a stop device.
• the switch V2 is a MOSFET transistor, which is connected to the source terminal to the reference potential VCC_MINUS.
• the switch V2 short-circuits the third winding of the transformer TRI via the rectifier.
• the control inputs of the electronic switches Ql and Q2 are short-circuited via the transformer TRI, so that the two switches are turned off.
• the switch V2 is controlled by a timer Ul.
• this timer is implemented by a CMOS IC 555.
• the circuit Ul provides the stop signal to PIN3.
• the signal In order to achieve the correct polarity for driving the switch V2, the signal must be in ⁇ vertiert. This is achieved by the inverter U2-D.
• VCC_PLUS and VCC_MINUS are provided, which are connected to PIN8 and PIN1 of the circuit.
• the series circuit of a resistor Rl and a Kon ⁇ densators Cl which is connected between the two supply terminals and VCC_PLUS VCC_MINUS, resulting in a time constant t the on time on is determined.
• the Verbin ⁇ ground point between the resistor Rl and the capacitor Cl is connected with both PIN6 and with PIN7 the circuit Ul to specify the timer corresponding to the time constant.
• PIN4 of the circuit Ul forms a reset input and has to be boosted with the positive operating voltage. ohmig connected via R2, so that the desired functionality of the circuit adjusts Ul.
• PIN2 of the circuit U1 forms a trigger input and is initially connected via a resistor R25 to the positive supply terminal VCC_PLUS.
• a negative pulse is necessary.
• This is supplied by a comparator U3-A, which can be realized for example by the component LM293.
• the Trig ⁇ gerimpuls is directly supplied to the circuit PIN2 Ul.
• the inverting input of comparator U3-A through a resistor R28 with VCC_PLUS and a reflection ⁇ stand R29 connected to VCC_MINUS.
• the non-inverting input of the comparator U3-A is fed by the DC voltage output of a full-bridge rectifier GL1.
• To the AC voltage input of this full-bridge rectifier GLl is the secondary winding of a current transformer or transformer TR3 maral ⁇ tet.
• the primary winding of the transformer TR3 is Zvi ⁇ rule the load circuit and the terminal 111 (see also Fig. 2).
• the DC output of the full-bridge rectifier GIl is terminated with a low resistance with a series connection of the resistors R30 and R31.
• the non-inverting input of the comparator U3-A is a voltage that is proportional to the rectified load current.
• the voltage at the inverting input of the comparator U3-A is temporarily higher than the voltage at the non-inverting input. This results as a comparator signal, a negative trigger pulse.
• the components U3-A, R28, R29, R30, R31, GL and TR3 thus form a triggering device based on current zero crossing detection. As soon as the load current has a zero crossing, the timer is triggered and switches off the transistor V2 for the on-time, whereby the activation of the switches Q1 and Q2 is enabled.
• the output of a further comparator U3-B is ge ⁇ turns on PIN4 the circuit Ul. Its inverting input is between resistors R30 and R31. The non-inverting input is connected between a series connection of resistors R26 and R27, which in turn is connected between the supply terminals VCC_PLUS and VCC_MINUS. So when the rectified load current exceeds a certain value is exceeded, the timer is reset and thus the per ⁇ stays awhile half-bridge switches is actively switched off.
• the duration of the preheating time (typically 0.4 to 2 s) and the duration of the transitional period from the preheat frequency f preheat to the operating frequency f operation (preferably 1 ms to 100 ms, so that charge carriers can build up in the lamp for the ignition) is over PIN5 of the circuit Ul set.
• the switching time from the preheating phase to the operating phase is determined by an RC element consisting of a series circuit of a resistor R24 with a capacitor C2.
• the capacitor C2 is between PIN5 and the negative supply terminal VCC_MINUS.
• the duration of the preheat time is determined with the RC series circuit R23, C3, which is located between the two supply terminals VCC_MINUS and VCC_PLUS.
• a node N2 between the two components R23 and C3 is connected to the input of inverter U2-B and a diode D6 to the resistor. stood R24 and thus to PIN5 of the circuit Ul. Diode D6 turns on the resistor R24 only during the preheating phase ⁇ dynamically parallel to C2 in order to ensure the desired timing.
• w 1TR3 and W 2TR3 represent the numbers of turns of the transformer TR3.
• the comparator can be constructed from a current mirror. This is also known as the "emitter-controlled differential comparator”.
• the goal is to operate the lamp with as few losses as possible. This also means achieving as low-loss switching as possible. This is possible in indukti ⁇ ven operation of the lamp.
• the voltage is pulled to 0 and the current switched in this state.
• the current during switching should be as low as possible. Therefore, the respective bipolar transistor Ql, Q2 is turned on in the current zero crossing, which is indicated by the base current I B in Fig. 4.
• This current profile of the base current I B occurs in the case of an ideal current transformer TRI, wherein the base current I B pha- is the same with the current I c in the load circuit.
• the base current I B is switched off by the timer or the switch V2. Due to a Ladungsträ ⁇ gerüberschusses in the bipolar transistor, a storage time t s obtained, so that the respective bipolar transistor until the time t 1 is actually shut off.
• a base series capacitor C29 is connected to the base of the bipolar transistor Q1 and a base series capacitor C30 is connected to the base of the bipolar transistor Q2.
• the base current rises faster after switching on, which is indicated by the dashed line I B 'in Fig. 4.
• a steeper and deeper basic current profile results, which manifests itself in a shortened storage time t s '.

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• Engineering & Computer Science (AREA)
• Power Engineering (AREA)
• Circuit Arrangements For Discharge Lamps (AREA)
• Inverter Devices (AREA)
• Dc-Dc Converters (AREA)

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• 2007
  • 2007-01-22 EP EP07704044A patent/EP2111730B1/fr not_active Not-in-force
  • 2007-01-22 DE DE502007005800T patent/DE502007005800D1/de active Active
  • 2007-01-22 US US12/524,087 patent/US8212495B2/en not_active Expired - Fee Related
  • 2007-01-22 AT AT07704044T patent/ATE489836T1/de active
  • 2007-01-22 WO PCT/EP2007/050576 patent/WO2008089839A1/fr active Application Filing

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