EP1949496B1 - Systeme d'antenne plate a acces direct en guide d'ondes - Google Patents

Systeme d'antenne plate a acces direct en guide d'ondes Download PDF

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Publication number
EP1949496B1
EP1949496B1 EP06819455A EP06819455A EP1949496B1 EP 1949496 B1 EP1949496 B1 EP 1949496B1 EP 06819455 A EP06819455 A EP 06819455A EP 06819455 A EP06819455 A EP 06819455A EP 1949496 B1 EP1949496 B1 EP 1949496B1
Authority
EP
European Patent Office
Prior art keywords
line
sub
network
slots
radiating elements
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Not-in-force
Application number
EP06819455A
Other languages
German (de)
English (en)
French (fr)
Other versions
EP1949496A1 (fr
Inventor
Eduardo Motta Cruz
Julien Sarrazin
Yann Mahe
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Bouygues Telecom SA
Original Assignee
Bouygues Telecom SA
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Bouygues Telecom SA filed Critical Bouygues Telecom SA
Publication of EP1949496A1 publication Critical patent/EP1949496A1/fr
Application granted granted Critical
Publication of EP1949496B1 publication Critical patent/EP1949496B1/fr
Not-in-force legal-status Critical Current
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Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q13/00—Waveguide horns or mouths; Slot antennas; Leaky-waveguide antennas; Equivalent structures causing radiation along the transmission path of a guided wave
    • H01Q13/20—Non-resonant leaky-waveguide or transmission-line antennas; Equivalent structures causing radiation along the transmission path of a guided wave
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/0006—Particular feeding systems
    • H01Q21/0037—Particular feeding systems linear waveguide fed arrays
    • H01Q21/0043—Slotted waveguides
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/0006—Particular feeding systems
    • H01Q21/0075—Stripline fed arrays
    • H01Q21/0081—Stripline fed arrays using suspended striplines
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/06—Arrays of individually energised antenna units similarly polarised and spaced apart

Definitions

  • the field of the invention is that of telecommunication antennas, and more particularly that of antennas for radio-relay systems (FH antennas).
  • FH antennas radio-relay systems
  • the invention more specifically relates to a flat antenna for microwave radio systems fed by a waveguide.
  • Satellite dishes are commonly used for radio-relay systems.
  • a rectangular waveguide is usually connected to a remote cabinet at the rear of the satellite dish to provide radio access to the antenna. It is shown schematically on the figure 1a a satellite dish 1 connected to a waveguide G.
  • flat antennas are known to be generally as effective as parabolic antennas.
  • Flat antennas are also characterized by their compactness and low wind resistance (especially because of a small thickness) and thus tend to be preferred to satellite dishes.
  • An advantage of the printed technology exploited in the context of the flat antenna is its good ability to adapt to coaxial connections, for example those of the SMA-3.5 mm type.
  • a flat antenna 2 having a coaxial connector to a waveguide G via a guide-coaxial transition TGC.
  • the flat antenna 2 comprises an array of radiating elements integrated in the dielectric substrate of the antenna.
  • the antenna 2 more precisely comprises a set of linear subarrays 1 to 4 parallel to each other, each linear subarray a 1 -a 4 consisting of a set of radiating elements 3.
  • the radiating elements typically each consist of a conductive square surface having a corner connected to a sub-array feed line b 1 -b 4 (typically in the form of a micro-ribbon line).
  • the figure 2 represents more precisely an embodiment of the supply of a flat antenna 2 via a guide-coaxial transition TGC.
  • a supply line L (typically a micro-ribbon line) fed by the waveguide via the guide-coaxial transition TGC is arranged transversely to the linear subarray a 1 -a 4 .
  • This supply line L thus makes it possible to supply the power supply lines of sub-networks and consequently the radiating elements of all the sub-networks.
  • the coaxial connection is effectively fragile and sensitive to galvanic cuts.
  • the micro-ribbon feed line L has significant linear losses, generally greater than the losses of the waveguide.
  • the subarrays are energized in phase opposition (every 180 °). And it is then necessary to provide means to compensate for +/- 180 ° phase shift.
  • the document US 6,509,874 thus shows (see in particular FIG. 3b) a supply of the sub-networks by slots in opposition of phase, and a phase correction carried out by moving the rows of elements. radiating along the power line with an electrical length of +/- 180 °.
  • the object of the invention is to propose a flat antenna FH which does not have the drawbacks associated with the use of a coaxial guide transition, while allowing an equiphase supply of all the radiating elements of the same sub-network.
  • the invention proposes a flat antenna system comprising at least one sub-array of radiating elements disposed on a face of a substrate superimposed on a ground plane, each sub-network consisting of a plurality radiating elements adapted to be fed by a sub-network supply line to which they are connected, a slot being formed in the ground plane opposite each sub-network supply line, the system comprising in addition to a power transmission line arranged with respect to the ground plane so as to effect electromagnetic coupling by slot between said power transmission line and each of the sub-network supply lines, the system being characterized in that that the power transmission line is arranged to extend obliquely with respect to the subnetwork supply lines.
  • a flat antenna 20 having a direct waveguide access G is particularly schematically represented.
  • figure 3 there is shown a possible embodiment of a flat antenna system. On this figure 3 , we have taken over, for the common elements with the figure 2 , the same references.
  • the system 10 comprises a flat antenna 20 as well as a waveguide G.
  • the flat antenna 20 conventionally comprises in itself a flat metal conductive plate constituting a ground plane 5 (at the rear on the figure 3 ), and a substrate in the form of a superimposed dielectric plate and substantially parallel to the ground plate
  • a circuit is printed on the face of the substrate opposite the ground plane 5 and has radiating elements 3.
  • the antenna 20 comprises a set of linear subarrays a 1 -a 4 disposed on the face of the substrate opposite to the ground plane, parallel to each other, each linear subarray a 1 -a 4 consisting of a set of radiating elements 3 adapted to be powered by a sub-network supply line b 1 -b 4 to which they are connected.
  • the supply line is typically a microstrip line ("microstrip" according to the English terminology) printed on the same substrate or on another layer.
  • the radiating elements typically consist of a conductive square surface whose apex is connected to the corresponding sub-network supply line b 1 -b 4 , the diagonal of the square starting from this vertex being perpendicular to the supply line b 1 -b 4 corresponding.
  • the invention is not limited to a particular form of the radiating elements, nor to a particular connection to the corresponding supply line.
  • the radiating elements may thus consist of a conductive surface having the shape of a polygon (for example a triangle or a rectangle) or even a circle.
  • the radiating elements may also be supplied at other points of the conductive surface at one of the peaks of said surface, for example along one of the sides or inside the conductive surface.
  • a slot F 1 -F 4 is formed in the ground plane 5 next to each sub-network supply line b 1 -b 4 .
  • the slots are preferentially identical. Each slot F 1 -F 4 is thus placed transversely to the corresponding supply line.
  • the system 10 also comprises a power transmission line G arranged with respect to the ground plane 5 so as to achieve an electromagnetic coupling by slot between said transmission line and each of the subnetwork supply lines.
  • the energy transmission line may be a waveguide, or any other type of transmission line, in particular a triplate line.
  • the waveguide has for example a waveguide having a rectangular sectional shape. It may also be a waveguide having a U-shape in section.
  • Electromagnetic fields propagate in the rectangular cavity of the waveguide from bottom to top in the example of the figure 3 .
  • a terminal resistor (not shown) may be provided at an upper plate 11 of the waveguide G.
  • wave radiation slots identical to the slits of the ground plane, are made, for example by machining, in the body of the waveguide, in particular on the one of the faces of the waveguide intended to be pressed against the ground plane 5 so that the slits of the ground plane and the slots of the waveguide are superimposed (for these reasons, the same references have been used. to designate all the slots).
  • the electromagnetic fields propagating in the space of the guide then radiate, via the superimposed slots made in the ground plane of the antenna and in the face of the waveguide pressed against the ground plane, and come to excite the power lines of the subnetworks.
  • the waveguide When the waveguide has a U-shaped section, the waveguide is arranged so that the ground plane 5 closes the waveguide space. The electromagnetic fields propagating in the space of the guide then radiate through the slots in the ground plane of the antenna.
  • the antenna structure further comprises a power supply means of the transmission line (not shown), so as to supply electrical energy to said line, this energy propagating inside that and radiating through the slots F 1 -F 4 .
  • slots are made on the same face of the waveguide (when a rectangular waveguide is used), and said face is arranged opposite the ground plane of the antenna 20, on the side opposite to the dielectric substrate of the antenna.
  • the guide access is secured to the ground plane of the antenna. Access is bein also understood solidarity with the ground plane when it comes close the space of the waveguide.
  • a power supply line in the form of a triplate line comprising a conductive line sandwiched between two plane planes triplate line.
  • one of the triplate line ground planes coincides with the ground plane of the antenna (in which the slots are made).
  • wave radiation slots are formed in one of the triplate line ground planes which is pressed against the ground plane of the antenna so that the slits of the ground plane 5 and those of the ground plane of the triplate line are superimposed.
  • the transmission line (here in the form of a waveguide, but this also applies to the triplate embodiment) is arranged so that it extends globally perpendicular to subnetwork supply lines.
  • the slots are made in the length of the transmission line (for example in the form of rectangular notches) so as to be positioned perpendicular to the supply lines.
  • each sub-network supply line is then excited by the energy radiated by the slots, and then supplies all the radiation elements connected to this line.
  • the antenna structure of the figure 2 provides the supply of sub-networks of radiating elements by a transverse feed line L
  • the antenna structure according to the invention thus proposes to use a plurality of slots made so as to achieve an electromagnetic coupling between each sub -Network and a section of the power transmission line, the opposite side to the dielectric substrate of the antenna.
  • this document does not relate to the supply of an antenna having a circuit on which radiating elements are printed, and therefore does not deal with the supply of such elements.
  • this document does not envisage exploiting the radiation of slots to form a coupling between two power transmission lines, and in particular a coupling of the waveguide with radiating element supply lines.
  • the flat antenna is a network of radiating elements. In the absence of a weighting of amplitudes of the radiating elements, the level of the side lobes is likely to be about -13 dB.
  • the following description relates to two possible embodiments of a weighting of amplitudes of the radiating elements of the flat antenna, in particular for containing the level of secondary lobes, for example at about -20 dB. It will be appreciated that these embodiments are not limited to the scope of the present invention for direct waveguide access by electromagnetic slot coupling between the waveguide and the subnetwork feed lines. It will also be appreciated that these embodiments may be implemented separately or together.
  • impedance transformers T are inserted between the radiating elements 3 of the same sub-network in the sub-network supply line b i .
  • Transformers T are more precisely provided with transformation ratios corresponding to the progressive attenuations that one wishes to obtain.
  • Transformers T are typically quarter-wave or half-wave transformers; they may also be transformers with so-called progressive laws (eg exponential or logarithmic laws).
  • the weighting is "integrated" with the radiating elements 3 by varying the surface of said elements.
  • the reduction of the surface of a radiating element is accompanied by a reduction in the energy transfer capacity from the radiating element towards the outside, while nevertheless maintaining the same signal level.
  • This second embodiment is advantageous in that it allows not to use transformers. These actually produce discontinuities on the subnetwork supply line b i . And these discontinuities generate in their turn a parasitic radiation in responsible for significant cross-component levels in the H-plane of the flat antenna radiation pattern (at approximately -10 dB).
  • the subnetwork supply line b i no longer has the discontinuities associated with the use of transformers.
  • the different radiating elements 3 of the sub-network are then equalized in that they are all fed in the same way by the supply line b i .
  • the radiating elements generally have the form of square conductive plates, on the side / 2, where represents the wavelength guided on the substrate of the printed circuit on which the radiating elements are formed and which corresponds to the main radiation frequency of the antenna.
  • a radiating element in the form of a rectangular conductive plate having a length of / 2 and a width of / n, where n is greater than 2.
  • the "integrated" weighting is preferably implemented by promoting the radiating elements 3 1 by subnet from the center (with respect to excitation point P in the sub-network power line in the center of the line), and gradually reducing the size of the radiating elements 3 2 , 3 3 as one moves away from the excitation point P, symmetrically with respect to the point P.
  • the antenna structure controls the transfer of energy between the two transmission lines (between the waveguide or the line triplate and a subnetwork supply line), i.e., the coupling rate is controlled, by varying the offset of the subnetwork supply line from the center of the subnetwork. slot.
  • the slots are identical to each other (for example identical rectangular notches made both in the ground plane and in the body of the rectangular waveguide) and it will be noted that the control of the coupling ratio is performed in the context of the invention without playing on the dimensions of the slots (that is to say, in particular without providing different sizes of slots).
  • This control of the coupling ratio is advantageous in that it makes it possible to compensate for the decrease in the power of the electromagnetic fields propagating inside the waveguide (progressive decay towards a terminal end - upper plate 11 of the guide waveform G - of the propagation of energy in the waveguide space) by progressively increasing the coupling rate waveguide / subnetwork supply line in the incoming direction (from the bottom to the top on the figure 3 ).
  • a slot F i of length L (actually two superimposed slots when using a rectangular section waveguide, or a triplate line whose ground plane is pressed against the ground plane of the antenna) coming to excite a subnetwork supply line b i . It is known that the distribution of currents along a half-wavelength slot has a maximum value at the center and decreasing towards the ends.
  • FIG. 5a On the figure 5a three possible positions of the line b i with respect to the slot F i are represented.
  • the point b illustrates the case where the line b i is placed perpendicular to the slot F i at the center of the slot.
  • the points a and c illustrate cases where the b i is placed perpendicular to the slot F i being offset with respect to the center of the slot. In particular the point c is more offset from the center of the slot than is the point a.
  • the figure 6 illustrates the advantageous embodiment of a flat antenna system according to the invention according to which a control of the coupling ratio between the power transmission line and the various supply lines is carried out.
  • the transmission line here waveguide G
  • the transmission line has a series of oblique slots F 1 -F 4 , and is here arranged slightly obliquely with respect to the supply lines of the sub-networks so that the slots of the waveguide are superimposed on the slits of the ground plane and thus positioned perpendicularly to the supply lines, while gradually varying, from one subnetwork supply line to the other, the coupling ratio between the waveguide and power line.
  • the coupling ratio increases from one feed line to the other in the incoming direction (from bottom to top on the figure 6 ).
  • crosses are shown the positioning of each feed line relative to the corresponding slot. Initially, for the first slot from entering the waveguide in the incoming direction, the cross is moved away from the center of the slot. A weak coupling therefore takes place.
  • the cross progressively approaches the center of the corresponding slot, and the coupling ratio thus increases progressively.
  • the cross coincides with the center of the corresponding slot, the coupling rate is then maximum.
  • the arrangement according to the invention of the waveguide oblique with respect to the supply lines of the sub-networks, as illustrated by the figure 6 , is further adapted to allow a supply of all the radiating elements of the same sub-network with the same phase (equiphase power supply).
  • the two types of transmission lines have different dielectric media.
  • the wavelength in the substrate of low losses of the antenna is of the order of 0.7 to 0.8 times the wavelength in the free space.
  • the wavelength in the free space is close to the wavelength in the waveguide.
  • the gap between the radiating elements does not exceed about 0.8 length. wave in free space.
  • said line which is 0.8 wavelength in the vacuum between two radiating elements, has an electric length of one wavelength in the dielectric between two radiating elements, allowing the supply of all elements with the same phase.
  • the positioning of the waveguide obliquely with respect to the power supply lines of the sub-networks makes it possible to achieve at a gap of one wavelength in the vacuum, and therefore an equi-phase power supply between the sub-networks, while leaving a Vertical spacing between sub-array lines of approximately 0.8 wavelengths.
  • the oblique positioning is further advantageous in that it allows to machine the body of the waveguide so as to practice oblique slots (the feed lines will then be perpendicular to the slots, as is schematically illustrated on the figure 5a ), which allows to obtain an optimal distribution of the currents on the slots, resulting from the propagation modes of the electromagnetic fields inside the waveguide.
  • An application that will be made of the antenna system according to the invention relates to transmissions in the band of 22.1 to 23.1 GHz, but the invention is of course in no way limited to this particular range of frequencies.

Landscapes

  • Variable-Direction Aerials And Aerial Arrays (AREA)
  • Waveguide Aerials (AREA)
EP06819455A 2005-11-14 2006-11-14 Systeme d'antenne plate a acces direct en guide d'ondes Not-in-force EP1949496B1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
FR0511527A FR2893451B1 (fr) 2005-11-14 2005-11-14 Systeme d'antenne plate a acces direct en guide d'ondes.
PCT/EP2006/068430 WO2007054582A1 (fr) 2005-11-14 2006-11-14 Systeme d'antenne plate a acces direct en guide d'ondes

Publications (2)

Publication Number Publication Date
EP1949496A1 EP1949496A1 (fr) 2008-07-30
EP1949496B1 true EP1949496B1 (fr) 2012-05-16

Family

ID=36204540

Family Applications (1)

Application Number Title Priority Date Filing Date
EP06819455A Not-in-force EP1949496B1 (fr) 2005-11-14 2006-11-14 Systeme d'antenne plate a acces direct en guide d'ondes

Country Status (8)

Country Link
US (1) US20090096692A1 (es)
EP (1) EP1949496B1 (es)
JP (1) JP2009516446A (es)
KR (1) KR101166665B1 (es)
CN (1) CN101310413B (es)
ES (1) ES2384887T3 (es)
FR (1) FR2893451B1 (es)
WO (1) WO2007054582A1 (es)

Families Citing this family (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2013005296A (ja) * 2011-06-17 2013-01-07 Hitachi Chem Co Ltd 線路層間接続器、線路層間接続器を有する平面アレーアンテナ、平面アレーアンテナモジュール
EP2805543B1 (en) 2012-03-05 2020-06-03 Huawei Technologies Co., Ltd. Method for improving handover performance in a cellular wireless communication system
CN105676007A (zh) * 2016-02-17 2016-06-15 北京森馥科技股份有限公司 偶极子天线以及使用该偶极子天线的全向性探头
TWI765755B (zh) * 2021-06-25 2022-05-21 啟碁科技股份有限公司 天線模組與無線收發裝置

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US2812501A (en) * 1954-03-04 1957-11-05 Sanders Associates Inc Transmission line
US3665480A (en) * 1969-01-23 1972-05-23 Raytheon Co Annular slot antenna with stripline feed
GB1529541A (en) * 1977-02-11 1978-10-25 Philips Electronic Associated Microwave antenna
JPS6124311A (ja) * 1984-07-13 1986-02-03 Matsushita Electric Works Ltd マイクロストリツプラインアンテナ
US4939527A (en) * 1989-01-23 1990-07-03 The Boeing Company Distribution network for phased array antennas
JPH03101507A (ja) * 1989-09-14 1991-04-26 Yagi Antenna Co Ltd 平面アンテナ
JPH0563409A (ja) * 1991-08-29 1993-03-12 Nissan Motor Co Ltd 導波管
JPH08186436A (ja) * 1994-12-27 1996-07-16 Toshiba Corp マイクロストリップアレイアンテナ
US5539361A (en) * 1995-05-31 1996-07-23 The United States Of America As Represented By The Secretary Of The Air Force Electromagnetic wave transfer
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JP3306592B2 (ja) * 1999-05-21 2002-07-24 株式会社豊田中央研究所 マイクロストリップアレーアンテナ
EP1212809B1 (en) * 1999-09-14 2004-03-31 Paratek Microwave, Inc. Serially-fed phased array antennas with dielectric phase shifters
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US6452550B1 (en) * 2001-07-13 2002-09-17 Tyco Electronics Corp. Reduction of the effects of process misalignment in millimeter wave antennas
US6509874B1 (en) * 2001-07-13 2003-01-21 Tyco Electronics Corporation Reactive matching for waveguide-slot-microstrip transitions
JP2003209411A (ja) * 2001-10-30 2003-07-25 Matsushita Electric Ind Co Ltd 高周波モジュールおよび高周波モジュールの製造方法
US20060273973A1 (en) 2005-06-02 2006-12-07 Chandler Cole A Millimeter wave passive electronically scanned antenna

Also Published As

Publication number Publication date
US20090096692A1 (en) 2009-04-16
WO2007054582A1 (fr) 2007-05-18
FR2893451B1 (fr) 2009-10-16
JP2009516446A (ja) 2009-04-16
ES2384887T3 (es) 2012-07-13
FR2893451A1 (fr) 2007-05-18
CN101310413A (zh) 2008-11-19
KR20080072048A (ko) 2008-08-05
EP1949496A1 (fr) 2008-07-30
CN101310413B (zh) 2012-11-28
KR101166665B1 (ko) 2012-07-24

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