Classifications

• • H—ELECTRICITY
  • H01—ELECTRIC ELEMENTS
  • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
  • H01P1/00—Auxiliary devices
  • H01P1/20—Frequency-selective devices, e.g. filters
  • H01P1/2005—Electromagnetic photonic bandgaps [EPB], or photonic bandgaps [PBG]
• • H—ELECTRICITY
  • H01—ELECTRIC ELEMENTS
  • H01Q—ANTENNAS, i.e. RADIO AERIALS
  • H01Q1/00—Details of, or arrangements associated with, antennas
  • H01Q1/27—Adaptation for use in or on movable bodies
  • H01Q1/32—Adaptation for use in or on road or rail vehicles
  • H01Q1/3208—Adaptation for use in or on road or rail vehicles characterised by the application wherein the antenna is used
  • H01Q1/3233—Adaptation for use in or on road or rail vehicles characterised by the application wherein the antenna is used particular used as part of a sensor or in a security system, e.g. for automotive radar, navigation systems
• • H—ELECTRICITY
  • H01—ELECTRIC ELEMENTS
  • H01Q—ANTENNAS, i.e. RADIO AERIALS
  • H01Q21/00—Antenna arrays or systems
  • H01Q21/0006—Particular feeding systems
• • H—ELECTRICITY
  • H01—ELECTRIC ELEMENTS
  • H01Q—ANTENNAS, i.e. RADIO AERIALS
  • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
  • H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
  • H01Q3/30—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array
  • H01Q3/32—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array by mechanical means
• • H—ELECTRICITY
  • H01—ELECTRIC ELEMENTS
  • H01Q—ANTENNAS, i.e. RADIO AERIALS
  • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
  • H01Q3/44—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the electric or magnetic characteristics of reflecting, refracting, or diffracting devices associated with the radiating element
  • H01Q3/443—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the electric or magnetic characteristics of reflecting, refracting, or diffracting devices associated with the radiating element varying the phase velocity along a leaky transmission line
• • H—ELECTRICITY
  • H01—ELECTRIC ELEMENTS
  • H01Q—ANTENNAS, i.e. RADIO AERIALS
  • H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
  • H01Q9/04—Resonant antennas
  • H01Q9/0407—Substantially flat resonant element parallel to ground plane, e.g. patch antenna
  • H01Q9/0442—Substantially flat resonant element parallel to ground plane, e.g. patch antenna with particular tuning means

Definitions

• the present invention relates to a device for emitting and / or receiving electromagnetic radiation, in particular electromagnetic high-frequency radar radiation, comprising at least one single-layer or multi-layer, in particular also at least one metallic layer, substrate on which at least one planar line, in particular in the form of a ribbon line or in the form of a symmetrical or asymmetrical coplanar line or in the form of a microstrip line or in the form of a slot line or in the form of a coplanar two-band line, with at least two antenna elements, in particular beam elements, of which at least in particular is applied partially serial feed and / or in particular at least partially in-phase feed and / or in particular at least partially phase and / or amplitude symmetrical feed, for example
• At least one electrical feedthrough from the underside of the substrate facing away from the antenna elements wherein at least one metallization layer can be arranged on the underside of the substrate facing away from the antenna elements.
• the present invention further relates to a method for
• Metallization layer can be provided.
• Sensing the surroundings of a means of transportation, in particular a motor vehicle can in principle be done by means of LI [ght] D [etecting] A [nd] R [anging], by means of RA [dio] D [etecting] A [nd] R [anging] Video or ultrasound.
• Radar sensors are becoming increasingly widespread on means of transportation, in particular on motor vehicles.
• Today's systems are used for automatic distance and / or
• Means of transportation around or the entire environment of the means of transportation are scanned.
• the antennas of the commercially available automotive radar sensors at a frequency of 77 gigahertz are usually constructed as lens antennas; For future radar sensors at a frequency of 24 gigahertz and at a frequency of 77 gigahertz, planar antennas are being examined.
• phase-controlled group antenna G (“phased array”) with phase shifters P (cf. FIG. 1A) and with power divider L (cf. FIG. 1A) or with beam-shaping array is used for this purpose
• Element or network S for generating the phase assignment, such as a Rotman / Archer / Gent lens, Butler matrix or Pale matrix.
• a plurality of antenna elements are usually arranged one above the other, which are controlled within a column with a fixed phase and amplitude relationship to one another.
• a beam bundling in elevation E is thus achieved, which serves to increase the range and to suppress undesired targets which are at a very low or high altitude.
• the group antenna G is usually built up planar on H [och] F [requenz] substrates, such as glass, ceramic or softboard. Patches are generally used as antenna elements of the group antenna G; alternatives are, for example, dipole or slot radiators. Current research is concerned with the transfer of these concepts into cost-effective systems for use in motor vehicles.
• the installation of the radar sensors places high demands on the size and shape of the sensor, especially for the side area.
• the sensor By using planar antennas, the sensor becomes flat. Since radar sensors cannot be installed behind the metallic outer walls of a vehicle, the (plastic) bumpers, plastic trims, scratches and scratches remain as installation space in the side area
• the radar sensor may therefore have to be installed at an angle because it is behind
• the installation angles for the radar sensor generally differ for the different installation locations on a motor vehicle and / or between different motor vehicles.
• the beam lobe in elevation is so wide that an inclined installation with a deviation of the order of about + five degrees to about + ten degrees from the vertical can be tolerated.
• planar short- to medium-range sensors or planar L [ong] R [ange] R [adar] - / A [daptive] C [ruise] C [ontrol] sensors are considered, the width of the beam is only increased in elevation be a few degrees to achieve the necessary antenna gain; then a beam lobe oriented as precisely as possible along the horizontal is absolutely necessary.
• planar H [och] F [requenz] lines and planar antennas planar H [och] F [requenz] lines, such as coplanar, are nowadays used for the construction of inexpensive H [och] F [requenz] circuits -, Microstrip, slot lines or the like used.
• planar line types shown in FIG. 3A in FIG. 3B and in FIG. 3C, there are a large number of other planar line types, such as ribbon lines or coplanar two-band lines (cf. for example R. K. Hoffma ⁇ n, "Integrated Microwave Circuits",
• microwave substrates such as glass, ceramic or plastic, which can be mixed with fillers or reinforced with glass fibers, or the like, serve as the substrate.
• Planar antennas for example with dipole, patch or slot radiators, are built up on this microwave substrate; Details on this are, for example, the presentation in P. Bhartia, K.V. S. Rao, R. S. Tomar, "Millimeter-Wave Microstrip and Printed Circuit Antennas", Artech House, Boston, London,
• FIG. 4A, FIG. 4B and FIG. 4C show possible configurations for the feeding of the planar antennas: in the case of the series feeding (so-called “series feed”) according to FIG. 4A, an electrical path length occurs between the antenna elements, via which a fixed beam deflection in elevation can be set;
• a combination of the series feed (see FIG. 4A) and the in-phase feed (see FIG. 4B) is the phase and amplitude symmetrical feed according to FIG. 4C.
• the antenna elements are not necessarily fed in phase, but the phase deviations and the amplitude assignment are symmetrical, and the feed network is also smaller than in the case of in-phase feed (cf. FIG. 4B).
• the antenna elements can be coupled directly to the feed network.
• the power distribution network is accordingly either on the same metal level as the antenna elements or on the Antenna elements opposite substrate side.
• the substrate can have an internal, locally interrupted metallization or can be constructed from a plurality of metallic and dielectric layers.
• the power distribution and feeding can be done on an inside
• Substrate layer take place.
• the beam lobes can be swiveled in elevation by adjusting the phase relationship between the antenna elements in elevation, so that the
• Beam lobes are aligned at a desired angle in the vertical (generally parallel to the horizontal plane) when the radar sensor is installed at an angle.
• phase relationship between the radiator elements can be set by various measures (i) and / or (ii):
• a special design of the antenna or the feed network for each elevation angle can be implemented most simply by different line lengths in the feed network, via which the antenna elements are controlled.
• phase shifters Electronically or otherwise adjustable phase shifters (cf. SK Koul, B. Bhat, "Microwave and Millimeter Wave Phase Shifters", Vol. 1 and Vol. 2, Artech House, Boston, London, 1991) are forbidden because of the number of phase shifters required, the associated costs and also the possibly increasing sensor size.
• the elevation angle of a radar sensor with electronic Controlled phase shifters could indeed be set to the correct value by exchanging information with the motor vehicle electronics, without errors occurring, but electronically controllable phase shifters are prohibited for cost reasons, as mentioned.
• the present invention is based on the inadequacies and, in recognition of the outlined prior art, the object of further developing a device of the type mentioned at the outset and a method of the type mentioned at the outset such that the angle of the beam lobes of the radar sensor can be adjusted in elevation in a simple and inexpensive manner is, the electronics and H [och] F [requenz] modules should remain unchanged for all realizable elevation angles.
• the present invention is intended to rule out errors which arise as a result of confusing the phase shifter assembly and / or the nameplate or as a result of incorrect "trimming".
• the teaching according to the present invention is therefore based on Provision of one or more radar antennas that can be used in the manner essential to the invention for transmitting and / or receiving high-frequency electromagnetic radiation for non-perpendicular installation on or in means of transportation, in particular on or in motor vehicles.
• the core of the present invention is the adjustment of the beam angle in elevation of the beam lobe of a radar antenna for means of transportation, in particular for motor vehicles, for which purpose the deliberate and targeted detuning of the at least one planar H [och] F [requenz] -
• dielectric loading by changing the effective dielectric constant, in particular the coefficient of propagation, of the signal line (so-called “dielectric loading"), for example by means of at least one cap made of dielectric material, or
• At least one element made of conductive material for example at least one Ra [dar] dom [e] s made of metal, at a certain distance from the signal line or
• planar lines such as microstrip lines or striplines (see page 73 in SK Koul, B. Bhat, "Microwave and Millimeter Wave Phase Shifters", Vol. 1 and Vol. 2, Artech House, Boston, London, 1991), which surrounds the planar line Material changes, for example by sliding a plate of dielectric material over the line.
• This principle can also be applied to other planar lines, such as coplanar lines, slot lines and a large number of symmetrical and asymmetrical strip lines; Analogously to this, the effective dielectric constant of a waveguide can also be changed by moving a piece of dielectric material within the waveguide (see page 75 in SK Koul, B. Bhat, "Microwave and Millimeter Wave Phase Shifters", Volume 1 and Volume 2, Artech House, Boston, London, 1991).
• the new and inventive embodiment according to the present invention is advantageous in that the complicated processing of the dielectric waveguide on the substrate is eliminated.
• the H [och] F [requenzj circuit is expediently constructed with planar H [och] F [requenz] lines.
• the H [och] F [requenz] circuit and the planar H [och] F [requenz] lines, the phase (relation) and the antenna pattern of which are influenced by the dielectric cap, are advantageously located on the same substrate.
• WO 00/54368 A1 is disclosed, in principle only possible to a very limited extent, because the waveguiding in the dielectric waveguide is based on the difference in the dielectric constant between the waveguide and the surrounding air. If a dielectric element were brought into the immediate vicinity of the dielectric waveguide, part of the
• a further delimitation criterion of the present invention for the disclosure according to the publication WO 00/54368 A1 is that the object known from the prior art relates to a "scanning" antenna, the beam lobe of which repetitively scans a certain angular range, whereas the present invention treated in a preferred manner the fixed setting of the beam by means of the cap of the (radar) sensor.
• both the present device and the present method can additionally
• feed network so-called "feed network”
• the exact adjustment of the different elevation angles can also take place via the material, in particular via the dielectric constant of the material, of the cap.
• the exact setting of the different elevation angles can also be achieved by suitable structuring of the cap depending on the elevation angle, for example in the form of holes, in the form of grooves, in the form of columns, in the form of steps, in the form of Honeycomb and / or in the form of the like.
• Structuring the dielectric or metal-coated cap with at least one periodic structure, for example with a P [hotonic] B [and] G [ap] structure, is particularly advantageous, so that a so-called
• “Slow Wave” structure is created. With such a periodic structure, which has a pass band and stop band in frequency and is known per se, for example, from waveguides, particularly large phase shifts and thus particularly large elevation angles can be achieved.
• a “slow wave” structure is particularly well suited for applications in the S [hort] R [ange] R [adar] because the “slow wave” structure is particularly broadband. Since the distance between the dielectric and / or conductive element and the high-frequency board comprising the substrate is to be set relatively precisely and is to be kept constant over the life of the sensor device according to the present invention, the tolerance range of this distance should be estimated in the
• the material of the dielectric body and / or the conductive body according to an expedient development of the present invention has a similar, optimally even the same thermal expansion coefficient as the material of the H [och] F [requenz] board, and in this case in particular how the material of the substrate.
• Bodies for the different elevation angles are made of the same material or at least of a material that is similar in terms of thermal expansion behavior, the elevation angle can be adjusted by means of the structuring of the dielectric and / or conductive element discussed above.
• the dielectric material and / or the conductive element can be mechanically, for example by clamping or screwing over spacers, or in direct contact with the H [och] F [requenz] circuit board, which can also be realized by selective contact surfaces be connected.
• An alternative or supplementary possibility is the selective or full-surface gluing of the dielectric and / or conductive body and H [och] F [requenz] board.
• the dielectric material and / or the conductive element can also be constructed in several parts.
• the element influencing the phases and thus the antenna pattern can be mounted above the feed or feed network or below the feed or feed network; at least one further, preferably cap-shaped element then protects the radar arrangement against environmental influences.
• this can be the phases and thus the
• Element influencing the antenna pattern can also be inserted into at least one recess in the cap, in order then to be mounted together with this cap over the feed network or under the feed network.
• the transitions between areas that are out of phase and areas that are out of phase can be realized by gradual transitions between these areas. This means that the distance between the dielectric and / or metallic body
• Planar conduction in the transition area preferably runs continuously, for example linearly trapezoidal, or varies in several small steps.
• the feed network or feed network can be embodied in at least one other line type in order to have a greater influence on the phase by the dielectric material or by the conductive element.
• This different embodiment is based on the fact that a larger proportion of the electromagnetic field in the air is conducted above the line in a coplanar or slot line than in a microstrip line; the influence of the dielectric cap or the conductive element is therefore greater.
• phase-influencing dielectric and / or conductive can be used in order to keep the radar beam in elevation at the same angle with different loads on a means of transportation without level control, in particular a motor vehicle without level control.
• Element can be designed to be adjustable. Such adjustment can take place, for example, via at least one electric motor.
• the (radar) sensor has at least one coding element which is expediently accessible from the outside, such as at least one jumper or at least one switch.
• Such a coding element is used for the purpose of the sensor
• Angle evaluation communicated the installation position. Then the sensor can "upside down” and “upside down” depending on whether upward or downward beam deflection is desired.
• the (radar) sensor only has to be designed for one type of cap element - dielectric or metal - and the beam deflection that can be achieved with such a type of cap element and only goes in one direction can be optimized or maximized.
• the present invention further relates to at least one mechanically controllable phase shifter which is based on the variation of the spacing of at least one conductive element from at least one planar H [och] F [requenz] line, such as, for example, from at least one ribbon line,
• microstrip line so-called "microstrip line”
• slot line so-called "slot line”
• the present invention further relates to at least one dielectric waveguide in which the phase shift or the angle, in particular the elevation angle, of the radiation and / or reception of the electromagnetic radiation in elevation by variably spacing arrangement of at least one at least partially made of conductive material, in particular at least partially made of metal, formed element is adjustable.
• the arrangement of at least one conductive element is preferred over the arrangement of at least one dielectric element, since "dielectric loading" only functions to a very limited extent on a dielectric waveguide in that the waveguide of the dielectric waveguide is based on total reflection at the interface Air is based and the wave is no longer guided when the dielectric loading is increased due to one or more dielectric elements.
• the present invention relates to the use of at least one device according to the type set out above and / or a method according to the type set out above in the automotive sector, in particular in the field of vehicle surroundings sensors, for example for measuring and determining the angular position of at least one object, as is also relevant in the context of a pre-crash sensor for triggering an airbag in a motor vehicle.
• a sensor system in particular a radar sensor system, is used to determine whether there will be a possible collision with the detected object, for example with another motor vehicle. If there is a collision, the speed and impact point of the collision are also determined.
• life-saving milliseconds can be obtained for the driver of the motor vehicle, in which preparatory measures can be carried out, for example, when the airbag is activated or when the belt system is tightened.
• planar antenna system proposed according to the present invention can be used both in the L [ong] R [ange] R [adar] range and in A [daptive] C [ruise] C [ontrol] systems, for example the third
• L [ong] R [ange] R [adar] is generally understood to be a long-range radar for long-range functions, which is typically used at a frequency of 77 gigahertz for A [daptive] C [ruise] C [ontrol] functions becomes.
• Beam (er) elements and equipped with the dielectric or metallized, in particular cap-shaped bodies proposed according to the present invention, provided that the targeted adjustment of the elevation angle proves to be necessary.
• S [hort] R [ange] R [adar] is generally understood to be a short-range radar for short-range functions, which is typically used at a frequency of 24 gigahertz for parking assistance functions or for pre-crash functions to trigger an airbag.
• the structure according to the present invention can be used in a S [hort] R [ange] R [adar] sensor in which the direction of the beam lobe is set in elevation by at least one vehicle-specific dielectric and / or conductive cap.
• 1A shows, in a partially schematic representation, a first arrangement for analog beam shaping via phase shifters according to the prior art
• 1B is a partial schematic representation of a second arrangement for analog beam shaping via a beam shaping network according to the prior art
• FIG. 1C shows, in a partially schematic representation, an arrangement for digital beam shaping according to the prior art
• 3A shows a first device according to the prior art in cross-sectional representation (upper part of the picture) and in a top view (lower part of the picture), the planar line arrangement of which is designed as a coplanar line;
• 3C shows a third device according to the prior art, the planar line arrangement of which is designed as a slot line, in cross-sectional representation (upper part of the figure) and in a top view (lower part of the figure);
• 4A shows a schematic representation of a first possibility for feeding antenna elements in the form of a series feed according to the prior art
• 4B shows a schematic representation of a second possibility for feeding antenna elements in the form of in-phase feeding according to the prior art
• 4C shows a schematic representation of a third possibility for feeding antenna elements in the form of a phase and amplitude symmetrical feeding according to the prior art
• 5A shows a top view of a first possibility for a direct or capacitive series feed of antenna elements according to the prior art
• 5B is a top view of a second option for direct or capacitive series feeding of antenna elements according to the prior art
• 6A in cross-sectional representation (upper right part of the picture), in side view (left part of the picture) and in a top view (lower right part of the picture) a first possibility for a series supply of antenna elements from the underside of the substrate by electromagnetic slot coupling according to the prior art;
• FIG. 8A shows a cross-sectional illustration of a first exemplary embodiment of the device according to the present invention, the planar line arrangement of which is designed as a coplanar line;
• FIG. 8B shows a cross-sectional illustration of the first exemplary embodiment of the device according to the present invention, the planar line arrangement of which is designed as a microstrip line;
• FIG. 8C shows a cross-sectional illustration of the first exemplary embodiment of the device according to the present invention, the planar line arrangement of which is designed as a slot line;
• FIG. 9A shows a cross-sectional illustration of a second exemplary embodiment of the device according to the present invention, the planar line arrangement of which is designed as a coplanar line;
• FIG. 9B shows a cross-sectional illustration of the second exemplary embodiment of the device according to the present invention, the planar line arrangement of which is designed as a microstrip line;
• FIG. 9C shows a cross-sectional illustration of the second exemplary embodiment of the device according to the present invention, the planar line arrangement of which is designed as a slot line;
• 10A shows a cross-sectional illustration of a third exemplary embodiment of the device according to the present invention, the planar line arrangement of which is designed as a coplanar line;
• 10B is a cross-sectional illustration of the third exemplary embodiment of the device according to the present invention, the planar line arrangement of which is designed as a microstrip line;
• FIG. 10C shows a cross-sectional illustration of the third exemplary embodiment of the device according to the present invention, the planar line arrangement of which is designed as a slot line;
• FIG. 11 shows a fourth exemplary embodiment of the device according to the present invention in cross-sectional representation (upper right part of the picture), in side view (left part of the picture) and in a top view (lower right part of the picture);
• FIG. 12 shows a fifth exemplary embodiment of the device according to the present invention in cross-sectional representation (upper right part of the image), in side representation (left part of the image) and in a top view (lower right part of the image);
• FIG. 13 shows a sixth exemplary embodiment of the device according to the present invention in cross-sectional representation (upper right part of the picture), in side view (left part of the picture) and in a top view (lower right part of the picture);
• FIG. 14 shows a seventh exemplary embodiment of the device according to the present invention in cross-sectional representation (upper right part of the image), in side representation (left part of the image) and in a top view (lower right part of the image);
• 15 shows a schematic representation of an eighth exemplary embodiment of the device according to the present invention
• 16 shows a schematic representation of a ninth exemplary embodiment of the device according to the present invention
• FIG. 17 shows a schematic representation of a device in which binary-shifted phase shift elements are installed
• FIG. 18 shows a schematic illustration of a tenth exemplary embodiment of the device according to the present invention.
• FIG. 19 shows a schematic representation of an eleventh embodiment of the device according to the present invention.
• FIG. 21 shows a schematic representation of a thirteenth exemplary embodiment of the device according to the present invention.
• FIG. 22 shows a schematic illustration of a fourteenth exemplary embodiment of the device according to the present invention.
• FIG. 23 shows a schematic representation of a fifteenth exemplary embodiment of the device according to the present invention.
• 24 shows a schematic illustration of an exemplary embodiment of a simple feed network designed for simulation calculations according to the present invention
• 25 shows a perspective illustration of an exemplary embodiment of a first simulation model of the arrangement with a simple feed network from FIG. 24 in the case of the provision of dielectric cap-shaped bodies according to the present invention
• FIG. 26 shows a perspective illustration of an alternative embodiment to FIG. 25 of a simulation model of the arrangement with a simple feed network from FIG. 24 in the case of the provision of metallic cap-shaped bodies according to the present invention
• FIG. 27 shows in three-dimensional plot the directivity measured in decibels in elevation of the arrangement with a simple feed network from FIG. 24 without a dielectric and / or metallic cap-shaped body according to the present invention
• FIG. 28 in two-dimensional graphic representation shows the directivity in elevation of the arrangement with simple feed network from FIG. 24 plotted against the measured beam deflection angle, measured in decibels, without dielectric and / or metallic cap-shaped body according to the present invention for different frequencies;
• 29 shows in a two-dimensional graphical representation (so-called antenna diagram in elevation) the directivity in elevation of the arrangement, plotted against the beam deflection angle measured in degrees and measured in decibels 24 simple feed network of FIG. 24 without dielectric and / or metallic cap-shaped body according to the present invention, with dielectric cap-shaped bodies according to the present invention and with metallic cap-shaped body according to the present invention;
• FIG. 30 shows a perspective illustration of an exemplary embodiment of a second simulation model of an arrangement with a meandering feed network according to the present invention
• FIG. 31 shows in two-dimensional graphic representation (so-called antenna diagram in elevation) the directivity in elevation of the arrangement with meandering feed network from FIG. 30 plotted against the beam deflection angle measured in degrees, measured in decibels, from FIG. 30 without dielectric and / or metallic cap-shaped body according to the present invention for different frequencies;
• FIG. 32 in a two-dimensional graphic representation shows the directivity in elevation of the arrangement with a meandering feed network from FIG. 30 plotted against the beam deflection angle measured in degrees, measured in decibels, without dielectric and / or metallic cap-shaped body according to the present invention, with dielectric cap-shaped bodies according to the present invention and with metallic cap-shaped bodies according to the present invention
• FIG. 33 in a two-dimensional graphic representation shows the directivity in elevation of the arrangement with a meandering feed network from FIG. 30 plotted against the beam deflection angle measured in degrees and measured in decibels from FIG. 30 without dielectric and / or metallic cap-shaped body according to the present invention for different frequencies, with dielectric cap-shaped body according to the present invention for different frequencies and with metallic cap-shaped body according to the present invention for different frequencies;
• FIG. 34 shows a perspective illustration of an exemplary embodiment of a third simulation model of an arrangement with an in-phase feed network according to the present invention
• 35 is a two-dimensional graphic representation (so-called antenna diagram in elevation) of the directivity plotted against the beam angle measured in degrees, measured in decibels in elevation of the arrangement with in-phase feed network from FIG. 34 without dielectric and / or metallic cap-shaped body according to the present invention, with dielectric cap-shaped body according to the present invention (beam deflection: "forwards") and with dielectric cap-shaped body according to the present invention (beam deflection: "backwards”); and
• Fig. 36 in a two-dimensional graphic representation (so-called antenna diagram in elevation) against the in degrees measured beam deflection angle, directivity measured in decibels in elevation of the arrangement with in-phase feed network from FIG. 34 without dielectric and / or metallic cap-shaped body according to the present invention for different frequencies, with dielectric cap-shaped body according to the present invention (beam deflection: "forward” ) for different frequencies and with a dielectric cap-shaped body according to the present invention (beam deflection: "backwards”) for different frequencies.
• the (radar) device 100 which is especially designed for the short range, and a method related thereto for detecting, detecting and / or evaluating one or more objects will be explained by way of example.
• the device 100 which functions as an antenna, can be used in an essential manner according to the invention for transmitting and / or receiving electromagnetic H [och] F [requenz] radar radiation.
• the device 100 has a substrate layer 10 with a
• Dielectric constant ⁇ r , ⁇ on; A metallization layer 12 is applied to the underside 10u of the substrate 10 (cf. FIG. 3B: design according to the prior art; cf. FIG. 8B: first exemplary embodiment the present device 100; see. FIG. 9B: second exemplary embodiment of the present device 100; see. Figure 10B: third embodiment of the present device 100).
• a planar configuration runs on the top 10o of the substrate 10
• the planar linework 20 leads to a plurality of antenna or beam elements 32, 34, 36, 38, likewise applied to the substrate-shaped H [och] F [requenz] board 10 (cf. FIGS. 4A, 4B, 4C, 5A, 5B , 6A, 6B: designs according to the prior art; see FIG. 11: fourth embodiment of the present device 100; see FIG. 12: fifth embodiment of the present device 100; see FIG. 13: sixth embodiment of the present device 100; see FIG. 14: seventh embodiment of the present device 100; see FIG. 15: eighth embodiment of the present device 100; see FIG. 16: ninth embodiment the present device 100; see.
• Figure 17 Device with three binary graded phase shift elements 60, 62, 64; see.
• Figure 18 tenth embodiment of the present device 100; see. Figure 19: eleventh embodiment of the present device 100; see. Figure 20: twelfth embodiment of the present device 100; see. Figure 21: thirteenth embodiment of the present device 100; see. Figure 22: fourteenth embodiment of the present device 100; see. Figure 23: fifteenth embodiment of the present device 100).
• These emitter elements 32, 34, 36, 38 can be supplied in various ways, for example as a serial supply 22s (so-called "series feed”: see FIGS. 4A, 5A, 5B, 6A, 6B: designs according to the prior art; see FIG. 11: fourth embodiment of the present device 100; see FIG. 12: fifth embodiment of the present device 100; see FIG. 13: sixth embodiment of the present device 100; see FIG. 14: seventh embodiment of the present device 100; see FIG. Figure 15: eighth embodiment of the present device 100; see Figure 22: fourteenth embodiment of the present
• Device 100 see. Figure 23: fifteenth embodiment of the present device 100).
• FIGS. 5A, 5B designs according to the prior art; see FIG. 11: fourth embodiment of the present device 100; see FIG. 12: fifth embodiment of the present device 100).
• serial feed 22s can also take place from the bottom 10u of the substrate 10 by means of electromagnetic coupling of the feed network through a slot 32s, 34s, 36s, 38s (see FIG. 6A: Execution according to the prior art Technology; see FIG. 13: sixth exemplary embodiment of the present device 100; see FIG. 22: fourteenth embodiment of the present device 100; see FIG. 23: fifteenth embodiment of the present device 100).
• a serial feed 22s can also be provided from the bottom 10u of the substrate 10 via an electrical feedthrough 32d, 34d, 36d, 38d (see FIG. 6B: version according to the prior art; see FIG. 14: seventh exemplary embodiment of the present device 100).
• Figure 17 Device with three binary graded phase shift elements 60, 62, 64; see.
• Figure 18 tenth embodiment of the present device 100; see.
• Figure 19 eleventh embodiment of the present device 100; see.
• Figure 20 twelfth embodiment of the present device 100; see.
• Figure 21 thirteenth embodiment of the present device 100).
• a further alternative or supplementary method for feeding the antenna elements 32, 34, 36, 38 to the method of series feeding 22s and / or to the method of in-phase feeding 22g is the phase and Amplitude-symmetrical feed 22p (cf. FIG. 40: design according to the prior art; cf. FIG. 16: ninth exemplary embodiment of the present device 100).
• the beam angle in elevation E of the radar antenna or radar device 100 provided for a motor vehicle 200 according to the present invention can be adjusted by the planar H [high] F [requency] signal line 20 and is specifically detuned.
• Phase difference ⁇ between two radiator elements 32, 34 and 34, 36 and 36, 38 can be increased.
• Phase difference ⁇ between the antenna elements 32, 34, 36, 38 and the resulting antenna pattern in the second exemplary embodiment of the present invention according to FIGS. 9A, 9B, 9C is carried out by attaching a plate-shaped or layered element 50 made of conductive material at a certain distance from the signal line 20.
• this metallic element 50 can be favorably replaced by a partial or complete one
• the conductive element 50 is coated with one or more dielectric layers 40s.
• FIGS. 10A, 10B, 10C takes place by means of a corresponding one which is dependent on the desired elevation angle ⁇
• FIGS. 10A, 10B, 10C Design of the dielectric cap 40 with conductive layer 50s (cf. FIGS. 10A, 10B, 10C) of the sensor 100 (for comparison, the respective undisturbed line 20 known from the prior art is shown in FIGS. 3A, 3B, 30).
• phase shifters are not controlled according to the invention, but practically the entire feed network or feed network is detuned or larger parts of the feed network or feed network are detuned; for this reason the feed network is at least partially constructed as a series feed 22s (so-called “series feed”) (see page 161 in P. Bhartia, KVS Rao, RS Tomar, "Millimeter-Wave Microstrip and Printed Circuit Antennas", Artech House, Boston, London, 1991).
• series feed 22s series feed 22s
• the just designed dielectric cap 40 which is arranged at a relatively large distance from the circuit board 10, influences the line 20 and which extends between the beam elements 32, 34, 36 thus the phase ⁇ of line 20 little.
• the graduated dielectric and / or partially metallized cap 40 according to FIG. 12 influences the line 20 running between the beam elements 32, 34, 36 and thus the
• the feed network on the same metallization level as the beam elements 32, 34, 36, 38, which means a direct or capacitive series supply of the directly coupled beam elements 32,
• the dielectric cap 40 or the conductive cap 50 then simultaneously forms a ra [dar] dom [e] or a “radar dome”, that is to say a dome-shaped weather protection for the patch elements, which is permeable to electromagnetic radiation, for example in the form of a plastic cladding for the Radar 100 antenna system.
• a ra [dar] dom [e] or a “radar dome” that is to say a dome-shaped weather protection for the patch elements, which is permeable to electromagnetic radiation, for example in the form of a plastic cladding for the Radar 100 antenna system.
• the feed network can also, like the respective one 13 shows the sixth exemplary embodiment according to FIG. 13 and the seventh exemplary embodiment according to FIG. 14, on which the side of the substrate 10 opposite the radiator elements 32, 34, 36, 38 are built.
• the emitters 32 or 34 or 36 or 38 are in this case
• the dielectric cap 40 determining the elevation angle ⁇ on the back, that is located on the side of the sensor 100 remote from the beam.
• FIG. 15 illustrates the beam deflection caused by a plate-shaped body 40 made of dielectric material of the dielectric constant ⁇ r , 2 in the case of serial feed 22s (so-called "series feed")
• FIG. 16 shows the ninth
• Embodiment of the device 100 the beam deflection with phase-symmetrical feed 22p (see also the illustration in FIG. 4C from the prior art).
• phase (and amplitude-symmetrical feed 22p) Due to its symmetry, the phase (and amplitude-symmetrical feed 22p) has advantageous properties in that a simpler design of the feed can be achieved for a power distribution that drops outwards from the center, particularly with regard to a reduction in the side lobes of the phase and amplitude symmetrical feed 22p
• Symmetry advantageously has little or no "squint" in elevation E.
• U [ltra] W [ide] B [and] systems are generally understood to mean radar and communication systems which work with pulsed signals, the pulse length of which is very short and the latter
• phase-shifting phase shifting element 62 which effects a phase shift of ⁇
• a first dielectric element 40 which causes a phase shift of 2 ⁇ and is suitably structured
• a second, suitably structured dielectric element 42 causing a phase shift of ⁇ and a third, suitably structured dielectric element 44 causing a phase shift of ⁇ can be graded using the three binary
• Phase shift elements 60, 62, 64 built-in phase shift n ⁇
• the three dielectric elements 40, 42, 44 are designed as suitably structured dielectric caps, the first dielectric cap 40 [ ⁇ --> phase shift 2 ⁇ ] being twice as long as the second dielectric cap 42 [ ⁇ --> phase shift ⁇ ] and how the third dielectric cap 44 [ ⁇ -> phase shift ⁇ ] is formed.
• conductive elements 50, 52, 54 it is also possible to use conductive elements 50, 52, 54 to compensate or to amplify the beam deflection, namely in such a way that
• a first conductive element 50 which causes a phase shift of 2 (- ⁇ ) and is suitably structured
• a second, suitably structured conductive element 52 which causes a phase shift of - ⁇ and
• a third, suitably structured conductive element 54 which causes a phase shift of - ⁇ and which can be compensated for by means of the three binary graded phase shift elements 60, 62, 64, phase shift n ⁇ - so that the beam deflection is reduced or even disappears (cf. foundedes Embodiment according to Figure 20),
• the three conductive elements 50, 52, 54 are designed as suitably structured metallic caps, the first metallic cap 50 [ ⁇ --> phase shift 2 (- ⁇ )] being twice as long as the second metallic cap 52 [ ⁇ --> Phase shift - ⁇ ] and how the third metallic cap 54 [ ⁇ --> phase shift - ⁇ ] is formed.
• Embodiment apparent, respectively opposite arrangement of the elements 40, 42, 44 or 50, 52, 54 influencing the phase shift n ⁇ on the individual branches of the feed network or feed network when the beam deflection disappears in FIGS. 18 and 20 or in relation to FIG. 17
• the doubled beam deflection in FIGS. 19 and 21 is explained by the fact that the effective dielectric constant e ⁇ on the feed network and thus the phase shift n ⁇ between the antenna elements 32, 34, 36, 38 - is increased by the dielectric materials 40, 42, 44 (cf. 18 and 19), which corresponds to an electrical extension of the planar line system 20, and
• FIG. 22 fourteenth embodiment of the device 100
• FIG. 23 fifteenth embodiment of the device 100
• the electrical path length between the beam (er) elements 32, 34, 36, 38 can be a multiple of half the wavelength by the
• ⁇ arcsin ⁇ 1 / [2 ⁇ a [( ⁇ eff, 2 / ⁇ eff, ⁇ ) 1 1/2 -1] ⁇ ,
• Such a configuration can be given in a manner essential to the invention by partial or complete metallization of at least one plastic cap which then functions as a metallic element 50 for adjusting the elevation angle ((cf. second exemplary embodiment according to FIGS. 9A, 9B, 9C).
• the effective dielectric constant ⁇ ⁇ depends on the thickness h of the substrate 10 and on the width w of the microstrip.
• ⁇ ⁇ ff 0.5 ⁇ + 1) + 0.5 ( ⁇ r, ⁇ - 1) (1 + 12h / w) "1/2 + 0, 02 ( ⁇ r ⁇ 1 - 1) (1-w / h) 2 for w ⁇ h;
• ⁇ ⁇ ff 0.5 * ( ⁇ r . ⁇ + 1) + 0.5 ( ⁇ r , ⁇ - 1) (1+ 12h / wV 1 2 for w ⁇ h.
• Dielectric constant ⁇ eff can be achieved, which is equal to the dielectric constant ⁇ r ⁇ 1 of the substrate 10.
• the effective dielectric constant ⁇ e ff always remains smaller than for the same "dielectric loading" for the coplanar line or slot line.
• the microstrip line (S [hort] R [ange] R [adar]; eight millimeters at one
• This HFSS simulation model for four slot-coupled, series-fed patches is shown in FIG. 25, which also contains the Ra [dar] dom [e] and adhesive for the Ra [dar] dom [e].
• a separate simulation calculation is carried out for the position of the reference planes at the branches of the branch lines to the patches; all branch lines are extended accordingly by 350 micrometers.
• a cap which is gradually brought up to the conductor track in the area of the distribution network, is attached below the feed network (see FIG. 26, in which the HFSS simulation model, namely only lines, coupling slots and cap, for simulation calculations on the influence of a metallic cap is shown).
• FIG. 27 shows a three-dimensional plot of the directivity measured in decibels in elevation of the arrangement with a simple feed or feed network without a dielectric and / or conductive cap in one
• FIG. 28 shows the directivity plotted against the beam deflection angle measured in degrees (from the z-axis) and measured in decibels in elevation of the arrangement with a simple feed or feed network without a dielectric and / or conductive cap. Due to the serial feed, the beam angle is frequency-dependent, the different frequencies 22 gigahertz, 24 gigahertz, 26 gigahertz and 28 gigahertz being considered.
• Path length of ⁇ i 4 ⁇ (corresponding to 2 ⁇ s , i.e. twice the wavelength of the substrate) connects in order to achieve the greatest possible deflection of the beam lobe.
• the feed or feed network according to FIG. 30 generates an output distribution of 0.25 / 1/1 / 0.25 with an amplitude assignment of 0.5 / 1/1 / 0.5. This reduces the side lobes to about -20 decibels below the main lobe maximum; the main lobe also widens.
• FIG. 31 shows the directivity plotted against the beam deflection angle measured in degrees (from the z axis) and measured in decibels in elevation of the arrangement with a meandering feed or feed network without a dielectric and / or conductive cap, the different frequencies being 22 gigahertz, 24 gigahertz, 26 gigahertz and 28 gigahertz can be considered.
• grating lobes occur.
• the directivities, measured in decibels, and measured in decibels in elevation of the arrangement with a meandering feed or feed network at a frequency of 24 gigahertz at a frequency of 24 gigahertz are compiled for the following different configurations against the beam deflection angle (from z-axis).
• a metallic cap at a short distance deteriorates the beam shape, so that a metallic cap at a distance of two hundred micrometers can achieve a beam deflection of -7 degrees.
• the frequency-dependent angle difference of the beam maxima decreases for large beam deflections, but remains very large there as well.
• Figure 34 shows an in-phase feed network, all
• the line lengths from the patches to the first branch are approximately eight millimeters, that is to say the line lengths from the patches to the first branch correspond to approximately ⁇ s .
• the line length between the first branch and the second branch is about ten millimeters to about twelve millimeters.
• a second dielectric cap shaped differently from the first dielectric cap can more than double the beam deflection.
• the directivities, measured in decibels, and measured in decibels in elevation of the arrangement with in-phase feed or feed network in a frequency range from twenty gigahertz to 28 gigahertz for the following different configurations are compiled against the beam deflection angle (from z-axis).
• the arrangement without a dielectric and / or metallized cap and for the dielectric cap which compensates for the beam deflection results in a relatively small variation in the beam lobe maximum with the Frequency.
• Exemplary embodiments of three different feed networks simple feed or feed network according to FIGS. 24 to 29; meandering feed or feed network according to FIGS. 30 to 33; in-phase feed network with a binary graded phase difference according to FIGS. 34 to 36) the potential of the latter
• Invention proposed setting of the elevation angle of a planar radar antenna.
• a column of four slot-coupled patches at a frequency of 24 gigahertz is used for the simulation calculations, these patches being available as optimized antenna or beam (s) elements for the simulation.
• the limitation to four antenna or beam (er) elements keeps the effort for the simulation within limits.
• the beam lobe of this column is so wide that there is only a difference in the directivities of a few decibels in the swivel range, so that the effort - not least because of the additional losses due to the swivel - would not be worthwhile for this configuration; however, these simulations do
• planar antennas are used in the medium range and for L [ong] R [ange] R [adar] applications, columns with about twenty antenna or beam (er) elements must be used in order to be able to achieve the necessary antenna gains at all.
• the beam is then only a few degrees wide, and an installation of about five degrees to about ten degrees from the plumb line can no longer be tolerated under any circumstances.
• This product is verified by opening and comparing two radar sensors for different installation angles, for example from two different motor vehicles. If the boards, on to which the feed network and the antennas are located, are identical and if the dielectric or conductive, in particular cap-shaped bodies differ, then the proof is completed.
• Beam (er) element ⁇ are provided with an opaque coating (in this case it is not visible whether the boards are identical or not), the coating has to be removed, for example by means of a solvent, or X-ray images of H [och] F to produce [requenz] boards.
• the dielectric or metallized, in particular cap-shaped bodies look identical and also have identical dimensions, then the dielectric constant of the dielectric or metallized, in particular cap-shaped bodies must be determined; there are suitable measuring techniques for this.

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• Physics & Mathematics (AREA)
• Electromagnetism (AREA)
• Optics & Photonics (AREA)
• Engineering & Computer Science (AREA)
• Computer Security & Cryptography (AREA)
• Radar, Positioning & Navigation (AREA)
• Remote Sensing (AREA)
• Variable-Direction Aerials And Aerial Arrays (AREA)
• Radar Systems Or Details Thereof (AREA)
• Waveguide Aerials (AREA)
• Fittings On The Vehicle Exterior For Carrying Loads, And Devices For Holding Or Mounting Articles (AREA)
• Waveguide Switches, Polarizers, And Phase Shifters (AREA)

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