EP1487052B1 - Système d'antennes dans l'aperture d'une carrosserie de véhicule conductrice d'électricité - Google Patents

Système d'antennes dans l'aperture d'une carrosserie de véhicule conductrice d'électricité Download PDF

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Publication number
EP1487052B1
EP1487052B1 EP03001676A EP03001676A EP1487052B1 EP 1487052 B1 EP1487052 B1 EP 1487052B1 EP 03001676 A EP03001676 A EP 03001676A EP 03001676 A EP03001676 A EP 03001676A EP 1487052 B1 EP1487052 B1 EP 1487052B1
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EP
European Patent Office
Prior art keywords
aperture
capacitive
low
conductor
arrangement according
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Expired - Lifetime
Application number
EP03001676A
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German (de)
English (en)
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EP1487052A1 (fr
Inventor
Heinz Lindenmeier
Jochen Hopf
Leopold Reiter
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Delphi Delco Electronics Europe GmbH
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Delphi Delco Electronics Europe GmbH
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Publication date
Application filed by Delphi Delco Electronics Europe GmbH filed Critical Delphi Delco Electronics Europe GmbH
Priority to AT03001676T priority Critical patent/ATE467922T1/de
Priority to DE50312708T priority patent/DE50312708D1/de
Priority to EP03001676A priority patent/EP1487052B1/fr
Publication of EP1487052A1 publication Critical patent/EP1487052A1/fr
Application granted granted Critical
Publication of EP1487052B1 publication Critical patent/EP1487052B1/fr
Anticipated expiration legal-status Critical
Expired - Lifetime legal-status Critical Current

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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q13/00—Waveguide horns or mouths; Slot antennas; Leaky-waveguide antennas; Equivalent structures causing radiation along the transmission path of a guided wave
    • H01Q13/10—Resonant slot antennas
    • H01Q13/103—Resonant slot antennas with variable reactance for tuning the antenna
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/12—Supports; Mounting means
    • H01Q1/1271—Supports; Mounting means for mounting on windscreens
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/27—Adaptation for use in or on movable bodies
    • H01Q1/32—Adaptation for use in or on road or rail vehicles
    • H01Q1/325—Adaptation for use in or on road or rail vehicles characterised by the location of the antenna on the vehicle
    • H01Q1/3275—Adaptation for use in or on road or rail vehicles characterised by the location of the antenna on the vehicle mounted on a horizontal surface of the vehicle, e.g. on roof, hood, trunk

Definitions

  • the invention relates to an antenna arrangement in the substantially rectangular or. trapezoidal aperture 1 of an electrically conductive vehicle body in the meter wave range z. B. for FM reception.
  • the invention is based on an antenna system, such as in the DE 195 35 250 A1 in Figure 4a using the example of a roof segment for a small vehicle is described.
  • the antennas specified there (5.6) for frequencies up to the meter range are preferably formed as conductor structures of thin wire. Due to the limited space available in vehicle construction spaces for the segments described there are primarily roof segments or segments in the trunk lid in question wherein the aperture length L through the vehicle width and their aperture width B by other vehicle technical predetermined conditions, such as the sunroof, the rollover security, etc. is restricted. This leads, in particular in the range of meter waves, to the fact that the aperture length L is often smaller than half the operating wavelength and the aperture width B must be chosen smaller than 1/10 of the operating wavelength.
  • the object of the invention is therefore to avoid the disadvantage of given at low loss adaptation of the antenna narrow band in such aperture antennas.
  • the radiation associated with an antenna in an aperture of the predetermined type is determined at aperture lengths significantly below the half-wave resonance mainly by the currents at the aperture edge.
  • an antenna of this kind for example in the roof of a motor vehicle ( Fig. 1a ), therefore, for frequencies below the aperture resonance results in a horizontal radiation pattern, as shown in Figure 1b).
  • This directional diagram which applies to the horizontal polarization, is independent in form of any excitation of the aperture, provided the aperture does not exceed the aperture resonance.
  • Antenna structures, which are introduced into the aperture thus subject at these frequencies in terms of their own contribution to radiation of the given by the boundary of the aperture dominance of the edge currents. For this reason, it is necessary to design the antenna structures introduced into the aperture in such a way that excitation of the edge currents of the aperture which is as low-loss as possible and the possible bandwidth is reduced as little as possible.
  • An aperture of the type described has a high pass-like character with respect to its radiation properties, with different beam patterns and relatively large bandwidths with good efficiency can be achieved with relatively slim antenna conductors at frequencies above the aperture self-resonance especially with a larger width of the aperture with different antenna structures and positions. This has been demonstrated in the past by numerous forms of window pane antennas in automobiles.
  • the frequency dependence of the received voltage when irradiated in the main receiving direction as effective height h eff in Fig. 2a considered.
  • the maximum current allocation occurs at the natural resonant frequency f s of the aperture, which is expressed in a maximum value of the open circuit voltage measured at the coupling point, measured as the effective height.
  • the resonant frequency is given by the electrical equality, that is the reactive power caused by the electric fields in the aperture, which is the reactive power produced by the magnetic fields in the aperture.
  • the optimum relative bandwidth, which can be achieved in this measure for the resonance peaking of the aperture currents at f o is given by the ratio of the total magnetic reactive power P ma to the radiated power P in the transmission case.
  • b R opt P ma P
  • the capacitive tuning element 5 acts with its effective capacitance AC in Fig. 3a between the boundary points A and A ', wherein the guide value G A shown dashed at this point represents the effective radiation damping of the arrangement.
  • the effective capacitances are each represented by the series connection of an inductance L p or L pc and a capacitance C p or C pc .
  • An essential element of the present invention is to make the effective capacitance at the selected location in the aperture extremely low induction, that is, with the smallest possible inductive influence. If the influence of the series inductance is negligible, the bandwidth of the resonance peak of the electric and magnetic fields in the aperture is largely independent of the position d A for the attachment of the capacitive tuning element. In this case, at the frequency f o, the maximum relative bandwidth b ropt results .
  • Fig. 4a is the bandwidth reduction as a function of the influence of the occurring in L p undesired reactive magnetic power as a function of the frequency ratio f o / f s for different values of C p / ⁇ C and P mp / P ma shown.
  • Fig. 4b the influence of the unwanted reactive magnetic power on the ratio of the relative bandwidth b ro at the frequency f o to the relative aperture bandwidth b rs at natural resonant frequency f s , taking into account that at low frequencies the optimally achievable bandwidth for the current resonance with the cube of the Frequency gets smaller. It is therefore all the more important not to reduce the bandwidth of the antenna arrangement by further disadvantageous coupling to the aperture.
  • the capacitive tuning element in particular when tuned outside the aperture center, must be designed to be particularly non-inductive according to the invention. From the It is clear from the above that a thin antenna conductor inserted into the aperture is not suitable for supplying the reactive power AP e necessary for the tuning to the aperture 1, since this is impossible due to its self-inductance without the bandwidth-reducing reactive magnetic power P mp .
  • the invention will be explained further using the example of an aperture 1 in a vehicle body 2 with an aperture length L of 90 cm and an aperture width B of 20 cm.
  • the aim in this example is to create an antenna for an operating frequency range according to the VHF range in Europe or according to the FM frequency range in Japan.
  • the effective conductance G c ( Fig. 3b ) is without capacitive detuning in the case of the Apertureigenresonanz f s about 1 mS and is reduced with the considered detuning to the resonant frequency f 0 to about 0.54 mS. Together with the reactive power ratios changed at the lower frequency, the indicated detuning results in the relatively large reduction of the relative bandwidth b ro of the aperture resonance.
  • the conductance of 0.54 mS corresponding to a resistance of 1.86 k ⁇ is too high a value to realize a simple lossless matching circuit.
  • the low-inductance conductor 9 can be designed as a flat conductor with a sufficiently large conductor width 11.
  • concentrated capacitive components 12 can be used to bridge the point of interruption, it being advantageous to avoid undesired inductive effect to use a plurality of such capacitive components 12 distributed over the conductor width 11.
  • the capacitive tuning element 5 with the desired effective capacitance ⁇ C is the design of the interruption point 6 as a slot capacitance, which can be set by selecting a suitable conductor slot width 14.
  • FIG Fig. 5a Another advantageous possibility of designing the capacitive tuning element 5 is shown in FIG Fig. 5a shown.
  • the capacitive tuning element 5 is introduced into an appreciable distance d A in the aperture. 1
  • the influence of the inductance L p is considerably greater there than that of an inductance L pc of the same size when mounted centrally (see equation 11). Therefore, a flat configuration of the low-inductance conductor 9 is advantageous.
  • a suitable choice of the capacitive component 7 with introduction of concentrated capacitive components 12 at a given edge distance 10 or with a suitable choice of a conductor slot width 14 in the sufficiently large selected conductor width 11 can be in Fig. 5b Achieve shown impedance curve. All possibilities shown in the figures for tuning the aperture resonance are practically equivalent.
  • the capacitive tuning element 5 as a larger conductive surface 17 with a longitudinal dimension up to half an aperture length L as low-inductance conductor 9 in the aperture 1, as in Fig. 6a , brought in.
  • the desired overall capacitive effect is formed by the edge distance 10 between the boundary of this conductive surface 17 and the aperture edges 13 in conjunction with suitably distributed concentrated capacitive devices 12.
  • This trough can advantageously be designed as a conductive base 25 of microwave antennas 24 ( Fig. 6c ). To lead out the connection lines from the aperture 1, these are made high impedance for the meter wave frequency range by throttling.
  • the contribution of the area of the aperture bridged with the trough to the formation of the self-inductance contributes less and the capacitance has to be correspondingly increased; however, the basic properties of the tuned aperture are preserved.
  • the coupling element 3 similarly to the conductive surface 17, which is in the form of a conductive well, it is not necessary to attach the coupling element 3 in the plane of the vehicle body surrounding the aperture 1. Rather, it may also be placed in a recessed manner on a dielectric carrier material in the aperture 1.
  • Magnetically acting coupling elements 3 for decoupling the strong magnetic fields at the end of the aperture 1 are additionally in the FIGS. 2b, 2d and 3a, 3b shown.
  • the decoupling with an electrical monopoly goes out Fig. 8a out.
  • the associated impedance curve in Fig. 6a shows the broadbandness of this arrangement at the antenna junction 4, which advantageously the transformation into the desired impedance curve in Fig. 7b with the in Fig. 7a indicated simple low-loss reactive elements allows.
  • a particularly advantageous coupling to the aperture 1 is the above-mentioned capacitive coupling for the design of an equivalent resonant band filter with two circles, as described, for example, in US Pat FIG. 5a is shown.
  • a particularly advantageous variant of the embodiment of the coupling element 3 with regard to the design of combination antennas is in Fig. 8a shown.
  • the substantially elongated conductor 22 is galvanically connected at its one end to the aperture edge 13. In planar design of the elongated conductor 22, this can be advantageously used as a conductive base 25 of microwave antennas 24 in a combined antenna system. Due to the galvanic coupling, the lead-out of the connection lines of the microwave antennas 24 can take place without problems.
  • the capacitive tuning element 5 is combined with the coupling element 3 in that in the aperture 1 over a large part of the aperture length L, a conductive surface 17 is introduced as a low-inductance conductor 9.
  • the vote is made by suitable design of the edge distance 10 in conjunction with the distributed introduction of concentrated capacitive elements 12. Due to the increased concentration of magnetic fields in the immediate vicinity of the edge is not too small edge distance 10 hardly a disadvantageous decrease in the self-inductance connected as a magnetic energy storage of the aperture ,
  • the desired antenna impedance can be adjusted with suitable positioning of the antenna connection point 4.
  • This impedance is in Fig. 10b and shows a broadband loop in the frequency range of 80 to 110 MHz.
  • such a broadband impedance can be transformed into a desired impedance curve, for example for the VHF range.

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  • Engineering & Computer Science (AREA)
  • Remote Sensing (AREA)
  • Details Of Aerials (AREA)

Claims (15)

  1. Réseau d'antennes dans l'ouverture substantiellement rectangulaire ou trapézoïdale (1), avec la longueur d'ouverture L et la largeur d'ouverture B, avec B < L/3, d'une carrosserie de véhicule (2) électriquement conductrice pour la plage des ondes métriques, dans lequel
    - la longueur d'ouverture L est sélectionnée pour être si petite que la fréquence de résonance propre (fs) de l'ouverture (1) est supérieure à la fréquence centrale de la plage de fréquences de service ;
    - il existe dans l'ouverture (1) un élément d'accord capacitif (5) pour accorder la résonance d'ouverture sur une fréquence de résonance fo proche de ladite fréquence centrale, et un élément de couplage (3) pour coupler le point de branchement d'antenne (4) avec les champs électromagnétiques élevés en résonance ;
    - l'élément d'accord capacitif (5) est disposé comme une connexion à effet capacitif entre des points opposés (A, A') sur les bords longitudinaux de l'ouverture (1) à une première distance finie (dA) par rapport au centre de la longueur d'ouverture L et est configuré avec une inductance tellement faible que la puissance magnétique réactive (Pmp), qui se manifeste en raison de l'effet inductif rémanent, de cette connexion soit aussi réduite que possible en comparaison avec la puissance magnétique réactive (Pma) produite par les champs magnétiques dans l'ouverture (1),
    - la distance (8) entre les deux points opposés est pontée par un conducteur à faible inductance (9) qui est interrompu au niveau d'au moins un point d'interruption (6), et
    - il existe au niveau de chacun desdits au moins un points d'interruption (6) pour le pontage de ladite distance un composant capacitif (7) dont la valeur de capacité est sélectionnée pour être si grande qu'au total la fourniture de la puissance électrique réactive (Pe) nécessaire pour accorder l'ouverture (1) sur la fréquence de résonance souhaitée fo soit donnée.
  2. Réseau d'antennes selon la revendication 1, caractérisé en ce qu'en particulier pour des valeurs supérieures de la première distance (dA), le conducteur à faible inductance (9) est réalisé comme un conducteur plan d'une largeur de conducteur (11) suffisante, et en ce que pour un pontage capacitif à faible inductance dudit au moins un point d'interruption (6), on utilise respectivement un ou plusieurs composants capacitifs (12) concentrés, répartis sur la largeur de conducteur (11).
  3. Réseau d'antennes selon l'une quelconque des revendications 1 à 2, caractérisé en ce qu'il n'existe qu'un seul point d'interruption (6) sur l'un des bords d'ouverture (13), de sorte que toute la surface du conducteur à faible inductance (9) est reliée par voie galvanique à la carrosserie de véhicule (2).
  4. Réseau d'antennes selon l'une quelconque des revendications 1 à 3, caractérisé en ce que ledit au moins un point d'interruption (6) du conducteur à faible inductance (9) réalisé de façon plane est configuré sous forme de fente avec une largeur de fente de conducteur (14) appropriée en vue de la capacité de fente active entre les bords de fente, de telle sorte que l'effet capacitif exigé soit donné pour la largeur de conducteur (11) sélectionnée.
  5. Réseau d'antennes selon l'une quelconque des revendications 1 à 3, caractérisé en ce que pour la configuration de l'élément d'accord capacitif (5), le conducteur à faible inductance (9) est réalisé comme une surface conductrice (17) sur une majeure partie de la longueur d'ouverture L dans l'ouverture (1), l'accord est donné par une configuration appropriée de la distance de bord (10) en conjonction avec des composants capacitifs concentrés (12) répartis, et le conducteur à faible inductance (9) est utilisé en combinaison comme un élément de couplage (3).
  6. Réseau d'antennes selon l'une quelconque des revendications 1 à 2, caractérisé en ce que pour la configuration de l'élément d'accord capacitif (5) le conducteur à faible inductance (9) est muni de petites dimensions en section transversale à proximité du centre de la longueur d'ouverture L, et l'effet capacitif est donné par l'enclenchement d'un composant capacitif concentré (7) ou de plusieurs composants capacitifs concentrés (7), lorsqu'il existe plusieurs points d'interruption (6).
  7. Réseau d'antennes selon l'une quelconque des revendications 1 à 3, caractérisé en ce que pour réaliser l'élément d'accord capacitif (5), une surface conductrice (17) d'une dimension de longueur allant jusqu'à la moitié de la longueur d'ouverture L est prévue en tant que conducteur à faible inductance (9) large dans l'ouverture (1), en ce que ledit au moins un point d'interruption (6) est donné par la distance entre la bordure de cette surface conductrice (17) et les bords d'ouverture (13), et en ce que l'effet global capacitif approprié est obtenu par un pontage à faible inductance avec plusieurs composants capacitifs concentrés (12) disposés de façon répartie.
  8. Réseau d'antennes selon l'une quelconque des revendications 1 à 5, caractérisé en ce que la surface conductrice (17) est réalisée à la manière d'une cuvette pour configurer l'élément d'accord capacitif (5), en ce que ledit au moins un point d'interruption (6) est donné comme une fente isolante diélectrique continue (18) entre le bord de cuvette (19) et le bord d'ouverture (13) et en ce que la fente (18) est réalisée par la mise en forme et le remplissage avec un matériau diélectrique adéquat de telle sorte que l'accord de la résonance d'ouverture sur la fréquence de résonance fo souhaitée est donné.
  9. Réseau d'antennes selon l'une quelconque des revendications 1 à 8, caractérisé en ce que pour un couplage avec le champ magnétique élevé en résonance, l'élément de couplage (3) est positionné dans l'ouverture comme un élément d'antenne ayant le caractère d'un dipôle magnétique (20).
  10. Réseau d'antennes selon l'une quelconque des revendications 1 à 8, caractérisé en ce que l'élément de couplage (3) pour le couplage avec le champ électrique élevé en résonance est positionné dans l'ouverture comme un élément d'antenne ayant le caractère d'un dipôle électrique (26).
  11. Réseau d'antennes selon l'une quelconque des revendications 1 à 8, caractérisé en ce que l'élément de couplage (3) est réalisé substantiellement comme un conducteur allongé et est disposé avec son point de branchement d'antenne (4) entre deux points opposés des bords d'ouverture (13) à la distance dD par rapport au centre de la longueur d'ouverture L, ladite distance dD étant sélectionnée avec une grandeur adéquate pour obtenir un niveau d'impédance suffisamment faible, et en ce que l'élément de couplage (3) comprend une capacité de couplage série pour le couplage avec l'ouverture (1) en tant que premier circuit résonant d'un filtre passe-bande à deux pôles couplé par voie capacitive, et en ce que le deuxième circuit de résonance du filtre passe-bande à deux pôles est formé par des éléments réactifs (21) à faibles pertes en parallèle au point de branchement d'antenne (4).
  12. Réseau d'antennes selon la revendication 11, caractérisé en ce que l'élément de couplage (3) comprend en outre une inductance série (26) dont la valeur d'inductance en combinaison avec la capacité de couplage (23) et les éléments réactifs à faibles pertes (21) donnent un filtre passe-bande à trois pôles qui augmente la largeur de bande.
  13. Réseau d'antennes selon la revendication 11, caractérisé en ce que le conducteur substantiellement allongé (22) dans l'élément de couplage (3) est relié par voie galvanique au niveau d'une de ses extrémités à un bord d'ouverture (13) et est configuré en vue de l'utilisation comme une surface de base conductrice (25) d'antennes à micro-ondes (24) pour des fréquences supérieures de plusieurs ordres de grandeur.
  14. Réseau d'antennes selon l'une quelconque des revendications 1 à 5 et 7 à 13, caractérisé en ce que la surface conductrice (17) est réalisée comme un élément d'accord capacitif (5) et sert également de surface de base conductrice (25) des antennes à micro-ondes (24) appliquées sur celle-ci pour des fréquences supérieures de plusieurs ordres de grandeur, et en ce que pour quitter l'ouverture (1), les lignes de connexion des antennes à micro-ondes (24) sont configurées par désaccord respectivement à haute impédance pour la plage de fréquences des ondes métriques.
  15. Réseau d'antennes selon l'une quelconque des revendications 1 à 2, 4, 5 et 7 à 13, caractérisé en ce qu'il existe dans l'ouverture (1) un élément d'antenne de réception LMSW capacitif (15) et en ce que l'effet de blindage du conducteur à faible inductance (9) concernant la réception des basses fréquences LMSW est largement compensé par l'agencement de plusieurs points d'interruption (6).
EP03001676A 2003-01-25 2003-01-25 Système d'antennes dans l'aperture d'une carrosserie de véhicule conductrice d'électricité Expired - Lifetime EP1487052B1 (fr)

Priority Applications (3)

Application Number Priority Date Filing Date Title
AT03001676T ATE467922T1 (de) 2003-01-25 2003-01-25 Antennenanordnung in der apertur einer elektrisch leitenden fahrzeug-karosserie
DE50312708T DE50312708D1 (de) 2003-01-25 2003-01-25 Antennenanordnung in der Apertur einer elektrisch leitenden Fahrzeug-Karosserie
EP03001676A EP1487052B1 (fr) 2003-01-25 2003-01-25 Système d'antennes dans l'aperture d'une carrosserie de véhicule conductrice d'électricité

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
EP03001676A EP1487052B1 (fr) 2003-01-25 2003-01-25 Système d'antennes dans l'aperture d'une carrosserie de véhicule conductrice d'électricité

Publications (2)

Publication Number Publication Date
EP1487052A1 EP1487052A1 (fr) 2004-12-15
EP1487052B1 true EP1487052B1 (fr) 2010-05-12

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EP03001676A Expired - Lifetime EP1487052B1 (fr) 2003-01-25 2003-01-25 Système d'antennes dans l'aperture d'une carrosserie de véhicule conductrice d'électricité

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EP (1) EP1487052B1 (fr)
AT (1) ATE467922T1 (fr)
DE (1) DE50312708D1 (fr)

Families Citing this family (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE102016006975B3 (de) 2016-06-07 2017-09-07 Audi Ag Kraftfahrzeug mit Antennenanordnung
DE102016009712A1 (de) 2016-08-10 2018-02-15 Heinz Lindenmeier Aktive Antennenanordnung für den Rundfunkempfang im Ausschnitt einer elektrisch leitenden Fahrzeugkarosserie
KR102209371B1 (ko) * 2018-11-29 2021-02-01 주식회사 지엔테크놀로지스 에너지 절감을 위한 전자기적 결합 장치 및 이를 포함하는 무선 통신 시스템

Family Cites Families (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3210766A (en) 1962-02-15 1965-10-05 Ralph O Parker Slot type antenna with tuning circuit
US4003056A (en) * 1975-05-20 1977-01-11 Ross Alan Davis Windshield antenna system with resonant element and cooperating resonant conductive edge
DE3907493A1 (de) * 1989-03-08 1990-09-20 Lindenmeier Heinz Scheibenantenne mit antennenverstaerker
US5465098A (en) * 1991-11-05 1995-11-07 Seiko Epson Corporation Antenna apparatus for transceiver
DE19535250B4 (de) 1995-09-22 2006-07-13 Fuba Automotive Gmbh & Co. Kg Mehrantennensystem für Kraftfahrzeuge

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DE50312708D1 (de) 2010-06-24
EP1487052A1 (fr) 2004-12-15
ATE467922T1 (de) 2010-05-15

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