EP0890295B1 - Vorrichtung zur vearbeitung von stereosignalen - Google Patents

Vorrichtung zur vearbeitung von stereosignalen Download PDF

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Publication number
EP0890295B1
EP0890295B1 EP97908378A EP97908378A EP0890295B1 EP 0890295 B1 EP0890295 B1 EP 0890295B1 EP 97908378 A EP97908378 A EP 97908378A EP 97908378 A EP97908378 A EP 97908378A EP 0890295 B1 EP0890295 B1 EP 0890295B1
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cross
signal
junction
signals
path
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French (fr)
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EP0890295A1 (de
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Richard Clemow
Fawad Nackvi
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Central Research Laboratories Ltd
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Central Research Laboratories Ltd
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04S—STEREOPHONIC SYSTEMS 
    • H04S1/00—Two-channel systems
    • H04S1/002—Non-adaptive circuits, e.g. manually adjustable or static, for enhancing the sound image or the spatial distribution

Definitions

  • This invention relates to apparatus for processing plural channel signals, particularly though not exclusively binaural signals.
  • Binaural technology is based on recordings made using a so-called "artificial head” microphone system, and the recordings are subsequently processed digitally.
  • the use of the artificial head ensures that the natural three-dimensional sound cues, which the brain uses to determine the position of sound sources in three-dimensional space, are incorporated into the stereo recording.
  • binaural signals is intended to mean two-channel or stereophonic signals which include a component representing audio diffraction effects created by an artificial head means positioned between a pair of spaced apart microphones.
  • the artificial head means may be, as is common, a precise model of a human head and torso, with microphones in the ear structures; alternatively it may be something far less precise, for example a block or sheet of wood positioned between a pair of spaced microphones, which nevertheless creates diffraction signals from the source of sound signals; it may even be an electrical synthesis circuit or system which creates and applies such a signal component to stereophonic signals.
  • the filters represent various combinations of two basic functions, firstly the transfer function (S) between a first loudspeaker of a pair of loudspeakers and the ear of a listener closer to such first loudspeaker, and secondly a function (A) representing the transfer function from the same first loudspeaker to the far ear of the listener (closer to the other loudspeaker).
  • S and A are termed "head related transfer functions" (HRTFs), and such functions have been measured and are widely published-see for example HL Han, J. Audio Eng. Soc., Jan./Feb. 1994, 42, (1/2), pp.15-36.
  • HRTFs may vary if, instead of measurements on a real human head, the HRTF is derived from measurements or calculations based on a model; if the model chosen is simply a block of wood between the microphones then the transfer function will be much simpler than that of a realistic dummy head; for the purposes of this specification, "head related transfer function" is intended to cover all such functions as measured on a real head or measured or calculated from a model of a human head.
  • FIG. 1 this shows one form of filter architecture described in Figure 5 of US-A-3,236,949 to Atal and Schroeder where all the crosstalk-cancellation effects are built into a set of four filters F1, F2, F3, F4.
  • a binaural input has LEFT-IN and RIGHT-IN input signals, filter F1 feeding the LEFT-IN signal to a LEFT-OUT output via a summing junction 2, where the LEFT-IN signal is combined with a RIGHT-IN signal via filter F2.
  • the RIGHT-IN signal is also fed through filter F4 and combined at summing junction 4 with LEFT-IN signal received via filter F3, to provide output signal RIGHT-OUT.
  • Figure 2 shows an alternative architecture as disclosed in GB-A-394,325 to Blumlein and US-A-4,893,342 to Cooper and Bauck where the filters are arranged as SUM and DIFFERENCE filters, with binaural LEFT-IN and RIGHT-IN signals being supplied to both filters via summing junctions 3 and subtractor junction 5 and the outputs of the filters being fed to summing junction 6, and subtractor junction 8 to derive output signals LEFT-OUT, RIGHT-OUT.
  • the arrangements of Figures 1 and 2 require filters of some complexity since they build in all the crosstalk-cancellation effects into one filter set. If an attempt is made to reduce the complexity of these filters too far, critical detail is lost and the arrangement becomes ineffective.
  • FIG. 3 A third arrangement, shown in Figure 3, and disclosed in our copending application WO 94/22278 Our Reference (PQ12529) also suffers from the same problem of complexity in a Y FILTER, although not in an X FILTER.
  • a binaural RIGHT-IN signal is combined via FILTER X with the LEFT-IN SIGNAL in summing junction 10, the output of junction 10 providing via FILTER Y a LEFT-OUT signal.
  • the RIGHT-IN signal is combined in summing junction 12 with LEFT-IN signal supplied via FILTER X, and the output of junction 12 is provided via FILTER Y as a RIGHT-OUT signal.
  • a further filter architecture is shown in Japan Acoustics Institute Collected Lecture Papers May 1976 pages 659, 660 - Figure 6 - A Circuit Of Stereo Sound Image Synthesis - T. Doi and O. Hamada.
  • a schematic diagram is shown in Figure 4, wherein the output of a summing junction 10 is applied through a filter A to the input of a summing junction 12, and through a filter B to provide an output signal LEFT-OUT.
  • the output of summing junction 12 is applied through a filter A to the input of summing junction 10, and through a filter B to provide an output signal RIGHTOUT.
  • the filters A, and B are complex in construction, but notably filters A in the cross feed paths comprise low pass filters in the same way that Blumlein (GB-A-394,325) does.
  • EP-A2-0160431 (Pioneer Electronic Corporation). This architecture implements a known system for sound field correction.
  • the present invention provides in a first aspect apparatus for processing plural channel signals including first and second signal paths for receiving respectively left and right input signals, the first signal path including a first combining junction (10) and the second signal path including a second combining junction (12), the output of the first combining junction (10) being coupled by a first cross-path (14,16,17,20) to an input of the second combining junction (12), and the output of the second combining junction (12)being coupled by a second cross-path (22,24,25,26) to an input of the first combining junction (10), characterised in that the plural channel signals are binaural signals, and each of the first and second cross-paths (14,16,17,20 and 22,24,25,26) includes cross-talk cancellation filter means (17,25 respectively) having a transfer function A/S, where A and S represent respectively far-ear and near-ear head-related transfer functions, and wherein the outputs of the first and second combining junctions (10, 12) represent binaural output signals in which, in use, unwanted signals originating from
  • Each combining junction will commonly be a summing junction, but may be a subtracting or differencing junction. Since it is normally required to subtract a component of one channel from the other channel in order to compensate for crosstalk, if a summing junction is employed, then the cross-path should provide a signal inversion.
  • the invention provides a method of processing plural channel signals including providing left and right input signals to respective first and second signal paths, the signal paths providing as outputs left and right output signals, feeding the left output signal via a first cross-path (14) to the second signal path through a first cross-talk cancellation filter means (17) and combining the filtered left output signal with the right input signal, and feeding the right output signal via a second cross-path (22) to the first signal path through a second cross-talk cancellation filter means (25) and combining the filtered right output signal with the left input signal, characterised in that each of the first and second cross-talk cancellation filter means (17,25) has a transfer function A/S, where A and S represent respectively far-ear and near-ear head-related transfer functions, and the plural channel signals are binaural signals in which, in use, unwanted signals originating from a left speaker and a right speaker and arriving directly at the respective right ear and left ear of a listener are at least partially cancelled.
  • Such a circuit architecture permits crosstalk filter means of a particularly simple construction in order to realise the function A/S. It will be appreciated that a simple filter could not be used in the prior art configurations of Figures 1 to 4 because in those arrangements the filters have to deal with multiple cancellation problems whereas in the present invention, since the cross-paths extend between the output of one channel and a combining junction in the other, the multiple cancellation problem does not arise.
  • the binaural signals may be produced by a number of means
  • the artificial head means include ear structures, in which are located microphones, mounted on either side of a head structure in order to create the various cues necessary for realistic three dimensional sound reproduction in all situations.
  • the combining junction will commonly be a summing junction, but may be a subtracting or differencing junction. Since it is normally required to subtract a component of one channel from the other channel in order to compensate for crosstalk, if a summingjunction is employed, then the cross-path should provide a signal inversion.
  • a particular advantage of the present invention arises in that it is fully compatible with the invention described in our copending International Patent Application No. WO 95/15069 (our ref. PQ12582); this addressed one problem arising with binaural sound recordings which is that generally a listener has to sit still in a well-defined position relative to the loudspeakers, or the binaural effect is lost.
  • the International Application discloses a mechanism for broadening the "sweet spot" to accommodate head movement, by a mechanism involving a less than complete crosstalk cancellation, the crosstalk being reduced by a factor between 0.95 and 0.5.
  • the sweet spot is accordingly broadened.
  • the circuit configuration is made more stable, in that the DC gain of the cross-paths is made less than one.
  • LEFT-IN binaural input signal is applied to a first summing junction 10, and a RIGHT-IN binaural input signal is applied to a second summing junction 12.
  • the output of the summing junction 10 is applied to an input of the second summing junction 12 through a first cross-path 14 which includes a filter means 17 comprising a delay 16, and a cross-talk cancellation filter 17.
  • the cross-path 14 also includes a gain control unit 20.
  • the output of the summing junction 12 is applied to an input of the first summing junction 10 through a second cross-path 22 which includes a filter means 25 comprising a delay 24, and a cross-talk cancellation filter 26.
  • the path 16 also includes a gain unit 28.
  • the outputs of the summing junctions provide output signals LEFT-OUT, RIGHT-OUT.
  • the filter transfer function for each filter 18, 26 is -A/S, S being the same-side transfer function (from a speaker to the nearest ear), and A the alternate side transfer function.
  • Delays 16, 24 introduce a time delay ⁇ , which is the time delay difference of the two functions A and S.
  • ⁇ is the time delay difference of the two functions A and S.
  • the preferred embodiment includes a gain factor x of slightly less than unity introduced by gain control units 20, 28. The reason for this is as follows. In practice S and A are often measured from an artificial head. Very low frequency measurements are very difficult to make due to the difficulty of generating very low frequency acoustic signals. It is therefore common practice to force artifically the A and S functions to the same gain at zero frequency.
  • the gain of the filter -A/S consequently has a gain of (minus) unity at zero frequency.
  • the arrangement of Figure 5 without the gain control units 20, 28 would therefore have positive feedback of unity at low frequencies and would be unstable.
  • a DC gain factor of less than one avoids this problem.
  • a secondary benefit of promidu's the gain control units 20, 28 is that the amount of crosstalk-cancellation is reduced, and the benefits disclosed in our International Patent Application WO 95/15069 as discussed above are realised.
  • LEFT-OUT (1-x 2 A 2 S -2 ) -1 (LEFT-IN-xAS -1 .RIGHT-IN)
  • FIG. 6 this is a graphical representation in terms of gain versus frequency of the theoretical value 40 of the function -A/S, derived from measurements on an artificial head, and an approximation function 42 provided by a filter in accordance with the invention.
  • the crosstalk-cancellation reduction factor of between 0.5 and 0.95 is not shown on this graph, but is implemented as the GAIN function 20 and 28 in Figure 5.
  • each filter 18, 26 has a pronounced dip at around 7 kHz and a pronounced peak at around 9 kHz in order closely to approximate to the theoretical function. It will be understood that it is practically not feasible to implement a filter which reproduces each and every detail of a theoretical A/S function, as it would require a great many filter stages and further the details of the function would vary depending on the precise measurement conditions.
  • Figure 6 also shows a plot of the poles and zeroes of the filter whose response is shown as 42.
  • the approximation may be made as accurate as desired, but for the purposes of this example, a filter with 4 poles and 4 zeroes is shown.
  • Figure 7 is a graphical representation in terms of phase versus frequency of the theoretical -A/S function 40 and of the approximation filter 42. The time delay element of A has been omitted for clarity.
  • IIR filters are particularly appropriate and one preferred crosstalk filter is shown in Figure 8 for implementing the approximation curve of Figure 6, consisting of two cascaded second-order IIR sections.
  • the filter 18, 26 requires 8 multipliers.
  • the two cascaded second order sections 50, 52 have similar configurations, and in each section, an input signal is passed to a summing junction 54 where summing occurs with an output from summing junction 56.
  • the output of junction 54 is applied to a further summing junction 58 and to two one-sample delay units 60, 62.
  • the output of delay unit 60 is scaled in a multiplier 64 by a coefficient B1/B0 and applied to an input of summing junction 58, and is scaled by a coefficient A1 in a multiplier 66 and applied to an input of summing junction 56.
  • the output of delay unit 66 is scaled by coefficient A2 in a multiplier 68 and applied to an input of summing junction 56, and is scaled by coefficient B2/B0 in a multiplier 70 and applied to a summing junction 72.
  • Summing junction 72 also receives the output signal from summing junction 58, and provides an output signal.
  • z is the well known z transform.
  • the curve 40 in Figure 6 is an example of data derived from measurements on an artificial or human head. It contains some unwanted detail, caused by for example spurious resonances, antiresonances and reflections. For example, the sharp peak at around 9 kHz and the sharp dip at around 16 kHz are probably due to such effects. A good approach is therefore to smooth curve 40 before trying to design a filter to fit it.
  • Figure 9 shows a graph similar to Figure 6, except that the measured -A/S function 76 has been smoothed but still retains the important characteristics of the function.
  • Curve 78 shows the response of an approximation filter which closely follows the desired response, with an error of less than 2 dB in the range 0 to 15 kHz.
  • Figure 10 shows graph of phase against frequency of the theoretical - A/S junction 76 and the approximation filter and is analogous to Figure 7.
  • a secondary benefit of this smoothing process is that a simpler filter 18, 26 can be designed to fit the curve 78, in line with the objectives of the invention.
  • One implementation of this filter is shown in Figure 11, using 5 multipliers, wherein similar parts to those of Figure 8 have the same reference numerals.
  • the second section 80 of the filter 18, 26 is simplified, having a summing junction 82 receiving as one input the output of stage 50.
  • a delay 84 and a multiplier 86 are coupled between the output and a further input of junction 82.
  • the output of summing junction 82 provides an output to the stage.
  • FIGs 12 and 13 show an example.
  • the approximation filter function 90 has an error of less than 5 dB over the full frequency range, with positive and negative errors distributed equally. For many applications, this approximation may be satisfactory.
  • One implementation is shown in Figure 14, using only 2 multipliers, wherein similar parts to those of Figure 8 have the same reference numerals.
  • a summing junction 54 whose output is coupled to one input of summing junction 58, which provides an output signal.
  • the output of junction 54 is also coupled to a delay unit 60, which is coupled to an input of junction 54 by a multiplier 66 providing a coefficient A1 and to an input of junction 58 by a multiplier 64 providing a coefficient B1/B0.
  • FIG. 15 A further level of simplification is possible, using only one multiplier, as shown in Figures 15 and 16.
  • the desired approximation function 100 is only followed accurately up to 6 kHz, and thereafter the response cannot be made to follow the desired curve accurately, but the low frequency region is more important than the higher frequency region.
  • Figure 17 One possible implementation is shown in Figure 17, wherein parts similar to that of Figure 11 are denoted by the same reference numerals.
  • a summing junction 82 receiving as one input an input signal INPUT.
  • a delay 84 and a multiplier 86 are coupled between the output and a further input of junction 82.
  • the output of summing junction 82 provides an output signal OUTPUT.
  • the filters disclosed above were tested by a group of listeners, listening to a binaural music track arranged to rotate a sound image "perfectly" around the listener in the horizontal plane, and applying the cross talk cancellation filters to determine their effect.
  • the filter characteristics were carefully optimised as shown, undesirable effects might occur such as the rearward, directly-behind-the-head positions fail, and the source reverts to a frontal position; the image may start to separate, with e.g. vocals, bass, percussion etc. separating spatially.

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  • Physics & Mathematics (AREA)
  • Engineering & Computer Science (AREA)
  • Acoustics & Sound (AREA)
  • Signal Processing (AREA)
  • Stereophonic System (AREA)

Claims (7)

  1. Vorrichtung zur Verarbeitung von Stereosignalen (Mehrkanal-signalen) mit ersten und zweiten Signalwegen zum Empfang linker bzw. rechter Eingangssignale, wobei der erste Signalweg einen ersten Verbindungs-Knotenpunkt (10) und der zweite Signalweg einen zweiten Verbindungs-Knotenpunkt (12) umfaßt, wobei der Ausgang des ersten Verbindungs-Knotenpunktes (10) durch einen ersten Querverbindungsweg (14, 16, 17, 20) mit einem Eingang des zweiten Verbindungs-Knotenpunktes (12) gekoppelt ist, und wobei der Ausgang des zweiten Verbindungs-Knotenpunktes (12) durch einen zweiten Querverbindungsweg (22, 24, 25, 26) mit einem Eingang des ersten Verbindungs-Knotenpunktes (10) gekoppelt ist, dadurch gekennzeichnet, dass die Mehrkanalsignale binaurale Signale sind, und dass jeder der ersten und zweiten Querverbindungswege (14, 16, 17, 20 und 22, 24, 25, 26) Übersprech-Löschungs-Filtermittel (17, 25) besitzt, welche eine Transferfunktion A/S besitzen, wobei A und S Kopf-bezogene Transferfunktionen bezogen auf das entferntere Ohr bzw. das nähere Ohr darstellen, und wobei die Ausgabesignale der ersten und zweiten Verbindungs-Knotenpunkte (10, 12) binaurale Ausgangssignale darstellen, in denen im Betrieb von einem linken Lautsprecher und einem rechten Lautsprecher erzeugte und direkt am rechten und linken Ohr eines Zuhörers ankommende unerwünschte Signale zumindest teilweise ausgelöscht werden.
  2. Vorrichtung nach Anspruch 1, worin jeder Querverbindungsweg (14, 22) ein Verstärkungsregelungs-Mittel (20, 28) besitzt, welches einen frequenzunabhängigen Dämpfungsfaktor zwischen 0,95 und 0,5 liefert.
  3. Vorrichtung nach Anspruch 1 oder 2, worin jeder Verbindungs-Knotenpunkt (10, 12) eine Summierverbindung ist, und jeder Querverbindungsweg (14, 22) eine Signalinversion liefert.
  4. Vorrichtung nach einem der vorhergehenden Ansprüche, worin jedes Übersprech-Löschungs-Filtermittel (17, 25) einen oder mehrere Abschnitte (50, 52) enthält, von denen wenigstens einer ein zweitrangiges stufenloses Impuls-Ansprech-Filter (infinite impulse response filter) IIR enthält.
  5. Vorrichtung nach Anspruch 4, worin jedes Übersprech-Löschungs-Filtermittel (17, 25) erste und zweite in Kaskade geschaltete Abschnitte (50, 52) enthält, wobei jeder Abschnitt ein zweitrangiges IIR-Filter besitzt.
  6. Vorrichtung nach Anspruch 4 oder 5, worin das oder jedes IIR-Filter (50, 52) eine erste Summierverbindung (54) zum Empfang eines Eingangssignals umfaßt, welches über erste und zweite Laufzeitelemente (60, 62) mit einer zweiten Summierverbindung (58) zum Erzeugen eines Ausgangs gekoppelt ist, worin Rückkopplungs- und Steuerungs-Wege mit koeffizienten Multiplikatoren (66, 68) zwischen den Laufzeitelementen (60, 62) und den Summierverbindungen (54, 58) vorgesehen sind.
  7. Verfahren zur Verarbeitung von Stereosignalen (Mehrkanalsignalen), umfassend die Versorgung entsprechender erster und zweiter Signalwege mit linken und rechten Eingangssignalen, wobei die Signalwege als Ausabe linke und rechte Ausgangssignale liefern, Zuführen des linken Ausgangssignals über einen ersten Querverbindungsweg (14) zu dem zweiten Signalweg durch ein erstes Übersprech-Löschungs-Filtermittel (17) und Kombinieren des gefilterten linken Ausgangssignals mit dem rechten Eingangssignal, und Zuführen des rechten Ausgangssignals über einen zweiten Querverbindungsweg (22) zu dem ersten Signalweg durch ein zweites Übersprech-Löschungs-Filtermittel (25), und Kombinieren des gefilterten rechten Ausgangssignals mit dem linken Eingangssignal, dadurch gekennzeichnet, dass jedes der ersten und zweiten Übersprech-Löschungs-Filtermittel (17, 25) eine Transferfunktion A/S besitzt, wobei A und S Kopf-bezogene Transferfunktionen bezogen auf das entferntere Ohr bzw. das nähere Ohr darstellen, und die Mehrkanal-Signale binaurale Signale sind, wobei im Betrieb von einem linken Lautsprecher und einem rechten Lautsprecher erzeugte und direkt am rechten und linken Ohr eines Zuhörers ankommende unerwünschte Signale zumindest teilweise ausgelöscht werden.
EP97908378A 1996-03-30 1997-03-20 Vorrichtung zur vearbeitung von stereosignalen Expired - Lifetime EP0890295B1 (de)

Applications Claiming Priority (3)

Application Number Priority Date Filing Date Title
GBGB9606814.3A GB9606814D0 (en) 1996-03-30 1996-03-30 Apparatus for processing stereophonic signals
GB9606814 1996-03-30
PCT/GB1997/000772 WO1997037514A1 (en) 1996-03-30 1997-03-20 Apparatus for processing stereophonic signals

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EP0890295A1 EP0890295A1 (de) 1999-01-13
EP0890295B1 true EP0890295B1 (de) 2001-10-31

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EP (1) EP0890295B1 (de)
JP (1) JP2000507762A (de)
DE (1) DE69707847T2 (de)
DK (1) DK0890295T3 (de)
GB (1) GB9606814D0 (de)
TW (1) TW357537B (de)
WO (1) WO1997037514A1 (de)

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GB9726338D0 (en) * 1997-12-13 1998-02-11 Central Research Lab Ltd A method of processing an audio signal
TW410527B (en) 1998-01-08 2000-11-01 Sanyo Electric Co Stereo sound processing device
JP4122507B2 (ja) * 1999-03-23 2008-07-23 オンキヨー株式会社 クロストーク・キャンセル装置および方法
KR100739762B1 (ko) * 2005-09-26 2007-07-13 삼성전자주식회사 크로스토크 제거 장치 및 그를 적용한 입체 음향 생성 시스템
EP1929837A4 (de) * 2005-09-26 2009-04-22 Samsung Electronics Co Ltd Vorrichtung und verfahren zum löschen von übersprechen und stereo-tonerzeugungssystem damit
ES2638269T3 (es) 2006-07-04 2017-10-19 Dolby International Ab Unidad de filtro y procedimiento de generación de respuestas al impulso de filtro de subbanda
KR100959499B1 (ko) 2008-09-23 2010-05-26 한국전자통신연구원 음상 정위 방법 및 전달 함수 생성 장치
TWI475896B (zh) * 2008-09-25 2015-03-01 Dolby Lab Licensing Corp 單音相容性及揚聲器相容性之立體聲濾波器
EP3852394A1 (de) 2016-06-21 2021-07-21 Dolby Laboratories Licensing Corporation Kopfverfolgung für vorgerendertes binaurales audio

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US4136260A (en) * 1976-05-20 1979-01-23 Trio Kabushiki Kaisha Out-of-head localized sound reproduction system for headphone
EP0160431B1 (de) * 1984-04-09 1990-09-19 Pioneer Electronic Corporation Schallfeldverbesserungssystem
GB2232796A (en) * 1989-06-13 1990-12-19 Secr Defence Processor for recursive computations
GB9324240D0 (en) * 1993-11-25 1994-01-12 Central Research Lab Ltd Method and apparatus for processing a bonaural pair of signals

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EP0890295A1 (de) 1999-01-13
DE69707847D1 (de) 2001-12-06
GB9606814D0 (en) 1996-06-05
DK0890295T3 (da) 2002-01-07
TW357537B (en) 1999-05-01
JP2000507762A (ja) 2000-06-20
WO1997037514A1 (en) 1997-10-09

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