EP0727062A1 - Alimentation a decoupage - Google Patents

Alimentation a decoupage

Info

Publication number
EP0727062A1
EP0727062A1 EP94930975A EP94930975A EP0727062A1 EP 0727062 A1 EP0727062 A1 EP 0727062A1 EP 94930975 A EP94930975 A EP 94930975A EP 94930975 A EP94930975 A EP 94930975A EP 0727062 A1 EP0727062 A1 EP 0727062A1
Authority
EP
European Patent Office
Prior art keywords
semiconductor switch
power supply
transformer
secondary winding
controllable semiconductor
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP94930975A
Other languages
German (de)
English (en)
Inventor
Günther Bergk
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Braun GmbH
Original Assignee
Braun GmbH
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Braun GmbH filed Critical Braun GmbH
Publication of EP0727062A1 publication Critical patent/EP0727062A1/fr
Withdrawn legal-status Critical Current

Links

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H02J7/02—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries for charging batteries from ac mains by converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/1563—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators without using an external clock
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P4/00—Arrangements specially adapted for regulating or controlling the speed or torque of electric motors that can be connected to two or more different electric power supplies
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J2207/00—Indexing scheme relating to details of circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H02J2207/20—Charging or discharging characterised by the power electronics converter

Definitions

  • the invention relates to a switching power supply according to the preamble of claim 1.
  • the mean value of the output current flowing through the consumer increases with a higher input voltage.
  • This current increase is approx. 50% when the input voltage rises from 100 volts to 300 volts and is mainly due to the greater impact, i.e. Storage time of the first controllable semiconductor operating in the saturated state as a switch increases as a percentage of the switch-on time.
  • the object of the invention is to provide a simple, but very precise and easily adjustable current control in a switching power supply of the type mentioned, in which no additional current sensor resistance is required.
  • control connection of the first controllable semiconductor switch is connected to an arrangement which limits the maximum peak current of the first controllable semiconductor switch as a function of the output current and which reduces the voltage drop across the internal resistance of the secondary winding caused by the output current through the secondary winding Transmitter recorded.
  • the solution according to the invention enables a precisely adjustable limitation of the peak current of the controllable semiconductor switch as a function of the output current, the internal resistance of the secondary winding being used as a current sensor resistor for detecting the output current, so that no additional current sensor resistor is required and the voltage drop generated by such a current sensor resistor is eliminated .
  • the output current is also reduced at higher temperatures due to the positive temperature coefficient of the copper of the transformer winding if no additional temperature compensation is carried out.
  • Another advantage of the solution according to the invention is that the temperature-dependent internal resistance of the secondary winding of the transformer detects the winding temperature during operation of the switched-mode power supply and can be used for protective and shutdown measures.
  • An advantageous embodiment of the solution according to the invention is characterized in that the arrangement which limits the maximum peak current of the first controllable semiconductor switch limits it as a function of the mean output current and the voltage drop across the internal resistance of the secondary winding of the transformer caused by the output current through the secondary winding with a reference voltage that corresponds to the maximum output current.
  • the limitation of the peak current of the first controllable semiconductor switch by detection of the average output current takes into account the on and off switching conditions of the controllable semiconductor switch, so that a correct measure for the output current is determined even with longer pause times of the controllable semiconductor switch.
  • the comparison of the voltage drop detected at the internal resistance of the secondary winding of the transformer with a reference voltage enables the permissible peak current to be set simply as a function of the components used.
  • a further advantageous embodiment of the solution according to the invention is characterized in that the arrangement which limits the maximum peak current of the first controllable semiconductor switch has an operational amplifier operating as an integrator, to the inputs of which the voltage drop across the internal resistance of the secondary winding of the transformer is applied and the output of which the control connection of the first controllable semiconductor switch is connected.
  • the mean value of the output current can be easily formed over several periods, so that when comparing the one input of the operational amplifier Given the voltage drop at the internal resistance of the secondary winding of the transformer and a reference voltage at the other input of the operational amplifier, a representative value for the permissible output current of the transformer is obtained, which is used to limit the peak current of the controllable semiconductor switch.
  • the comparison between the voltage drop across the internal resistance of the secondary winding of the transformer with a predetermined reference voltage can alternatively take place in that either the negative input of the operational amplifier is connected to a voltage divider arranged in parallel with the diode, the dividing point of which via the one voltage divider resistor with the cathode of the diode is connected, or that the negative input of the operational amplifier is connected via the series connection of two resistors with reference potential, the connection of the two resistors being connected via a Zener diode to the one winding end of the secondary winding of the transformer.
  • the output of the operational amplifier can be connected to the control connection of the first controllable semiconductor switch via a controllable threshold value switch, so that below a predetermined threshold value the arrangement below the predetermined reference value that limits the peak current of the first controllable semiconductor switch has no influence on the peak current switch-off and only if a predetermined threshold value is exceeded, the peak current cutoff of the first controllable semiconductor switch is influenced.
  • An additional Z-diode can be arranged between the output of the operational amplifier and the controllable threshold switch when the operating voltage of the operational amplifier is less than the maximum voltage at the control connection of the first controllable semiconductor switch in its switch-on phase.
  • An additional influence on the peak current switch-off of the first controllable semiconductor switch can be taken in that a second controllable semiconductor is provided, the collector-emitter path of which lies between the control connection of the first controllable semiconductor switch and the reference potential and whose base is both via a third Z- Diode with the emitter of the first controllable semiconductor switch and connected via a resistor with reference potential.
  • a Z diode can be provided between the control connection of the first controllable semiconductor switch and the reference potential.
  • a feedback on the secondary side can take place on the control electrode of the first controllable semiconductor switch by providing a resistor in series with a capacitor which is connected on the secondary side to the the end of the secondary winding connected to the cathode of the diode is connected.
  • FIG. 3 shows the time course of the current through the first controllable semiconductor switch and the control voltage at the output of the operational amplifier at different input voltages in an arrangement according to FIG. 1.
  • the switched-mode power supply shown in FIG. 1 has a primary clocked flyback converter with a transformer 5 and a first controllable semiconductor switch 1 in the form of a transistor, and a diode 31 provided in the load circuit, which is polarized so that during the blocking time of the transistor 1 in Transmitter 5 stored energy is discharged into the consumer 6, which here consists of an accumulator 61 and a DC motor 62 which can be switched to the accumulator 61 via a switch 63. If the consumer is only a DC motor without an accumulator, a capacitor must be connected in parallel to the motor to smooth the output voltage.
  • the flyback converter is connected via a rectifier bridge circuit 4 and a resistor 28 fed from a direct or alternating voltage network, the voltage of which can vary between 100 and 250 volts, in extreme cases also 12 volts, and the frequency of which can be almost arbitrary in the case of a feeding alternating voltage network.
  • the rectified output voltage is applied to the input of the flyback converter or the control and regulating electronics via a series choke 8 and a shunt capacitor 9.
  • the rectified voltage U g is connected to the series connection of the primary winding 51 of the transformer 5, the collector-emitter path of the transistor 1, the resistor 21 and the load 6.
  • the base of the transistor 1 is connected via the series connection of a resistor 26 and a capacitor 1 2 with one connection of the secondary winding 52 of the transformer 5 and also via a resistor 25 with the positive potential of the rectified voltage U g .
  • the base of transistor 1 is connected to ground or reference potential via the collector-emitter path of a transistor 2.
  • the emitter of transistor 1 is connected to ground or reference potential via resistor 21 and accumulator 61.
  • the base of the transistor 2 is connected via a resistor 24 with reference potential and via a Z diode 30 to the emitter of the transistor 1.
  • the Zener diode 30 allows the switching threshold of the transistor 2 to be defined.
  • the winding direction of the primary and secondary windings 51 and 52 of the transformer 5 is determined by the points entered.
  • the positive input (+) of an operational amplifier 40 is now led via a resistor 44 to the end A of the secondary winding 52 connected to the accumulator 61.
  • the operational amplifier is connected as an integrator by a capacitor 42 located between the negative (-) input (point F) of the operational amplifier 40 and its output D.
  • the negative input F is connected to reference potential via a voltage divider containing the resistors 46 and 48, and the divider point C is connected via a resistor 47 to the end B of the secondary winding 52 connected to the cathode of the diode 31.
  • the anode of the diode 31 is connected to the reference potential.
  • a capacitor 41 is connected between the two inputs of the operational amplifier 40 to suppress interference.
  • the output D of the operational amplifier 40 is led via a resistor 45 and a Z diode 36 to the input of a controllable Z diode Z consisting of a transistor 3 and a resistor 34.
  • the emitter-collector path of the transistor 3 lies between the base E of the switching transistor 1 and the reference potential.
  • the base of transistor 3 forming the input of the controllable Z-diode is connected to its emitter and thus also to the base of transistor 1 via resistor 34.
  • the Zener diode 36 is only necessary if the voltage at the base of the transistor 3 can be greater than the operating voltage of the operational amplifier 40.
  • the end of the resistor 45 facing away from the output D of the operational amplifier is also for smoothing the output signal of the operational amplifier via a condenser ⁇ sator 43 connected to reference potential.
  • the circuit can also be constructed in such a way that the accumulator is fed only by the secondary current flowing through the secondary winding and not, as in FIG. 1, is also flowed through by the primary current flowing through the primary winding.
  • the resistor 21 is then connected directly to the reference potential.
  • the cathode of a Zener diode 39 is connected to the secondary winding 52 and its anode is connected to two resistors 49, 50, one of which serves to lower the potential 49 with the resistor 46 and the cathode of the diode 31 and the other as Series resistor for stabilizing the Z-diode 39 arranged resistor 50 is connected to the reference potential.
  • the transistor operating as a switching transistor becomes 1 is driven via the resistor 25 with a low base current, as a result of which the transistor 1 is driven into the conductive state.
  • a positive feedback effect is created via the secondary winding 52 of the transformer 5, by means of which the transistor 1 is additionally activated and suddenly switched to the fully conductive state.
  • the collector current increases linearly and generates a voltage drop proportional to the respective collector current at the resistor 21.
  • the voltage present at the emitter of the transistor 1 against the reference potential then corresponds in FIG. 1 to the voltage drop across the resistor 21 plus the battery voltage U a , which here represents the output voltage.
  • the transistor 2 is activated via the Zener diode 30, thereby becoming conductive and connecting the base of the transistor 1 to ground or reference potential and thus removing the base current from the transistor 1, whereupon the transistor 1 blocks .
  • the polarity of the voltage induced in the secondary winding 52 of the transformer 5 changes.
  • the energy stored in the transformer 5 is thus delivered to the accumulator via the diode 31 according to the principle of the flyback converter.
  • This current-proportional voltage drop is applied to the inputs of the operational amplifier 40, the positive input of the operational amplifier 40 being connected to the point A via the resistor 44, while the negative input of the operational amplifier 40 is connected to a negative reference voltage via the resistor 46.
  • the negative reference voltage is applied to the voltage divider formed from resistors 47 and 48 tapped at which the accumulator voltage, which is to be regarded as essentially constant, is present.
  • the operational amplifier 40 is connected as an integrator and thus detects the mean value of the output current of the secondary winding 52 of the transformer 5.
  • the transistor 3 remains blocked and the arrangement which limits the maximum peak current has no influence on the peak current cutoff of the switching transistor.
  • the input of the operational amplifier is controlled via resistors 46, 47.
  • the output of the operational amplifier 40 becomes more negative and controls the base of the switching transistor 1 via the controllable Z-diode, which also becomes more negative, so that the voltage across the emitter resistor 21 can no longer rise as high, as a result of which the peak current of the switching transistor 1 is reduced.
  • the Z diode 36 connected upstream of the transistor 3 of the controllable Z diode is only required if the operating voltage of the operational amplifier 40 is less than the maximum voltage at the base of the switching transistor 1 in the switch-on phase.
  • the maximum peak current emitted by the secondary winding 52 is therefore limited by an arrangement in which the base of the switching transistor 1 is increased by one certain voltage conductive, the reference voltage source is kept constant with respect to the reference potential.
  • FIGS. 3a to 3c show the current flowing through the transistor 1 and the control voltage present at the output of the operational amplifier 40 at different input voltages of the flyback converter.
  • 3a shows the conditions at an input voltage of 100 V
  • FIG. 3b at an input voltage of 180 V
  • FIG. 3c the conditions at an input voltage of 260 V.
  • the graphic representation shows how the control voltage at the output of the operational amplifier 40 decreases as the input voltage rises and, accordingly, the peak value T of the transistor current i is reduced by shortening its leading phase.

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

Alimentation à découpage comprenant un convertisseur indirect à cadencement primaire pour l'alimentation contrôlée d'un consommateur électrique (6; 61, 62) à partir d'une source de tension d'entrée, dont la tension est d'un type et d'un niveau pouvant varier au choix, dans lequel le montage en série de l'enroulement primaire (51) d'un transformateur (5), du chemin de courant principal d'un premier commutateur commandé à semi-conducteur (1) et d'une première résistance (21) est commuté en parallèle à la source de tension d'entrée. L'enroulement secondaire (52) du transformateur (5) est monté en série avec une diode (31) et le consommateur (6; 61, 62). L'électrode de commande du premier commutateur commandé à semi-conducteur (1) est reliée à un dispositif limitant le courant de crête maximum du premier commutateur commandé à semi-conducteur (1) en fonction du courant de sortie, ce dispositif détectant la chute de tension dans la résistance interne de l'enroulement secondaire (52) du transformateur (5) provoquée par le courant de sortie à travers l'enroulement secondaire (52).
EP94930975A 1993-11-03 1994-10-25 Alimentation a decoupage Withdrawn EP0727062A1 (fr)

Applications Claiming Priority (3)

Application Number Priority Date Filing Date Title
DE4337461A DE4337461A1 (de) 1993-11-03 1993-11-03 Schaltnetzteil
DE4337461 1993-11-03
PCT/EP1994/003506 WO1995012840A1 (fr) 1993-11-03 1994-10-25 Alimentation a decoupage

Publications (1)

Publication Number Publication Date
EP0727062A1 true EP0727062A1 (fr) 1996-08-21

Family

ID=6501664

Family Applications (1)

Application Number Title Priority Date Filing Date
EP94930975A Withdrawn EP0727062A1 (fr) 1993-11-03 1994-10-25 Alimentation a decoupage

Country Status (5)

Country Link
US (1) US5708572A (fr)
EP (1) EP0727062A1 (fr)
JP (1) JPH09504679A (fr)
DE (1) DE4337461A1 (fr)
WO (1) WO1995012840A1 (fr)

Families Citing this family (8)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
KR970702610A (ko) * 1995-02-16 1997-05-13 요트.게.아. 롤페즈 전원 공급 장치 및 통신 회로(Power-supply and communication)
US5668462A (en) † 1995-05-08 1997-09-16 Telefonaktiebolaget Lm Ericsson Method and apparatus for controlling a charging current of a battery in a portable chargeable electronic unit
US6344980B1 (en) * 1999-01-14 2002-02-05 Fairchild Semiconductor Corporation Universal pulse width modulating power converter
JP3515012B2 (ja) * 1999-04-23 2004-04-05 シャープ株式会社 半導体装置およびその製造方法
DE19941449A1 (de) * 1999-08-31 2001-03-01 Braun Gmbh Schaltnetzteil
US6314010B1 (en) 2000-02-25 2001-11-06 Compaq Computer Corporation Slope-based primary feedback to control the off-time of a power supply
US6839248B2 (en) * 2003-05-01 2005-01-04 Ko Semiconductors Co., Ltd. Flyback power supply device and control method thereof
GB0402319D0 (en) * 2004-02-03 2004-03-10 M & Fc Holdings Llc Wide range power supply for polyphase electricity meter

Family Cites Families (9)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE3218594A1 (de) * 1982-05-17 1983-12-22 Braun Ag, 6000 Frankfurt Elektronisches schaltnetzteil
NL8503479A (nl) * 1985-12-18 1987-07-16 Philips Nv Voedingsschakeling.
DE3545324A1 (de) * 1985-12-20 1987-06-25 Braun Ag Elektronisches schaltnetzteil
DE8809723U1 (de) * 1988-07-30 1988-12-08 Braun Ag, 6000 Frankfurt Schaltnetzteil mit einem primär getakteten Gleichspannungswandler
US4939632A (en) * 1989-02-14 1990-07-03 U.S. Philips Corporation Power supply circuit
US5101334A (en) * 1989-02-14 1992-03-31 U.S. Philips Corporation High speed power supply circuit with circuit with positive feedback
US4969077A (en) * 1989-02-14 1990-11-06 U.S. Philips Corporation Power supply circuit
DE4008663C1 (fr) * 1990-03-17 1991-05-02 Braun Ag, 6000 Frankfurt, De
DE4125510A1 (de) * 1991-08-01 1993-02-04 Philips Patentverwaltung Schaltungsanordnung mit einem schaltnetzteil

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
See references of WO9512840A1 *

Also Published As

Publication number Publication date
JPH09504679A (ja) 1997-05-06
WO1995012840A1 (fr) 1995-05-11
DE4337461A1 (de) 1995-05-04
US5708572A (en) 1998-01-13

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