EP0651461B1 - Antenne mit Strahlergruppe - Google Patents

Antenne mit Strahlergruppe Download PDF

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Publication number
EP0651461B1
EP0651461B1 EP94402449A EP94402449A EP0651461B1 EP 0651461 B1 EP0651461 B1 EP 0651461B1 EP 94402449 A EP94402449 A EP 94402449A EP 94402449 A EP94402449 A EP 94402449A EP 0651461 B1 EP0651461 B1 EP 0651461B1
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EP
European Patent Office
Prior art keywords
antenna
radiating elements
antenna according
arrays
circuits
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Expired - Lifetime
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EP94402449A
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English (en)
French (fr)
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EP0651461A1 (de
Inventor
André Champeau
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Thales SA
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Thomson CSF SA
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/29—Combinations of different interacting antenna units for giving a desired directional characteristic
    • H01Q21/293—Combinations of different interacting antenna units for giving a desired directional characteristic one unit or more being an array of identical aerial elements
    • H01Q21/296—Multiplicative arrays
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/06—Arrays of individually energised antenna units similarly polarised and spaced apart
    • H01Q21/22—Antenna units of the array energised non-uniformly in amplitude or phase, e.g. tapered array or binomial array

Definitions

  • the present invention relates to beam formation at the reception in a network antenna.
  • a network antenna consists of an assembly of elements radiant distributed in a network, mostly surface, according to a mesh of approximately half ⁇ / 2 of the wavelength of the emitted radiation or received to avoid the appearance of lobes of the network disturbing the directivity of the antenna.
  • the dimensioning of an antenna depends on the amplitude of the signal to be received, i.e. the signal to noise ratio desired in reception and the desired angular resolution.
  • the signals to be received are characterized by a uniform power surface density instead of receiving so that the strength of the useful signal received grows as the useful surface of the antenna.
  • the angular resolution is, for its part, defined in each direction by the linear dimension L of the antenna in the direction considered relative to the wavelength ⁇ in the relation ⁇ / L, the solid angular resolution being defined in the ratio ⁇ 2 / S where S is the surface of the antenna.
  • the absence of certain radiating elements means that the mesh at approximately ⁇ / 2 is no longer respected which leads to the appearance of network lobes if the disposition missing radiating elements is periodic or diffuse lobes if this arrangement is random. It is important to minimize these network and diffuse lobes.
  • a network antenna can be mechanically pointing or electronic.
  • the score is electronic, it can be associated with a analog beamforming or beamforming by the calculation.
  • Analog beam formation requires equipping the radiating elements of individual phase shifting modules allowing to orient the plane of the waves transmitted or received in the desired direction. She has the advantage of working both on transmission and on reception.
  • attenuators or a distribution network allow amplitude weighting.
  • Beam formation by calculation consists in digitizing the signals received by each of the radiating elements after they have been demodulated in a coherent way and then to phase them individually and to make a weighted sum by calculator to orient the wave plane received in the desired direction. It has the advantage of giving great flexibility in beam formation since it is possible to form simultaneously by calculating several beams pointing in directions different. It also allows for anti-jamming by adjustment the position of the zeros in the radiation diagram. However, she has the disadvantage of not being usable on the show, of requiring a expensive equipment for digitizing element signals radiant and claim a very large amount of calculations.
  • an antenna network is often used for both transmitting and receiving it is usual to equip the radiating elements with an antenna array of modules individual phase shifters allowing pointing by beam formation analog and group the radiating elements of the antenna into subnets to carry out anti-jamming on reception by training reduced beam by calculation, grouping of radiating elements taking place in surface sub-networks and beam formation by the calculation performed in the two pointing directions, deposit and site.
  • the reduced beam formation by calculation generates a radiation pattern whose main lobe retains the direction of pointing produced by the phase shift modules but whose zeros are moved in the direction of the jammers, this by playing second order on the relative phase shifts imposed on the reception signals of the sub-networks.
  • This radiation diagram keeps the disadvantage of having network lobes at angular positions discrete or diffuse lobes depending on whether the organization of the subnets areal in the network is periodic or random because the subnetworks necessarily have phase centers spaced a distance apart greater than or equal to ⁇ reflecting a subsampling of the surface of the network.
  • the object of the present invention is to form a beam for an array antenna with a low level of side lobes or lobes diffuse, whether this network antenna is full, incomplete or rarefied and provided or not of a reduced beam formation by calculation.
  • Its object is an antenna with a network of radiating elements which has its radiating elements grouped in reception, in two sets of parallel linear sub-networks oriented in two different directions, and which comprises two beam forming circuits each receiving the signals from one of the sets of subnets and each delivering a reduced beamforming signal, and an output circuit providing a reception signal from a non-linear combination of the two signals generated by the two beam forming circuits.
  • the directions of the two sets of subnets linear are orthogonal and oriented one according to the site plan and the other according to the network antenna field plan.
  • the output circuit does not combine linear the two signals generated by the two formation circuits of beam by performing for example either their product or their convolution.
  • Figure 1 illustrates a prior art array antenna with a planar network of 48 radiating elements distributed in a mesh of approximately ⁇ / 2, individually equipped with phase shift modules and shown under shape of contiguous blocks 1.
  • Each phase shift module allows to adjust individually the phase of each radiating element to obtain the emission or the reception a wave plane directed at the same time in deposit and in site.
  • the 48 radiant elements and their modules phase shifters 1 are grouped in parallel in groups of four into twelve Areal subnets 2 whose contours are shown in lines supported.
  • the reception signals of the twelve surface subnets 2 are then directed to a beam forming circuit 3 by calculation which performs reduced beam formation for anti-jamming, that is to say to obtain a reception radiation diagram with a main lobe in the pointing direction imposed by the modules phase shifters and zeros in the directions of the jammers. Bearing on twelve receive source signals this reduced beam formation allows to place zeros of the radiation diagram in eleven different directions and therefore eliminate eleven jamming directions. However, its performance is severely limited by the existence of large lobes or diffuse lobes due to equal spacing or greater than ⁇ between the phase centers of the surface sub-networks.
  • the radiating elements are distributed on reception a network antenna and their possible individual phase shift modules in two sets of parallel linear sub-networks oriented in two separate directions, we proceed to a reduced beam formation on each of two sets of parallel linear subnets and one combines the two signals obtained non-linearly by multiplication or convolution after a possible thresholding.
  • FIG. 2 represents a directive network antenna which can be electronically orientated on site and in a field implementing this solution.
  • This network antenna is composed of m ⁇ n radiating elements 4 associated with individual phase-shifting modules 5 and arranged in rows and columns according to a planar network with a mesh of approximately ⁇ / 2 to meet the surface sampling criterion guaranteeing the absence of network lobes in the case of an electronic scan over a wide angle.
  • Each radiating element with its phase shift module participates to the two sets of linear subnetworks by dividing its signal from output in two identical components in amplitude and in phase.
  • FIG. 3 separately represents the two nested sets of linear sub-networks 6, 7 to facilitate the explanation.
  • the antenna is pointed electronically at reception, and at transmission in the case of a radar, by means of phase shift modules.
  • all of the n horizontal linear sub-networks 6 supply n signals to a first beam forming circuit 8 which performs a reduced n- order beam formation in elevation while all of the m sub-networks vertical lines 7 provides m signals to a second beam forming circuit 9 which performs reduced beam formation of order m in bearing.
  • the reduced formation of beam in elevation gives a radiation pattern without grating lobes or diffuse lobes in the direction of the deposit since it takes place on the signals of solid horizontal linear sub-grids and with grating lobes or diffuse lobes in direction of the site compensated by the possibility of an adjustment of n -1 zeros in site.
  • the reduced formation of beam in bearing gives a radiation diagram without lobes of lattice or diffuse lobes in direction of the site since it is carried out on the signals of the vertical linear sub-networks full and with lobes of lattice or diffuse lobes in direction of the deposit offset by the possibility of adjusting m -1 zeros in the deposit.
  • the two beam forming circuits 8 and 9 can operate reduced beam formations by calculation and be produced by means of a computer.
  • the n + m output signals of the n + m horizontal and vertical linear sub-networks 6 and 7 are then demodulated in coherence and digitized before being applied to it.
  • the computer can perform the reduced beam formation in elevation and in bearing alternately, the order of formation in elevation then in bearing or vice versa having no influence.
  • the signals delivered by the two training circuits of bundle 8 and 9 are then applied to a combination circuit 10 which performs the product or convolution and issues a single output signal antenna.
  • the single antenna output signal appears, when it has origin a single transmitting source picked up by the antenna, as the signal of reception of an antenna which would have, for radiation diagram, the produces two radiation patterns of reduced formations of beam in site and in deposit; radiation pattern which is lacking network lobes and diffuse lobes due to subsampling because one of the component diagrams does not have a lobe or lobe diffuse in the site map and the other component diagram has no lobes of network or diffuse lobe in the deposit plan.
  • Figures 4a and 4b show, plotted in a trihedron of reference whose OX axis is graduated in bearing angle, OY axis in angle of the site and the OZ axis in signal level, the cross-sections in the XOZ planes and YOZ of the surfaces of the radiation patterns obtained at the output of two reduced beam formation circuits 9 and 8.
  • FIG. 4a represents the radiation diagram obtained at the output of the beam forming circuit 9 operating on the signals of the m vertical linear sub-networks 7. It comprises a fine main lobe oriented in the pointing direction imposed by the settings of the phase shift modules individual surrounded by side lobes of small amplitudes in the YOZ site plane because the sub-networks at the base of the reduced beam formation are full vertical linear sub-networks, and of more marked amplitudes in the XOZ field plane but with spacer zeros whose positions are adjustable by the adaptive action of reduced beamforming.
  • FIG. 4b represents the radiation diagram obtained in output of the beam forming circuit 8 operating on the signals of n Horizontal linear sub-networks 6. Like the previous one, it has a fine main lobe oriented in the direction of pointing imposed by the individual phase shift module settings. But this one is surrounded by small amplitude side lobes in the XOZ plane, because the subnets at the base of reduced beam formation are subnets full horizontal lines, and of more marked amplitudes in the YOZ site map but with insert zeros whose positions are adjustable by the adaptive action of reduced beam formation.
  • the adaptive actions of the two reduced beam formations one independently in the site plan, the other in the plan deposit by creating zeros in the form of valleys recalled in the figures 4a, 4b by dotted lines, each valley consuming only one degree of freedom on only one of the two reduced beam formations.
  • the product of the two diagrams presents two sets of adjustable zeros angularly one in the site plan, the other in the deposit plan which shows the advantage of performing between the signals of the two training circuits reduced beam a nonlinear combination such as a product or a convolution.
  • it is interesting to subject the thresholds to signals from the two reduced beam forming circuits to prevent a parasitic signal received by one of the two formations reduced beam is only validated by thermal noise from the other reduced beam formation. There is then no incompatibility so that the threshold chosen is not that of limiting false alarms by noise in a detection process.
  • FIG. 5 illustrates the network antenna diagram to which we end up.
  • This comprises a network of radiating elements arranged in rows and columns in a mesh of approximately ⁇ / 2 and equipped with individual phase-shifting modules.
  • the radiating elements are shown without their phase shift modules and the network is shown split in 12 and 12 '.
  • At 12 appears the first grouping in reception of the radiating elements in m vertical linear sub-networks 13 delivering m signals to a first reduced beam forming circuit 14 operating in the plane of the deposit.
  • Two threshold circuits 17, 18 placed at the output of the two beam forming circuits 14, 16 provide a basing of their signals before the latter are applied to a nonlinear combination circuit 19 which produces the product or the convolution thereof.
  • the product operation can be a simple multiplication, a addition of signals which we have taken the logarithm or a logical operation of type "and" controlled by signals made previously bivalent.
  • Multiplication improves angular resolution because, at width of identical main lobe, the attenuation in dB is double that of each of the two sets of subnets considered in isolation, but this at the price of a 6 dB loss in signal to noise ratio.
  • the two signals delivered by the two training circuits of beam being of identical amplitudes, we are in optimal conditions of a multiplication operation.
  • the convolution operation allows to mitigate even more strongly the interfering signals received in one of the reduced formations of beam and not in the other, by absence of correlation with the signal emitted by the radar, or between them.
  • the spacing between the linear sub-networks of each set grows, in geometric progression, from one edge to the other of the antenna, but other spacings without harmonic periodicity are possible.
  • the radiating elements located at the crossing points of the vertical and horizontal linear subnets participate in both assemblies and are fitted with individual output phase shift modules double delivering identical signals in amplitude and phase.
  • the other radiating elements have individual phase shift modules with output simple. Whether coming from single or double output modules, the signals are of the same magnitude and have relative phases which are those of the law pointing the antenna.
  • the outputs of the vertical linear sub-networks 20 of the first together are connected to the inputs of a first training circuit 22 beam in the reservoir plane while the outputs of the subnetworks horizontal lines 21 of the second set are connected to inputs of a second beam-forming circuit 23 in the site plan.
  • the two outputs of the two beam forming circuits 22, 23 are, as in the case of FIG. 5, connected via two threshold circuits at the two inputs of a combination circuit no linear performing a product or a convolution to generate the signal of antenna output.
  • the antenna is pointed electronically by the modules individual phase shifters, on reception and also on transmission in the case of a radar.
  • the first circuit 22 of reduced beam formation delivers, at the reception, a signal corresponding to that of an antenna having a radiation pattern with weak lobes in the site plane secondary defined by the weighting law applied analogically.
  • Figure 7a gives an example of such a diagram with diffuse lobes.
  • the second circuit 23 of reduced beam formation delivers, at reception, a signal corresponding to that of an antenna having a radiation pattern with weak lobes in the deposit plane secondary defined by the law of weighting applied analogously to each horizontal linear sub-network 21 and, in the site plane, lobes of diffuse network or lobes depending on whether the scarcity of all the sub-networks full horizontal linear 21 is distributed periodically or randomly.
  • Figure 7b gives an example of such a diagram with diffuse lobes.
  • the two formations beam reductions obtained can be fixed or adaptive and, in the latter case, allowing the positioning of zeros, separately in site and deposit as illustrated previously in Figures 4a and 4b.
  • the thresholding of the two signals resulting from the two reduced beam formations separated in the site and deposit planes and their non-linear combination by product or convolution makes it possible to obtain a reception signal having properties similar to that of a beam-forming antenna total with only two reduced orthogonal beam formations of cumulative moments n + m .
  • the number of degrees of freedom in other words, the number of adaptive zeros achievable is of course only ( m -1) + ( n -1) but the lattices or diffuse lobes have been eliminated by the product operation or convolution subject only to the fact that the secondary lobes orthogonal to these lattices or diffuse lobes have themselves been eliminated by the thresholding operation on the two channels, hence the advantage of adaptive thresholds taking into account the level disturbing signals, such as clutter residue. Interference-type disturbers will be treated in the first degree by zeros in the two reduced adaptive beam formations, but possible residues will receive additional treatment by the combination of thresholding and product or convolution operations.
  • the proposed network antenna architecture avoids the limitations of the prior art by an organization of its radiating elements based on a juxtaposition side by side in parallel, of m linear sub-networks of n elements contiguous to each other and whose centers of phase are spaced according to sampling criteria of the antenna surface which avoid the creation of high lobe or diffuse lobes. Limited to this organization, the antenna could only be provided with beam formation in the plane perpendicular to the sub-arrays. To avoid this, the radiating elements of the antenna are reused to form a second juxtaposition side by side in parallel with n sub-arrays of m elements orthogonal to the first sub-arrays and completely nested in them.
  • two beam formations are produced at m and n moments in two orthogonal planes whose signals are combined non-linearly by product or convolution to obtain a reception signal similar to that of '' a network antenna forming a two-plane network at n ⁇ m moments.
  • the proposed antenna architecture presents two ways of reception from the two reduced beam formations on which it may be advantageous to carry out, before the product or convolution, certain treatments such as Doppler filtering of fixed echoes in the case of a radar, which are then split.
  • the cost of this duplication is however much less than that of a total formation of beam in two planes and is fully justified by performance obtained in comparison with those of a reduced beam formation two plans of the prior art.
  • Figure 8 gives an example of an antenna rarefied non-periodic network with reduced beam formations putting in the proposed architecture.
  • the radiating elements are fitted with phase shift modules individual.
  • the element-to-element spacing in subnets is 0.55 ⁇ .
  • the spacing between their sub-networks is variable and grows from one edge to the other of the antenna by example in geometric progression.
  • the antenna obtained is part of a 49.5 ⁇ by 41.8 ⁇ surface giving a directivity of about 3 dB 1.45 degrees by 1.7 degrees.
  • the full antenna equivalent in this aspect would include 6,840 radiating elements and individual phase shift modules whereas this one comprises only 1835. The coefficient of rarefaction is therefore 3.73.
  • the output signals of the eleven linear subnetworks horizontal 30 of the first set are scanned before being applied to a first beam forming circuit by calculation 32 which performs reduced adaptive beam formation in the vertical or planar plane eleven-point site, allowing ten directions anti-jamming different on site.
  • the output signals of the thirteen vertical linear sub-networks 31 of the second set are digitized before being applied to a second beamforming circuit by calculation 33 which performs a reduced adaptive beamforming in the horizontal or planar plane deposit at thirteen points, thus allowing the jamming of twelve different directions in deposit.
  • the two signals delivered by the two training circuits of beam by calculation 32, 33 or rather, their modules are applied to two threshold circuits 34, 35.
  • the signals delivered by the two threshold circuits 34 and 35 are then applied to the inputs of a type 36 logic circuit performing their produces and delivers the antenna reception signal.

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  • Variable-Direction Aerials And Aerial Arrays (AREA)
  • Aerials With Secondary Devices (AREA)

Claims (13)

  1. Antenne mit einem Netz von Strahlungselementen, dadurch gekennzeichnet, daß ihre Strahlungselemente in Empfangsrichtung in zwei Einheiten von parallelen linearen Unternetzen (6, 7) gruppiert sind, die entlang von zwei unterschiedlichen Richtungen ausgerichtet sind, und daß die Antenne zwei Strahlbildungsschaltungen (8, 9) aufweist, die je die Signale einer der Einheiten von linearen Unternetzen (6, 7) empfangen und je ein Signal eingeschränkter Strahlbildung liefern, wobei eine Ausgangsschaltung (10) eine Empfangssignal ausgehend von einer nichtlinearen Verknüpfung der beiden Signale einer eingeschränkten Strahlbildung liefert, die von den beiden Strahlbildungsschaltungen (8, 9) erzeugt werden.
  2. Antenne nach Anspruch 1, dadurch gekennzeichnet, daß die Richtungen der linearen Unternetze (6, 7) der beiden Einheiten senkrecht zueinander stehen.
  3. Antenne nach Anspruch 2, dadurch gekennzeichnet, daß die Richtung der linearen Unternetze (6) einer der Einheiten waagrecht und die Richtung der linearen Unternetze (7) der anderen Einheit senkrecht verläuft.
  4. Antenne nach Anspruch 1, dadurch gekennzeichnet, daß die beiden Einheiten von linearen Unternetzen (6, 7) miteinander verschachtelt sind.
  5. Antenne nach Anspruch 1, dadurch gekennzeichnet, daß sie lückenhaft besetzt ist, wobei ihr Netz von Strahlungselementen Lücken aufweist und die Anzahl der fehlenden Strahlungselemente kleiner als die Anzahl der vorhandenen Strahlungselemente ist.
  6. Antenne nach Anspruch 1, dadurch gekennzeichnet, daß sie verarmt besetzt ist, wobei ihr Netz von Strahlungselementen Lücken aufweist und die Anzahl der fehlenden Strahlungselemente größer als die Anzahl der vorhandenen Strahlungselemente ist.
  7. Antenne nach Anspruch 1, dadurch gekennzeichnet, daß in jeder Einheit von parallelen linearen Unternetzen (20, 21) die parallelen linearen Unternetze (20, 21) einen gegenseitigen Abstand besitzen, der von einem Rand zum anderen der Antenne variiert.
  8. Antenne nach Anspruch 7, dadurch gekennzeichnet, daß der Abstand von einem Rand zum anderen der Antenne gemäß einer geometrischen Progression variiert.
  9. Antenne nach Anspruch 1, dadurch gekennzeichnet, daß sie außerdem zwei Schwellenschaltungen (17, 18) zwischen den beiden Strahlbildungsschaltungen (8, 9) und der Ausgangsschaltung (10) eingefügt enthält.
  10. Antenne nach Anspruch 1, dadurch gekennzeichnet, daß die Ausgangsschaltung (10) eine Konvolutionsschaltung ist.
  11. Antenne nach Anspruch 1, dadurch gekennzeichnet, daß die Ausgangsschaltung (10) eine Multiplizierschaltung ist.
  12. Antenne nach Anspruch 1, dadurch gekennzeichnet, daß sie außerdem zwischen den beiden Strahlbildungssschaltungen (32, 33) und der Ausgangsschaltung (36) zwei Schwellenschaltungen (34, 35) enthält, die die von den beiden Strahlbildungsschaltungen (32, 33) gelieferten Signale in binäre Signale umwandelt und daß die Ausgangsschaltung (36) eine logische Schaltung vom UND-Typ ist.
  13. Antenne nach Anspruch 1, dadurch gekennzeichnet, daß die Strahlbildungsschaltungen (8, 9) auf einer Berechnung beruhen und eine Störsignalunterdrückungsfunktion gewährleisten.
EP94402449A 1993-11-02 1994-10-28 Antenne mit Strahlergruppe Expired - Lifetime EP0651461B1 (de)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
FR9312995 1993-11-02
FR9312995A FR2712121B1 (fr) 1993-11-02 1993-11-02 Antenne à réseau d'éléments rayonnants.

Publications (2)

Publication Number Publication Date
EP0651461A1 EP0651461A1 (de) 1995-05-03
EP0651461B1 true EP0651461B1 (de) 1998-05-06

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EP94402449A Expired - Lifetime EP0651461B1 (de) 1993-11-02 1994-10-28 Antenne mit Strahlergruppe

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US (1) US5675343A (de)
EP (1) EP0651461B1 (de)
JP (1) JPH07273530A (de)
CA (1) CA2134055A1 (de)
DE (1) DE69410059T2 (de)
ES (1) ES2115179T3 (de)
FR (1) FR2712121B1 (de)

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US6124828A (en) * 1997-07-08 2000-09-26 Thomson-Csf Anti-jamming array antenna
EP1045473A2 (de) * 1999-04-16 2000-10-18 Robert Bosch Gmbh Multibeam-Phasenarray-Antenneneinrichtung
EP1045473A3 (de) * 1999-04-16 2001-04-11 Robert Bosch Gmbh Multibeam-Phasenarray-Antenneneinrichtung
US6362780B1 (en) 1999-04-16 2002-03-26 Robert Bosch Gmbh Multi-beam phase-array antenna device

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DE69410059D1 (de) 1998-06-10
US5675343A (en) 1997-10-07
JPH07273530A (ja) 1995-10-20
ES2115179T3 (es) 1998-06-16
DE69410059T2 (de) 1998-09-03
EP0651461A1 (de) 1995-05-03
CA2134055A1 (fr) 1995-05-03
FR2712121A1 (fr) 1995-05-12
FR2712121B1 (fr) 1995-12-15

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