EP0651461A1 - Antenne mit Strahlergruppe - Google Patents

Antenne mit Strahlergruppe Download PDF

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Publication number
EP0651461A1
EP0651461A1 EP94402449A EP94402449A EP0651461A1 EP 0651461 A1 EP0651461 A1 EP 0651461A1 EP 94402449 A EP94402449 A EP 94402449A EP 94402449 A EP94402449 A EP 94402449A EP 0651461 A1 EP0651461 A1 EP 0651461A1
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EP
European Patent Office
Prior art keywords
radiating elements
antenna
antenna according
arrays
signals
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Granted
Application number
EP94402449A
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English (en)
French (fr)
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EP0651461B1 (de
Inventor
André Champeau
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Thales SA
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Thomson CSF SA
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/29—Combinations of different interacting antenna units for giving a desired directional characteristic
    • H01Q21/293—Combinations of different interacting antenna units for giving a desired directional characteristic one unit or more being an array of identical aerial elements
    • H01Q21/296—Multiplicative arrays
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/06—Arrays of individually energised antenna units similarly polarised and spaced apart
    • H01Q21/22—Antenna units of the array energised non-uniformly in amplitude or phase, e.g. tapered array or binomial array

Definitions

  • the present invention relates to beam formation on reception in a network antenna.
  • a network antenna consists of an assembly of radiating elements distributed in a network, most of the time surface, in a mesh of approximately half ⁇ / 2 of the wavelength of the radiation emitted or received to avoid the appearance of lobes of the network disturbing the directivity of the antenna.
  • the dimensioning of an antenna is a function of the amplitude of the signal to be received, that is to say the signal to noise ratio desired at reception and the angular resolution desired.
  • the signals to be received are characterized by a uniform power surface density at the place of reception so that the power of the received useful signal increases as the useful surface of the antenna.
  • the angular resolution is, for its part, defined in each direction by the linear dimension L of the antenna in the direction considered relative to the wavelength ⁇ in the relation ⁇ / L, the solid angular resolution being defined in the ratio ⁇ 2 / S where S is the surface of the antenna.
  • the absence of certain radiating elements means that the mesh at approximately ⁇ / 2 is no longer respected, which leads to the appearance of network lobes if the arrangement of the missing radiating elements is periodic or diffuse lobes if this arrangement is random. It is important to reduce these network and diffuse lobes as much as possible.
  • a network antenna can be mechanical or electronic pointing.
  • the pointing is electronic, it can be associated with an analog beam formation or with a beam formation by calculation.
  • Analog beam formation requires equipping the radiating elements with individual phase shifting modules making it possible to orient the plane of the waves transmitted or received in the desired direction. It has the advantage of working both on transmission and on reception.
  • attenuators or a distribution network allow amplitude weighting.
  • Beam formation by calculation consists in digitizing the signals received by each of the radiating elements after they have been coherently demodulated, then in phase shifting them individually and in making a weighted sum thereof by computer to orient the plane of the waves received in the desired direction. It has the advantage of giving great flexibility to beam formation since it is possible to simultaneously form by calculation several beams pointing in different directions. It also allows anti-jamming by adjusting the position of the zeros in the radiation diagram. However, it has the disadvantage of not being usable on transmission, of requiring expensive equipment for digitizing the signals of the radiating elements and of requiring a very large amount of calculations.
  • a network antenna is often used for both transmission and reception, it is customary to equip the radiating elements of a network antenna with individual phase shift modules allowing pointing by analog beam formation and grouping the radiating elements of the antenna in sub-arrays to effect an anti-jamming on reception by a reduced beam formation by calculation, the regrouping of the radiating elements being effected in surface sub-arrays and the beam formation by calculation taking place in the two pointing directions, deposit and site.
  • the reduced beam formation by the calculation generates a radiation diagram whose main lobe retains the pointing direction produced by the phase-shifting modules but whose zeros are displaced in the direction of the jammers, this by playing in the second order on the relative phase shifts imposed on the subnetwork reception signals.
  • this radiation diagram retains the disadvantage of having lobes of the network at discrete angular positions or diffuse lobes depending on whether the organization of the surface sub-networks in the network is periodic or random because the sub -networks necessarily have phase centers spaced by a distance greater than or equal to ⁇ reflecting a subsampling of the network surface.
  • the aim of the present invention is to form a beam for a network antenna with a low level of secondary lobes or of diffuse lobes, whether this network antenna is full, incomplete or rarefied and whether or not provided with reduced beam formation by calculation. .
  • Its subject is an antenna with a network of radiating elements which has its radiating elements grouped together on reception, in two sets of parallel linear sub-arrays oriented in two different directions, and which comprises two beam forming circuits each receiving the signals of one of the sets of sub-networks and each delivering a reduced beam-forming signal, and an output circuit delivering a reception signal from a non-linear combination of the two signals generated by the two beam-forming circuits .
  • the directions of the two sets of linear sub-arrays are orthogonal and oriented one along the site plane and the other along the bearing plane of the array antenna.
  • the output circuit non-linearly combines the two signals generated by the two beam forming circuits, for example by performing either their product or their convolution.
  • FIG. 1 illustrates a network antenna of the prior art with a planar network of 48 radiating elements distributed in a mesh of approximately ⁇ / 2, individually equipped with phase-shifting modules and represented in the form of contiguous blocks 1.
  • Each phase-shifting module allows '' individually adjust the phase of each radiating element to obtain The emission or the reception a wave plane oriented at the same time in deposit and in site.
  • the 48 radiating elements and their phase-shifting modules 1 are grouped in parallel in groups of four into twelve surface sub-networks 2, the contours of which are shown in solid lines.
  • reception signals of the twelve surface sub-networks 2 are then directed to a beam forming circuit 3 by the calculation which performs a reduced beam formation for anti-jamming, that is to say to obtain a radiation diagram. in reception with a main lobe in the pointing direction imposed by the phase shift modules and zeros in the directions of the jammers. Relating to twelve signals from reception sources, this reduced beam formation makes it possible to place zeros of the radiation diagram in eleven different directions and therefore to eliminate eleven directions of interference. However, its performance is severely limited by the existence of lattices or high diffuse lobes due to the spacing equal to or greater than ⁇ between the phase centers of the surface subnetworks.
  • the radiating elements of a network antenna and their possible individual phase shift modules are distributed in reception in two sets of parallel linear sub-networks oriented in two distinct directions, a reduced beam formation is carried out on each of two sets. of parallel linear sub-networks and the two signals obtained are combined non-linearly by multiplication or convolution after a possible thresholding.
  • FIG. 2 represents a directive network antenna which can be electronically orientated on site and in a field implementing this solution.
  • This network antenna is composed of m ⁇ n radiating elements 4 associated with individual phase-shifting modules 5 and arranged in rows and columns according to a planar network with a mesh of approximately ⁇ / 2 to meet the surface sampling criterion guaranteeing the absence of network lobes in the case of an electronic scan over a wide angle.
  • Each radiating element with its phase shift module participates in two sets of linear sub-arrays by dividing its output signal into two identical components in amplitude and in phase.
  • FIG. 3 separately represents the two nested sets of linear sub-networks 6, 7 to facilitate the explanation.
  • the antenna is pointed electronically at reception, and at transmission in the case of a radar, by means of phase shift modules.
  • all of the n horizontal linear sub-networks 6 supply n signals to a first beam forming circuit 8 which performs a reduced n- order beam formation in elevation while all of the m sub-networks vertical lines 7 provides m signals to a second beam forming circuit 9 which performs reduced beam formation of order m in bearing.
  • the reduced formation of beam in elevation gives a radiation pattern without grating lobes or diffuse lobes in the direction of the deposit since it takes place on the signals of solid horizontal linear sub-grids and with grating lobes or diffuse lobes in direction of the site compensated by the possibility of an adjustment of n -1 zeros in site.
  • the reduced formation of beam in bearing gives a radiation diagram without lobes of lattice or diffuse lobes in direction of the site since it is carried out on the signals of the vertical vertical sub-gratings full and with lobes of lattice or diffuse lobes in direction of the deposit compensated by the possibility of adjusting m -1 zeros in the deposit.
  • the two beam forming circuits 8 and 9 can operate reduced beam formations by calculation and be produced by means of a computer.
  • the n + m output signals of the n + m horizontal and vertical linear sub-networks 6 and 7 are then demodulated in coherence and digitized before being applied to it.
  • the computer can perform the reduced beam formation in elevation and in bearing alternately, the order of formation in elevation then in bearing or vice versa having no influence.
  • the signals delivered by the two beam forming circuits 8 and 9 are then applied to a combination circuit 10 which performs the product or the convolution thereof and delivers a single antenna output signal.
  • the single antenna output signal appears, when it originates from a single transmitting source picked up by the antenna, like the reception signal of an antenna which would have, for radiation pattern, the product of the two radiation patterns reduced beam formations on site and in deposits; radiation diagram which lacks lobes and diffuse lobes due to sub-sampling because one of the component diagrams does not have a lobe or diffuse lobe in the site plan and the other component diagram does not has no network lobes or diffuse lobes in the deposit plane.
  • Figures 4a and 4b show, plotted in a reference trihedron whose OX axis is graduated in bearing angle, OY axis in elevation angle and OZ axis in signal level, the cross-sections in the XOZ planes and YOZ of the surfaces of the radiation patterns obtained at the output of the two reduced beam formation circuits 9 and 8.
  • FIG. 4a represents the radiation diagram obtained at the output of the beam forming circuit 9 operating on the signals of the m vertical linear sub-networks 7. It comprises a fine main lobe oriented in the pointing direction imposed by the settings of the modules individual phase shifters surrounded by secondary lobes of small amplitudes in the YOZ site plane because the sub-networks at the base of the reduced beam formation are full vertical linear sub-networks, and of more marked amplitudes in the XOZ field plane but with interleaving zeros whose positions are adjustable by the adaptive action of the reduced beam formation.
  • FIG. 4b represents the radiation diagram obtained at the output of the beam forming circuit 8 operating on the signals of n horizontal linear sub-networks 6. Like the preceding one, it comprises a fine main lobe oriented in the pointing direction imposed by the individual phase shift module settings. But this one is surrounded by secondary lobes of low amplitudes in the plane XOZ deposit because the sub-networks at the base of the reduced beam formation are full horizontal linear sub-networks, and of more marked amplitudes in the site plan YOZ but with intermediate zeros whose positions are adjustable by the adaptive action of the reduced beam formation.
  • the adaptive actions of the two reduced beam formations are performed independently, one in the site plane, the other in the reservoir plane by creating zeros in the form of valleys recalled in FIGS. 4a, 4b by dotted lines, each valley consuming only one degree of freedom on only one of the two reduced beam formations.
  • the product of the two diagrams presents two series of angularly adjustable zeros, one in the site plane, the other in the bearing plane, which shows the advantage of effecting a non-combination between the signals of the two circuits of reduced beam formation. linear such as a product or a convolution.
  • FIG. 5 illustrates the network antenna diagram to which we end up.
  • This comprises a network of radiating elements arranged in rows and columns in a mesh of approximately ⁇ / 2 and equipped with phase-shifting modules individual.
  • the radiating elements are shown without their phase shift modules and the network is shown split in 12 and 12 '.
  • the first grouping appears on reception of the radiating elements in m vertical linear sub-networks 13 delivering m signals to a first reduced beam forming circuit 14 operating in the reservoir plane.
  • the second grouping in reception of the radiating elements appears in n horizontal linear sub-networks 15 delivering n signals to a second reduced beam forming circuit 16 operating in the site plane.
  • Two threshold circuits 17, 18 placed at the output of the two beam forming circuits 14, 16 provide a basing of their signals before the latter are applied to a nonlinear combination circuit 19 which produces the product or the convolution thereof.
  • the operation produced can be a simple multiplication, an addition of signals of which we have taken the logarithm or a logical operation of type "and" controlled by signals rendered previously bivalent.
  • Multiplication improves the angular resolution because, at identical main lobe width, the attenuation in dB is twice that of each of the two sets of sub-networks considered in isolation, but this, at the cost of a loss of 6 dB in relation signal to noise.
  • the two signals delivered by the two beam forming circuits being of identical amplitudes, we are in the optimal conditions of a multiplication operation.
  • the convolution operation makes it possible to attenuate even more strongly the interfering signals picked up in one of the reduced beam formations and not in the other, by absence correlation with the signal emitted by the radar, or between them.
  • the spacing between the linear sub-arrays of each set increases, in geometric progression, from one edge to the other of the antenna, but other spacings without harmonic periodicity are possible.
  • the radiating elements located at the crossing points of the vertical and horizontal linear sub-networks participate in the two assemblies and are equipped with individual phase-shifting modules with double output delivering identical signals in amplitude and in phase.
  • the other radiating elements have individual phase-shift modules with single output. Whether they come from single or double output modules, the signals are of the same amplitude and have relative phases which are those of the antenna pointing law.
  • the outputs of the vertical linear sub-networks 20 of the first set are connected to the inputs of a first beam-forming circuit 22 in the plane of bearing while the outputs of the horizontal linear sub-networks 21 of the second set are connected to the inputs of a second beam forming circuit 23 in the site plane.
  • the two outputs of the two beam forming circuits 22, 23 are, as in the case of FIG. 5, connected via two threshold circuits at the two inputs of a nonlinear combination circuit performing a product or a convolution to generate the antenna output signal.
  • the antenna is pointed electronically by the individual phase shift modules, at reception and also at transmission in the case of a radar.
  • the first circuit 22 of reduced beam formation delivers, on reception, a signal corresponding to that of an antenna having a radiation pattern with, in the site plane, small lobes secondary defined by the law of weighting applied analogously to each full vertical linear sub-network 20 and, in the bearing plane, of lobes of network or diffuse lobes according to whether the rarefaction of the set of full vertical linear sub-networks 20 is distributed periodically or randomly.
  • Figure 7a gives an example of such a diagram with diffuse lobes.
  • the second circuit 23 of reduced beam formation delivers, on reception, a signal corresponding to that of an antenna having a radiation diagram with, in the bearing plane, small secondary lobes defined by the law of weighting applied analogously to each horizontal linear sub-network 21 and, in the site plane, network lobes or diffuse lobes depending on whether the rarefaction of all of the full horizontal linear sub-networks 21 is distributed periodically or randomly.
  • Figure 7b gives an example of such a diagram with diffuse lobes.
  • the two reduced beam formations obtained can be fixed or adaptive and, in the latter case, allow the positioning of zeros, separately in site and in deposit as illustrated previously in FIGS. 4a and 4b.
  • the thresholding of the two signals resulting from the two reduced beam formations separated in the site and deposit planes and their non-linear combination by product or convolution makes it possible to obtain a reception signal having properties similar to that of a beam-forming antenna total with only two reduced orthogonal beam formations of cumulative moments n + m .
  • the number of degrees of freedom in other words, the number of adaptive zeros achievable is of course only ( m -1) + ( n -1) but the lattices or diffuse lobes have been eliminated by the product operation or convolution subject only to the fact that the secondary lobes orthogonal to these lattices or diffuse lobes have themselves been eliminated by the thresholding operation on the two channels, hence, the advantage of adaptive thresholds taking into account the level disturbing signals, such as clutter residue. Interference-type disturbers will be treated in the first degree by zeros in the two reduced adaptive beam formations, but possible residues will be given a complementary processing by the combination of thresholding and product or convolution operations.
  • the proposed network antenna architecture avoids the limitations of the prior art by an organization of its radiating elements based on a juxtaposition side by side in parallel, of m linear sub-networks of n elements contiguous to each other and whose centers of phase are spaced according to sampling criteria of the antenna surface which avoid the creation of high lobe or diffuse lobes. Limited to this organization, the antenna could only be provided with beam formation in the plane perpendicular to the sub-arrays. To avoid this, the radiating elements of the antenna are reused to form a second juxtaposition side by side in parallel with n sub-arrays of m elements orthogonal to the first sub-arrays and completely nested in them.
  • two beam formations are produced at m and n moments in two orthogonal planes whose signals are combined non-linearly by product or convolution to obtain a reception signal similar to that of '' a network antenna forming a two-plane network at n ⁇ m moments.
  • the signal-to-disruptor ratio is improved because it virtually eliminates the intervention of thermal noise. of each of the two signals in the product or convolution operation allowing the development of the reception signal.
  • the proposed antenna architecture has two reception channels from the two reduced beam formations on which it may be advantageous to carry out, before the product or convolution operation, certain treatments such as the Doppler filtering of fixed echoes in the radar, which are then split.
  • the cost of this duplication is however much less than that of a total training of beam in two planes and is entirely justified by the performances obtained in comparison with those of a reduced beam formation two planes of the prior art.
  • the network antennas incomplete or rarefied, are affected by powerful network or diffuse lobes.
  • the proposed antenna architecture avoids this major drawback.
  • the adaptivity properties are not required in the reduced beam formations, these can be performed in analog.
  • FIG. 8 gives an exemplary embodiment of a rarefied non-periodic array antenna with reduced beam formations implementing the proposed architecture.
  • the radiating elements are fitted with individual phase shift modules.
  • the spacing of element to element in the sub-networks is 0.55 ⁇ .
  • the spacing between their sub-networks is variable and increases from edge to edge. 'other antenna for example in geometric progression.
  • the antenna obtained fits into a surface of 49.5 ⁇ by 41.8 ⁇ giving a directivity of about 3 dB 1.45 degrees by 1.7 degrees.
  • the equivalent full antenna in this aspect would have 6,840 radiating elements and individual phase-shifting modules, while this one only has 1,835.
  • the rarefaction coefficient is therefore 3.73.
  • the output signals of the eleven horizontal linear sub-arrays 30 of the first set are digitized before being applied to a first beamforming circuit by computation 32 which performs reduced adaptive beamforming in the vertical plane or site plane on eleven points, thus allowing anti-jamming from ten different directions on site.
  • the output signals of the thirteen vertical linear sub-arrays 31 of the second set are digitized before being applied to a second beam forming circuit by calculation 33 which performs reduced adaptive beam formation in the horizontal plane or bearing plane on thirteen points, thus allowing the anti-jamming of twelve different directions in bearing.
  • the two signals delivered by the two beam forming circuits by calculation 32, 33 or rather, their modules are applied to two threshold circuits 34, 35.
  • the signals delivered by the two threshold circuits 34 and 35 are then applied to the inputs of a type 36 logic circuit performing their product and delivering the antenna reception signal.

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  • Variable-Direction Aerials And Aerial Arrays (AREA)
  • Aerials With Secondary Devices (AREA)
EP94402449A 1993-11-02 1994-10-28 Antenne mit Strahlergruppe Expired - Lifetime EP0651461B1 (de)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
FR9312995 1993-11-02
FR9312995A FR2712121B1 (fr) 1993-11-02 1993-11-02 Antenne à réseau d'éléments rayonnants.

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EP0651461A1 true EP0651461A1 (de) 1995-05-03
EP0651461B1 EP0651461B1 (de) 1998-05-06

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US (1) US5675343A (de)
EP (1) EP0651461B1 (de)
JP (1) JPH07273530A (de)
CA (1) CA2134055A1 (de)
DE (1) DE69410059T2 (de)
ES (1) ES2115179T3 (de)
FR (1) FR2712121B1 (de)

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D.E.N. DAVIES ET AL.: "Low sidelobe patterns from thinned arrays using multiplicative processing", IEE PROCEEDINGS F. COMMUNICATIONS, RADAR & SIGNAL PROCESSING, vol. 127, no. 1, February 1980 (1980-02-01), STEVENAGE GB, pages 9 - 15 *

Cited By (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0891005A1 (de) * 1997-07-08 1999-01-13 Thomson-Csf Gruppenantenne mit Störungschutz
FR2766017A1 (fr) * 1997-07-08 1999-01-15 Thomson Csf Antenne reseau antibrouillee
WO2005071791A1 (fr) * 2003-12-24 2005-08-04 Thales Procede d'optimisation de l’architecture d’une antenne multifaisceaux a formation de faisceaux par le calcul (ffc) a sous-reseaux imbriques.

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DE69410059D1 (de) 1998-06-10
US5675343A (en) 1997-10-07
JPH07273530A (ja) 1995-10-20
ES2115179T3 (es) 1998-06-16
DE69410059T2 (de) 1998-09-03
CA2134055A1 (fr) 1995-05-03
FR2712121A1 (fr) 1995-05-12
EP0651461B1 (de) 1998-05-06
FR2712121B1 (fr) 1995-12-15

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