EP0524008A1 - Transmetteur à circuits de correction de non-linéarité - Google Patents

Transmetteur à circuits de correction de non-linéarité Download PDF

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Publication number
EP0524008A1
EP0524008A1 EP92306557A EP92306557A EP0524008A1 EP 0524008 A1 EP0524008 A1 EP 0524008A1 EP 92306557 A EP92306557 A EP 92306557A EP 92306557 A EP92306557 A EP 92306557A EP 0524008 A1 EP0524008 A1 EP 0524008A1
Authority
EP
European Patent Office
Prior art keywords
signal
envelope
detector
diode
circuit
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Granted
Application number
EP92306557A
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German (de)
English (en)
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EP0524008B1 (fr
Inventor
Takayuki Matsumoto
Hiroaki Kosugi
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Panasonic Holdings Corp
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Matsushita Electronics Corp
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Filing date
Publication date
Application filed by Matsushita Electronics Corp filed Critical Matsushita Electronics Corp
Publication of EP0524008A1 publication Critical patent/EP0524008A1/fr
Application granted granted Critical
Publication of EP0524008B1 publication Critical patent/EP0524008B1/fr
Anticipated expiration legal-status Critical
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Classifications

    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03G—CONTROL OF AMPLIFICATION
    • H03G3/00—Gain control in amplifiers or frequency changers
    • H03G3/20—Automatic control
    • H03G3/30—Automatic control in amplifiers having semiconductor devices
    • H03G3/3036—Automatic control in amplifiers having semiconductor devices in high-frequency amplifiers or in frequency-changers
    • H03G3/3042—Automatic control in amplifiers having semiconductor devices in high-frequency amplifiers or in frequency-changers in modulators, frequency-changers, transmitters or power amplifiers
    • H03G3/3047—Automatic control in amplifiers having semiconductor devices in high-frequency amplifiers or in frequency-changers in modulators, frequency-changers, transmitters or power amplifiers for intermittent signals, e.g. burst signals
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
    • H03D1/00—Demodulation of amplitude-modulated oscillations
    • H03D1/08—Demodulation of amplitude-modulated oscillations by means of non-linear two-pole elements
    • H03D1/10—Demodulation of amplitude-modulated oscillations by means of non-linear two-pole elements of diodes
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/32—Modifications of amplifiers to reduce non-linear distortion
    • H03F1/3241—Modifications of amplifiers to reduce non-linear distortion using predistortion circuits
    • H03F1/3247—Modifications of amplifiers to reduce non-linear distortion using predistortion circuits using feedback acting on predistortion circuits
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F2200/00—Indexing scheme relating to amplifiers
    • H03F2200/102—A non-specified detector of a signal envelope being used in an amplifying circuit

Definitions

  • the invention relates to a transmitter of wireless appliance employing a digital modulation system.
  • a transmitter employing a digital modulation system has been developed and disclosed in the U. S. Patent Application Serial No. 07/777,012.
  • the distortion of power amplifier is compensated by taking out a part of the transmission signal from the power amplifier, comparing the transmission envelope signal in which the signal is detected of the envelope and a distortion-free envelope signal in an error detector to generate an error signal, and controlling the gain of a gain control amplifier by using this error signal as the gain control signal.
  • This appliance has many points to be improved.
  • a variable gain control amplifier is controlled by positive DC voltage with some degrees.
  • an output voltage of error amplifier is fixed by the gain of the error amplifier, and a voltage difference between the transmission envelope signal and the distortion-free reference envelope signal. This output voltage of the error amplifier is directly used as a control voltage of the gain control amplifier.
  • Vg (Vcont-Vdeta) where G.Vcont and Vdeta are a gain of the error amplifier, a voltage of the distortion-free reference envelope signal, and a voltage of the transmission envelope signal, respectively.
  • G.Vcont and Vdeta are a gain of the error amplifier, a voltage of the distortion-free reference envelope signal, and a voltage of the transmission envelope signal, respectively.
  • Vdeta is close to Vcont, the higher the precision of linearity compensation is.
  • This appliance does not gives a superior precision of lineality because of the restriction of the gain of the error amplifier (G) in this appliance.
  • G error amplifier
  • a transmitter of the invention takes out a part of the transmission signal amplified by a power amplifier by a monitor circuit, compares a transmission envelope signal detected by an envelope detection circuit with a distortion-free standard envelope signal by an error detector, adds an error signal and a DC voltage in an adder, and feeds a sum signal to a gain control terminal to control the gain or attenuation of a gain variable circuit.
  • a variable gain control amplifier is controlled by positive DC voltage within some degrees.
  • the control voltage of the variable gain amplifier is an output voltage of an adder which adds a DC voltage supplied from outside and an output voltage of an error amplifier. So, the output voltage of the error amplifier can be made lower by a value of the DC voltage.
  • Vg G (Vcont-Vdeta) + Vd
  • G Vcont, Vdeta, Vd are a gain of the error amplifier, a voltage of the distortion-free standard envelope signal, a voltage of the transmission envelope signal and a DC voltage supplied from outside, respectively.
  • Vdeta Vcont - (Vg-Vd)/G0
  • Vdeta is closed to Vcont, the higher the precision of linearity compensation is.
  • Vcont-Vdeta When, the output voltage of the error amplifier, G (Vcont-Vdeta), is added with the DC voltage supplied from outside by the adder, the second term of right hand, (Vg-Vd)/G, can be lower by Vd/G compared with the case of absence of the DC voltage adder. Accordingly, the difference Vdeta and Vcont can be smaller than a conventional case.
  • the feedback-loop circuit described above provide an advantage in terms of the linear correction, and distortion-free transmission output will be achieved.
  • a transmitter in a preferred constitution comprises a gain variable circuit for amplifying or attenuating a modulation carrier signal, and having its gain or attenuation being controlled by a control signal supplied to its gain control terminal, a power amplifier for amplifying an output signal of the gain variable circuit to obtain a transmission signal, a transmission monitor circuit for taking out a part of the transmission signal from the power amplifier as a monitor signal, an envelope detector for detecting an envelope of the monitor signal to obtain a transmission envelope signal, a standard envelope generator for generating a distortion-free standard envelope signal, an error detector for comparing the standard envelope signal and the transmission envelope signal and generating an error signal by amplifying an error of the two signals, and an adder for adding a DC voltage supplied from outside and the error signal to generate a control signal, this control signal being fed to the gain control terminal of the gain variable circuit, thereby controlling the gain or attenuation of the gain variable circuit.
  • the detector comprises of a variable high frequency attenuator capable of attenuating a high frequency signal and having its attenuation quantity varied by an external control signal, a diode detector comprising a diode and a capacitor, and a variable load circuit for varying a load resistance value by an external control signal.
  • a variable high frequency attenuator capable of attenuating a high frequency signal and having its attenuation quantity varied by an external control signal
  • a diode detector comprising a diode and a capacitor
  • a variable load circuit for varying a load resistance value by an external control signal.
  • Fig. 1 is a block diagram of a transmitter in an embodiment of the invention.
  • Fig. 2 is an output waveform spectrum characteristic diagram in the transmitter in Fig. 1, in which Fig. 2(a) is an output waveform spectrum characteristic diagram obtained by applying 0 (V) to a DC voltage application terminal 10 in Fig. 1, and Fig. 2 (b) is an output waveform spectrum characteristic diagram obtained by applying 1.5 (V) to the DC voltage application terminal 10.
  • Fig. 3 is a block diagram of a transmitter in other embodiment than in Fig. 1 of the invention.
  • Fig. 4 is a timing chart of the transmitter in Fig. 3.
  • Fig. 5 is a constitution example of a diode detector and a variable load circuit in an envelope detector, and a detection characteristic compensator of the invention.
  • Fig. 6 is a diagram showing the input and output characteristics of the envelope detector comprising a variable high frequency attenuator capable of attenuating a high frequency signal and varying the attenuation quantity by an external control signal, a diode detector possessing a diode bias terminal, and a variable load circuit capable of varying the load resistance value by an external control.
  • signal in which the axis of abscissas denotes the transmission monitor circuit monitor output which is the input of the envelope detector, and the axis of ordinates represents the output of the envelope detector.
  • Fig. 1 shows a block diagram of a transmitter in an embodiment of the invention.
  • numeral 1 is a modulation carrier signal input terminal
  • 2 is a variable gain amplifier possessing a gain control terminal 11, capable of amplifying or attenuating a modulation carrier signal, and varying the gain or attenuation of this circuit by a control signal supplied to the gain control terminal 11
  • 3 is a power amplifier for amplifying the output signal of variable gain amplifier and obtaining a transmission signal
  • 4 is a monitor circuit for taking out a part of the transmission signal from the power amplifier as a monitor signal
  • 5 is a transmission signal output terminal
  • 6 is an envelope detector connected to the transmission monitor circuit 4 for detecting the envelope of the monitor signal and delivering a transmission envelope signal (Vdeta)
  • 7 is a standard envelope signal generator for delivering a standard envelope signal (Vcont)
  • 8 is an error detector connected between the envelope detector 6 and the standard envelope signal generator 7 for comparing the transmission envelope signal (Vdeta) and standard envelope signal (Vcont), and generating an error signal by amplifying the error of the two signals
  • the modulation carrier signal entered from the modulation carrier signal input terminal 1 is amplified or attenuated by the the variable gain amplifier 2, and further amplified by the power amplifier 3, and a part of the transmission signal is taken out as a monitor signal by the monitor circuit 4.
  • the monitor signal is detected of its envelope by the envelope detector 6, and the transmission envelope signal (Vdeta) is produced.
  • This transmission envelope signal (Vdeta) is fed into the error amplifier 8 together with the standard envelope signal (Vcont) generated in the standard envelope signal generator 7.
  • the error voltage of the transmission envelope signal (Vdeta) and the standard envelope signal (Vcont) is detected and amplified by the error amplifier 8 to be produced as an error signal.
  • the error signal voltage and DC voltage (VD) applied from the DC voltage application terminal 10 are summed up in the adder 9, and a control signal is produced, which controls the gain or attenuation of the variable gain amplifier 2.
  • VD DC voltage
  • the transmission output is controlled by the standard envelope signal.
  • Fig. 3 and Fig. 4 show a block diagram and a timing chart of a transmitter in other embodiment of the invention, respectively.
  • numeral 1 is a modulation carrier signal input terminal
  • 12 is a second variable gain amplifier possessing a gain control terminal 13 capable of amplifying or attenuating the modulation carrier signal, and varying the gain or attenuation of this circuit by a control signal entered in the gain control terminal
  • 2 is a first variable gain amplifier possessing a gain control terminal 11 capable of amplifying or attenuating the output signal of the second variable gain amplifier, and varying the gain or attenuation of this circuit by a control signal entered in the gain control terminal
  • 3 is a power amplifier possessing a supply voltage control terminal 31 for receiving the output signal of the first variable gain amplifier, and amplifying this input signal to obtain a transmission signal
  • 4 is a transmission monitor circuit for taking out a part of the transmission signal from the power amplifier as a monitor signal
  • 5 is a transmission signal output terminal
  • 6 is an envelope detector connected to the transmission monitor circuit 4 for detecting the envelope of the monitor signal and producing a transmission envelope signal (Vdeta)
  • 7 is a
  • the envelope detector 6 is composed of a variable attenuator 61 possessing a variable high frequency attenuator control terminal 611, capable of attenuating the high frequency signal, and varying the attenuation quantity by applying an external control signal to the high frequency attenuator control terminal 611, a high frequency amplifier 62 capable of amplifying a high frequency signal, a diode detector 63 composed of diode and capacitor, and possessing a diode bias terminal 631 for applying a bias voltage to the diode, and a variable load circuit 64 possessing variable load circuit control terminals 641, 642, capable of varying the load resistance value by applying an external control signal to these terminals.
  • the standard envelope generator 7 is composed of a distortion-free envelope signal generator 71 for generating a distortion-free envelope signal (Venv), a first ramping signal generator 72 for generating a ramping up-down signal (Vrampa) for burst control of the distortion-free envelope signal, a multiplier 73 for multiplying the distortion-free envelope signal and burst control signal, and a detector compensation circuit 74 possessing resistance load control terminals 741, 742, for receiving the multiplier output signal, compensating the nonlinearity of the detector, and producing the detection characteristic compensation envelope signal, and the output of the detector compensation circuit 74 is delivered as the standard envelope signal (Vcont).
  • Venv distortion-free envelope signal
  • Vrampa ramping up-down signal
  • the time t1-t2 is the transmission signal rise time
  • the time t2-t3 is the modulation data transmission time
  • the time t3-t4 is the transmission signal fall time.
  • the modulation carrier signal is a modulated signal
  • the standard envelope generator 7 produces a distortion-free standard envelope signal compensating the characteristic of the envelope detector 6.
  • the feedback loop is controlled by this distortion-free standard envelope signal, and a distortion-free transmission signal is generated consequently.
  • the envelope detector 6 is composed of the variable high frequency attenuator 61 for varying the attenuation quantity by external control signal, the high frequency amplifier 62 for amplifying the high frequency signal, diode detector 63, and variable load circuit 64 for varying the load resistance value by external control signal, using the control voltage applied to the variable high frequency attenuator control terminal 611, and variable load circuit control terminals 641, 642, by varying the attenuation quantity of the variable high frequency attenuator 61 and load value of variable load circuit, if the transmission signal output is varied and the transmission monitor circuit monitor output voltage changes to a certain degree, the detection voltage in a certain specific range can be delivered.
  • the linearity of the input and output characteristic of the diode detector 63 can be enhanced, and the effect of the linearity compensation for compensating the distortion of the power amplifier 3 may be improved.
  • Fig. 5 shows a structural example of diode detector 63 and variable load circuit in the envelope detector 6, and the detector compensation circuit 74, and Fig. 6 shows the input and output characteristic of the envelope detector.
  • numeral 63 is a diode detector
  • 64 is a variable load circuit
  • 6004 is a detector diode
  • 6003 is a capacitor for bypassing the modulation carrier signal
  • 6005 is a bias coil
  • 6006, 6007, 6012, 6017 are high frequency grounding capacitors
  • 6008, 6009, 6010, 6013, 6014, 6015, 6018, 6019, 7004, 7005, 7006, 7009, 7010, 7011, 7014, 7015 are fixed resistors
  • 6011, 6016, 7007, 7012 are transistors for variable load resistance on/off control
  • 631 is a diode detector bias input terminal
  • 641, 642 are variable load circuit control terminals
  • 7002 is a detector characteristic compensating diode
  • 7001, 7003, 7008, 7013 are DC voltage stabilizing capacitors
  • 741, 742 are load control terminals.
  • the diode 7002 of the detector compensation circuit 74 is same as the detector diode 6004 used in the diode detector 63 of the envelope detector 6, and the diodes matched in characteristic for the both are used.
  • a modulation carrier signal is entered in the diode detector 63, this signal is detected, and a detection current proportional to the electric power of the input modulation carrier signal is generated.
  • the transistors 6011, 6016 are in non-conductive state, the detection current generates a detection voltage according to the current flowing into the variable resistance load circuit 64 and the resistance of the fixed resistors 6008, 6009. By passing a current into the variable resistor control terminal 641, the transistor 6011 is set in conductive state.
  • the transistor 6016 By not passing a current into the variable resistor control terminal 642, the transistor 6016 is set in the non-conductive state, a detection voltage depending on the current flowing into the variable resistance load circuit 64 and the resistances of the fixed resistors 6008, 6009, 6010 is generated. Similarly, by passing a current into the variable resistor control terminal 642 to conduct the transistor 6016, and by not passing a current into the variable resistor control terminal 641 to set the transistor 6011 in non-conductive state, a detection voltage conforming to the current flowing into the variable resistor load circuit 64 and the resistance of fixed resistors 6008, 6009, 6015 is generated.
  • the transistors 6011, 6016 are set in conductive state by passing a current into the variable resistor control terminals 641, 642, a detection voltage conforming to the current flowing into the variable resistor load circuit 64 and the resistance of the fixed resistors 6008, 6009, 6010, 6015 is generated. That is, by turning on or off the resistance on/off transistors 6011, 6016, the fixed resistance in the variable resistor load 64 is selected, and the detection voltage output may be varied freely, and therefore if the detector input voltage varies, the detection voltage is suppressed so as not to change largely.
  • the diode detector 63 has a diode bias terminal 631, and by applying a bias voltage to the diode bias terminal 631 from outside, a bias current flows into the detector diode 6004 of the diode detector 63. By passing this bias current, if the high frequency electric power fed in the diode detector is small, a large detection voltage can be generated.
  • the detector compensation circuit using the voltage applied to the resistance load control terminals 741, 742, by turning on and off the resistance on/off transistors 7007, 7012, the output voltage of the detector compensation circuit may be freely varied.
  • the detector characteristic compensation circuit 74 After a distortion-free envelope signal passes through the detector characteristic compensation circuit 74, the same nonlinearity as in the detector diode 6004 is applied, and the standard envelope signal (Vcont) which is the output of the detector characteristic compensation circuit and the transmission envelope signal (Vdeta) which is the output of the envelope detector 6 are fed into the error detector 8, in which the mutual nonlinearities are canceled.
  • Vcont the standard envelope signal
  • Vdeta transmission envelope signal
  • the axis of abscissas denotes the output of the transmission monitor circuit
  • the axis of ordinates represents the detection voltage delivered to the envelope detector
  • numeral 661, 662, 663 are characteristics of the envelope detector, showing the large, medium and small resistance values of the variable load resistance when the attenuation quantity of the variable high frequency attenuator is small
  • 664, 665, 666 refer to the case when the attenuation quantity of the variable high frequency attenuator is large, showing large, medium and small resistances of the variable load resistance.
  • the transmission monitor output is ⁇ P1 if the resistance of the resistance load is medium, the transmission monitor output is ⁇ P2, and if the resistance of the resistance load is small, the transmission monitor output is ⁇ P3, and in the case the attenuation quantity of the variable high frequency attenuator is large, if the resistance of the variable load circuit is large, the transmission monitor output is ⁇ P4, if the resistance of the resistance load is medium, the transmission monitor output is ⁇ P5, and if the resistance of the resistance load is small, the transmission monitor output is ⁇ P6, and therefore as the comprehensive detection characteristic, it is known that the transmission monitor output range ⁇ P7 is extended. Besides, by applying a bias voltage to the detector diode, the individual output voltages are found to maintain the linearity if the transmission monitor output is small.

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  • Physics & Mathematics (AREA)
  • Nonlinear Science (AREA)
  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Transmitters (AREA)
  • Monitoring And Testing Of Transmission In General (AREA)
  • Mobile Radio Communication Systems (AREA)
EP92306557A 1991-07-19 1992-07-17 Transmetteur à circuits de correction de non-linéarité Expired - Lifetime EP0524008B1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
JP3179486A JP2776071B2 (ja) 1991-07-19 1991-07-19 送信出力包絡線検波回路および線形送信回路
JP179486/91 1991-07-19

Publications (2)

Publication Number Publication Date
EP0524008A1 true EP0524008A1 (fr) 1993-01-20
EP0524008B1 EP0524008B1 (fr) 1997-01-22

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EP92306557A Expired - Lifetime EP0524008B1 (fr) 1991-07-19 1992-07-17 Transmetteur à circuits de correction de non-linéarité

Country Status (5)

Country Link
US (1) US5319804A (fr)
EP (1) EP0524008B1 (fr)
JP (1) JP2776071B2 (fr)
CA (1) CA2074124C (fr)
DE (1) DE69216931T2 (fr)

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EP0635936A2 (fr) * 1993-07-24 1995-01-25 Philips Patentverwaltung GmbH Système de communication utilisant des signaux selon le système de multiplexage par répartition dans le temps
EP0654898A2 (fr) * 1993-11-19 1995-05-24 Matsushita Communication Industrial Co., Ltd. Circuit de transmission
DE19506051A1 (de) * 1995-02-22 1996-09-05 Mikom Gmbh Schaltungsanordnung zur Auswertung von Intermodulationsprodukten
EP0784379A1 (fr) * 1996-01-12 1997-07-16 Fujitsu Limited Circuit de compensation non-linéaire
GB2316560A (en) * 1996-08-14 1998-02-25 Motorola Ltd Improving the linearity of a transmitter amplifier using a pilot tone and feedback
GB2332312A (en) * 1997-12-15 1999-06-16 Matsushita Electric Ind Co Ltd Open and closed loop output power control in a transmitter with modification of the feedback loop
EP0982849A1 (fr) * 1998-08-24 2000-03-01 Nec Corporation Générateur de prédistorsion
WO2001097372A2 (fr) * 2000-06-14 2001-12-20 Infineon Technologies Ag Circuit et procede de demodulation
WO2002054580A2 (fr) * 2001-01-03 2002-07-11 Siemens Aktiengesellschaft Procede et circuit pour reguler la puissance de sortie d'un amplificateur a haute frequence pour produire un signal haute frequence a enveloppante variable
US6602652B2 (en) 1998-09-15 2003-08-05 Shipley Company, L.L.C. Antireflective coating compositions and exposure methods under 200 nm
KR100458998B1 (ko) * 1995-12-29 2005-02-28 퀄컴 인코포레이티드 비선형장치에대한대역외보상
WO2006066628A1 (fr) * 2004-12-23 2006-06-29 Freescale Semiconductor, Inc Systeme de reglage de puissance pour une unite de communication sans fil
US7991367B2 (en) 2004-12-23 2011-08-02 Freescale Semiconductor, Inc. Wireless communication unit and power control system thereof

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US5673001A (en) * 1995-06-07 1997-09-30 Motorola, Inc. Method and apparatus for amplifying a signal
US5995541A (en) * 1995-10-13 1999-11-30 Philips Electronics North America Corporation Method and apparatus for self-calibration and testing of ZPSK transmitter/receiver IC's
JPH09205333A (ja) * 1996-01-24 1997-08-05 Sony Corp 電力増幅回路
US6091942A (en) * 1996-12-02 2000-07-18 Motorola, Inc. Self gain aligning circuit and method
DE19911437A1 (de) * 1999-03-04 2000-09-07 Deutsche Telekom Ag Verfahren und Anordnung für digitale Übertragung mit amplitudenmodulierten Sendern mit Modulationstransformator
US6717980B1 (en) * 1999-05-24 2004-04-06 Koninklijke Philips Electronics N.V. Reduction of transmitter induced cross modulation in a receiver
US6670849B1 (en) * 2000-08-30 2003-12-30 Skyworks Solutions, Inc. System for closed loop power control using a linear or a non-linear power amplifier
US6677823B2 (en) 2001-02-28 2004-01-13 Andrew Corporation Gain compensation circuit using a variable offset voltage
US6759902B2 (en) * 2002-03-25 2004-07-06 Andrew Corporation Single-detector automatic gain control circuit
JP4185527B2 (ja) * 2003-02-14 2008-11-26 アナログ デバイスズ インコーポレイテッド 対数ｒｍｓ／ｄｃコンバータにおける伝達関数リプルを低減するシステム及び方法
US8019292B2 (en) * 2007-07-11 2011-09-13 Axiom Microdevices, Inc. Power amplifier amplitude modulator system and method
JP5744712B2 (ja) 2011-12-15 2015-07-08 サムソン エレクトロ−メカニックス カンパニーリミテッド． 電力検波回路
DE112018003553T5 (de) * 2017-07-11 2020-03-26 Mitsubishi Electric Corporation Ausgangsleistungssteuereinrichtung

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EP0369135A2 (fr) * 1988-11-17 1990-05-23 Motorola, Inc. Amplificateur de puissance pour signaux à radiofréquence
EP0446073A1 (fr) * 1990-03-09 1991-09-11 Nokia Mobile Phones Ltd. Procédé pour améliorer la précision de régulation de puissance dans un radio-téléphone

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Cited By (25)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0635936A2 (fr) * 1993-07-24 1995-01-25 Philips Patentverwaltung GmbH Système de communication utilisant des signaux selon le système de multiplexage par répartition dans le temps
EP0635936A3 (fr) * 1993-07-24 1995-08-23 Philips Patentverwaltung Système de communication utilisant des signaux selon le système de multiplexage par répartition dans le temps.
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Also Published As

Publication number Publication date
JP2776071B2 (ja) 1998-07-16
US5319804A (en) 1994-06-07
CA2074124C (fr) 2000-09-26
JPH0529967A (ja) 1993-02-05
CA2074124A1 (fr) 1993-01-20
DE69216931T2 (de) 1997-08-07
DE69216931D1 (de) 1997-03-06
EP0524008B1 (fr) 1997-01-22

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