EP0064799A1 - Miniaturisiertes Zweifachmodus-Resonator-Filter dessen Hohlräume dielektrische Elemente enthalten - Google Patents

Miniaturisiertes Zweifachmodus-Resonator-Filter dessen Hohlräume dielektrische Elemente enthalten Download PDF

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Publication number
EP0064799A1
EP0064799A1 EP82300831A EP82300831A EP0064799A1 EP 0064799 A1 EP0064799 A1 EP 0064799A1 EP 82300831 A EP82300831 A EP 82300831A EP 82300831 A EP82300831 A EP 82300831A EP 0064799 A1 EP0064799 A1 EP 0064799A1
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EP
European Patent Office
Prior art keywords
resonator
cavity
axis
filter according
axes
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP82300831A
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English (en)
French (fr)
Inventor
Slawomir Jerzy Fiedziuszko
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Space Systems Loral LLC
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Ford Aerospace and Communications Corp
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Filing date
Publication date
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Publication of EP0064799A1 publication Critical patent/EP0064799A1/de
Withdrawn legal-status Critical Current

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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P7/00—Resonators of the waveguide type
    • H01P7/10—Dielectric resonators
    • H01P7/105—Multimode resonators
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/20—Frequency-selective devices, e.g. filters
    • H01P1/207—Hollow waveguide filters
    • H01P1/208—Cascaded cavities; Cascaded resonators inside a hollow waveguide structure
    • H01P1/2084—Cascaded cavities; Cascaded resonators inside a hollow waveguide structure with dielectric resonators
    • H01P1/2086—Cascaded cavities; Cascaded resonators inside a hollow waveguide structure with dielectric resonators multimode

Definitions

  • the present invention relates to a microwave filter having particular application in transmitters and receivers designed to meet difficult requirements of minimum size, minimum weight, and tolerance of extreme environmental conditions.
  • Such filters are thus suited for use in mobile, airborne, or satellite communication systems in which the requirement exists to sharply define a number of relatively narrow frequency bands or channels within a relatively broader portion of the frequency spectrum.
  • filters to be described as embodiments of the present invention are especially useful in bandpass configurations which define the many adjacent channels utilized in satellite communication stations for both military and civilian purposes.
  • Such satellite communication stations have come to be used for a variety of purposes such as meteorological data gathering, ground surveillance, various kinds of telecommunication, and the retransmission of commercial television entertainment prog.rams. Since the cost of placing a satellite in orbit is considerable, each satellite must serve as many communication purposes and cover as many frequency channels as possible. Consequently, the ability to realize complex and sophisticated filter functions in compact and lightweight filter units is a significant advance which permits the extension of frequency band coverage without an increase in size or weight. Moreover, these advances are possible without relaxing the stringent requirements which must be met by such communication systems, including the requirement to maintain stable performance over a wide range of temperature.
  • the rods may be grooved to vary their electrical length without changing their physical length.
  • U.S. Patent 4,027,256 issued May 31, 1977 to Samuel Dixon discloses a type of wide-band ferrite limiter in which a ferrite rod extends axially along the centre of a cylindrical dielectric structure and through the centres of a plurality of dielectric resonator discs which are spaced along the resonant structure.
  • the patent contains little of interest to the worker seeking to realize microwave filter functions in compact high performance filter units.
  • U.S. Patent 4,184,130 issued January 15, 1980 to Nishikawa et al discloses a filter design employing a single mode (TE o1 ⁇ ) in a resonator which is coupled to a coaxial line by means of a short section of that line which has been made leaky by cutting apertures in the outer conductor.
  • TE o1 ⁇ single mode
  • the Williams et al patent discusses dual mode filters utilizing the conventional cavity resonators, while the British patent utilizes evanescent modes.
  • none of this prior art relating to unfilled cavity resonators contains any suggestion to significantly reduce the volume of the resonant structure by employing a resonator element of high dielectric constant as the principal component of the resonator, while enclosing this element within a reduced-dimension cavity which would itself be below cutoff at the frequencies of interest were it not for the included resonator element.
  • An object of the present invention is the provision of a microwave filter having reduced dimensions and weight as compared to prior art filters of comparable performance.
  • a further object of the present invention is the provision of a microwave filter which can readily realize complex filter functions involving several or many poles, or cross-couplings between poles.
  • the present invention provides a miniaturized microwave filter comprising in combination:
  • the filter preferably comprises a plurality of these compact filter units which utilize composite resonators operating simultaneously in each of two orthogonal resonant modes.
  • Each of these orthogonal resonant modes is tunable independently of the other, such that each can be used to realize a separate pole of a filter function.
  • the composite resonators themselves comprise resonator elements made of a high dielectric constants. solid material and may comprise short cylindrical sections of a ceramic material, together with a surrounding cavity resonator which is dimensioned small enough in comparison to the wavelengths involved that it would be well below cutoff but for the high dielectric constant resonator element within the cavity.
  • Capacitive probes or inductive irises may be used to provide coupling between several such composite resonators, and also to provide input and output coupling for the entire filter unit formed of these composite resonators.
  • these coupling devices By suitably positioning these coupling devices with respect to the two orthogonal resonant modes, it is possible to achieve cross- coupling between any desired resonant modes, such that filter functions requiring such couplings can easily be realized.
  • Independent tuning of the orthogonal resonant modes may be achieved by the use of a pair of tuning screws projecting inwardly from the cavity wall along axes which are orthogonal to one another. Microwave resonance along either of these axes may be coupled to excite resonance along the other by a mode coupling screw projecting into the cavity along an axis which is at 45° to the orthogonal mode axes.
  • Excellent temperature stability may be achieved by choosing a resonator material having a temperature coefficient of resonant frequency which is nearly zero, and by selecting materials for the resonant cavity and the tuning screws such that thermal expansion of one is very nearly compensated by thermal expansion of the other.
  • FIG. 1 a multi-cavity filter 1 embodying features of the present invention is shown.
  • Filter 1 is shown to comprise an input cavity 3, an output cavity 5, and one or more intermediate cavities 7, which are indicated more-or-less schematically in the broken region between cavities 3 and 5.
  • Cavities 3, 5 and 7 may all be electrically defined within a short length of cylindrical waveguide 9 by a series of spaced, transversely extending cavity endwalls 11a, b, c, and d.
  • These endwalls and waveguide 9 may be made of invar or graphite-fiber-reinforced plastic (GFRP) or of any other known material from which waveguide hardware is commonly made.
  • GFRP graphite-fiber-reinforced plastic
  • waveguide 9 and endwalls lla-d may be surface plated with a highly conductive material such as silver, which may be applied by sputtering onto the surfaces thereof. Endwalls lla-d may be joined to the interior wall of waveguide 9 by any known brazing or soldering technique, or by other known bonding techniques as appropriate to the materials concerned.
  • An input coupling device in the form of a probe assembly 13 is used to couple microwave energy from an external source (not shown) into input cavity 3.
  • probe assembly 13 includes a coaxial input connector 15, an insulative mounting block 17, and a capacitive probe 19.
  • Microwave energy coupled to probe 19 is radiated therefrom into input cavity 3, where microwave resonance is excited in the hybrid HE 111 mode.
  • microwave energy is further coupled into intermediate cavities 7 by a first iris 21 of cruciform shape, and from intermediate cavities 7 into output cavity 5 by a second iris 23,. also of cruciform shape.
  • energy is coupled from output cavity_5 into a waveguide system (not shown) by an output iris 25 of simple slot configuration.
  • a dielectric resonator element 27 made of a material possessing a high dielectric constant, a high Q, and a low temperature coefficient of resonant frequency.
  • Resonator element 27 is cylindrical in form as shown, such that together with cylindrical cavities 3, 5, and 7, composite resonators of axially symmetric shape are formed.
  • Resonator elements 27 may be made of a variety of materials such as rutile, barium tetratitanate (BaTi 4 O 9 ), related ceramic compounds such as the Ba 2 TinO 20 compound which was developed by Bell Laboratories, or a series of barium zirconate ceramic compounds which are available from Murata Mfg. Co. under the tradename Resomics.
  • the composite resonators formed by the combination of cavity and resonator element can also possess a high Q and a low temperature coefficient of resonant frequency, while the high dielectric constant of the resonator element concentrates the electromagnetic field of resonant energy within the dielectric element, thus significantly reducing the physical size of the composite resonator as compared to "empty" cavity resonators designed for the same resonant frequency.
  • each cylindrical resonator element together with the cylindrical cavity in which it is disposed forms a composite resonator having axial symmetry
  • each of these composite resonators is provided with means to tune it to resonance along each of a pair of orthogonal axes.
  • a first tuning screw 29 projects into input cavity 3 along a first axis which intersects the axis of cavity 3 and resonator element 27 at substantially a 90° angle thereto.
  • a second tuning screw 31 similarly projects into cavity 3 along a second axis which is rotationally displaced from the first axis by 90°.
  • Tuning screws.29 and 31 serve to tune cavity 3 to resonance in each of two orthogonal HE 111 resonant modes along the first and second axes respectively. Since the amount of projection of screws 29 and 31 is independently adjustable, each of the two orthogonal modes can be separately tuned to a precisely selected resonant frequency, such that input cavity 3 can provide a realization of two of the poles of a complex filter function.
  • a third tuning screw or mode coupling screw 33 is provided extending into cavity 3 along a third axis which is substantially midway between the first two axes or at an angle of 45° thereto. Screw 33 serves to perturb the electromagnetic field of resonant energy within the cavity such that resonance along either the first or second axis is coupled to excite resonance along the other as well. Moreover, the degree of such coupling is variable by varying the amount by which screw 33 projects into cavity 3.
  • waveguide 9 may be formed of a variety of known materials.
  • One particularly satisfactory material is thin (0.3 to 1.0mm) Invar, which can be used to form the cavity resonators and endwalls lla-d.
  • brazing may be carried out using a "NiOro" brazing alloy consisting of 18% nickel and 82% gold.
  • the material used to form the three screws 29, 31, and 33 can be selected in consideration of the temperature coefficient of resonant frequency of resonator element 27 and the temperature coefficient of expansion of the material used for construction of the cavities so that the temperature coefficient of resonant frequency of the composite resonator is as near zero as possible.
  • Invar is used for -the cavity structure, in combination with a resonator element having a coefficient of 0.5 ppm/°C, brass or Invar can be successfully used as materials for the tuning and mode coupling screws.
  • other materials such as aluminum may be found useful in securing a near-zero temperature coefficient for the composite resonator.
  • resonator elements 27 can be successfully mounted in cavities 3, 5, and 7 by a variety of insulative mounting means which generally take the form of pads or short columns of low-loss insulator material such as polystyrene or PTFE. However, the best performance has been obtained by the use of mountings made of a low-loss polystyrene foam.
  • Each of cavities 3, 5, and 7 is similarly equipped with first and second tuning screws extending along orthogonal axes and a mode coupling screw extending along a third axis which is at substantially a 45° angle to the first and second axes.
  • These screws have not been shown for the intermediate cavity 7, while they have been illustrated as 29', 31', and 33' for output cavity 5, where the primed numbers correspond to like-numbered parts in cavity 3.
  • screws 29', 31', and 33' have been illustrated in an alternative orientation with respect to the central axis of the cavities, it is to be understood that their function is not altered thereby, and the orthogonal first and second axes remain in the same position as in the case of input cavity 3.
  • each cavity is equipped with mcans to couple microwave energy into and out of the cavity.
  • these means all comprise one or another variety of iris in the embodiment of Fig. 1.
  • the coupling means could be entirely capacitive probes, or inductive irises, or any combination of the two.
  • irises 21 and 23 have been illustrated as cruciform in shape, such that they function as orthogonal slot irises to couple to each of the two orthogonal modes in the respective cavities, other forms of iris.could be used, depending on the nature of the inter- cavity coupling required by the filter function being realized.
  • Fig. 2 is shown a simple theoretical model useful in calculating the resonant frequency of each composite resonator, such that it is possible to accurately design each of the composite resonators needed to realize a complex filter function.
  • the composite resonator is modeled as a dielectric cylinder 35 having a radius R and being made of .a material having a dielectric constant ⁇ , coaxially surrounded by a cylindrical conductive wall 37 representing the inner surface of a circular waveguide of radius R s .
  • the dielectric-filled region in F ig. 2, marked "1" in the drawing will be denoted by the subscript 1 following the respective parameters.
  • the region marked "2" in the drawing between radius R and radius R s will be assumed to be evacuated and to have a dielectric constant equivalent to free-space permittivity ⁇ 0 .
  • the subscript 2 will be used.
  • Fig.3 a second theoretical model useful in analyzing the axial distribution of electromagnetic field for the purpose of refining the calculations of resonant frequency is illustrated.
  • a detailed analysis of the resonances of such a structure has been published by E. 0. Amman and R. J. Morris in the paper "Tunable Dielectric-Loaded Microwave Cavities Capable of High Q and High Filling Factor", IEEE Trans. MTT-11, pp. 528-542, November 1963.
  • equations [1] and [2] form a set of coupled equations from which the values of f o and Yi can be determined, thus providing values of the resonant frequencies.
  • data was measured for several samples of high- ⁇ , low-loss resonators. This data, showing especially a high degree of c or- relation between theoretically predicted and measured resonant frequency, is presented below:
  • FIG. 4 the actual passband performance of an 8-pole, quasi-elliptic bandpass filter built according to the teachings of the present invention is illustrated.
  • Fig. 4 is actually representative of the performance of a filter constructed in accordance with the embodiment of Fig. 1 of this application, using a total of only four cavities, (such that intermediate cavities 7 are two in number).
  • a rejection curve 39 in Fig. 4 shows the frequency response of the filter on a highly magnified frequency scale which is centered on the narrow passband region at approximately 4.2 GHz.
  • curve 39 illustrates, the passband of this filter is bounded by steep skirts 41, providing almost an ideal bandpass characteristic.
  • An insertion loss curve 43 in Fig. 4 shows the passband region of curve 39 on a 20-times magnified amplitude scale to reveal the insertion loss of the filter within the passband region.
  • the insertion loss for this filter is less than 1.0 dB over most of the passband, again indicating a very high level of performance.
  • Fig. 4 shows reflected power in the form of a return loss curve 45, which is similar to a curve of VSWR for the filter, except that the amplitude is plotted on a logarithmic (dB) scale.
  • Curve 45 reveals quite clearly the presence and frequency-spacing of the 8 poles of this filter by means of eight corresponding peaks 47 on the trace of curve 45. Curve 45 thus serves as a check of the accuracy of the realization of the filter function upon which this filter was based.

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EP82300831A 1981-05-11 1982-02-18 Miniaturisiertes Zweifachmodus-Resonator-Filter dessen Hohlräume dielektrische Elemente enthalten Withdrawn EP0064799A1 (de)

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US26258081A 1981-05-11 1981-05-11
US262580 1981-05-11

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Cited By (25)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0188367A2 (de) * 1985-01-14 1986-07-23 Com Dev Ltd. Dreifachmodus mit dielektrischen Resonatoren belastete Bandpassfilter
DE3706965A1 (de) * 1986-03-04 1987-09-10 Murata Manufacturing Co Doppel-modenfilter
GB2242319A (en) * 1990-03-12 1991-09-25 Marconi Gec Ltd Waveguide filter
GB2276039A (en) * 1993-03-12 1994-09-14 Matra Marconi Space Uk Ltd Support arrangement for a dielectric element within a cavity, for a dieletric resonator filter
GB2276040A (en) * 1993-03-12 1994-09-14 Matra Marconi Space Uk Ltd Dielectric resonator demultiplexer
EP0742603A1 (de) * 1995-05-12 1996-11-13 Alcatel N.V. Dielektrischer Resonator für Mikrowellenfilter und Filter damit
EP0691702A3 (de) * 1994-07-07 1997-03-26 Com Dev Ltd Temperaturkompensiertes Multimodefilter und Verfahren zu seiner Herstellung und Kompensierung
WO1998025321A1 (en) * 1996-12-06 1998-06-11 Filtronic Plc Microwave resonator
US5781080A (en) * 1993-10-15 1998-07-14 Murata Manufacturing Co., Ltd. Dielectric duplexer
US5796318A (en) * 1994-01-24 1998-08-18 Murata Manufacturing Co., Ltd. Dual TM-mode dielectric resonator apparatus equipped with window for electromagnetic field coupling, and band-pass filter apparatus equipped with the dielectric resonator apparatus
EP1014473A1 (de) * 1997-09-04 2000-06-28 Murata Manufacturing Co., Ltd. Multimodale dielektrische resonanzvorrichtungen, dielektrisches filter,zusammengestelltes deeltkrisches filter, sythetisierer, verteiler und kommunikationsgerät
EP1014474A1 (de) * 1997-09-04 2000-06-28 Murata Manufacturing Co., Ltd. Multimodale dielektrische resonanzvorrichtung, dielktrisches filter, synthesierer, verteiler und kommunikationsgerät
EP1041663A1 (de) * 1999-03-27 2000-10-04 Space Systems / Loral, Inc. Zweimoden-Hohlraumfilter mit dielektrischem Resonator und allgemeiner Filterkurve
WO2000079640A1 (de) * 1999-06-18 2000-12-28 Forschungszentrum Jülich GmbH Dielektrische resonatorkonfiguration für mikrowellen-mehrpolbandpassfilter
CN104995788A (zh) * 2013-02-21 2015-10-21 梅萨普莱克斯私人有限公司 多模腔体滤波器
CN104995786A (zh) * 2013-02-21 2015-10-21 梅萨普莱克斯私人有限公司 具有带有耦合段的孔布置的多模式滤波器
CN104995787A (zh) * 2013-02-21 2015-10-21 梅萨普莱克斯私人有限公司 多模腔体滤波器
CN105161814A (zh) * 2015-09-29 2015-12-16 江苏吴通通讯股份有限公司 双模介质腔体谐振器及滤波器
CN105789792A (zh) * 2016-03-30 2016-07-20 华南理工大学 一种单腔多模的金属圆柱腔滤波器
CN111029697A (zh) * 2019-12-31 2020-04-17 无锡惠虹电子有限公司 一种双模陶瓷介质滤波器
CN111403876A (zh) * 2020-04-27 2020-07-10 江苏贝孚德通讯科技股份有限公司 具有两种谐振腔的小型混合模滤波器
CN113410603A (zh) * 2021-06-16 2021-09-17 聪微科技(深圳)有限公司 一种微波滤波器的制造方法及微波滤波器
RU206936U1 (ru) * 2021-03-30 2021-10-01 Станислав Константинович Крылов СВЧ-фильтр с термостабилизацией
CN114039187A (zh) * 2021-12-03 2022-02-11 大富科技(安徽)股份有限公司 介质双模谐振器及滤波器
CN114824723A (zh) * 2022-05-11 2022-07-29 南通至晟微电子技术有限公司 一种水平极化双模介质谐振器

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US5179074A (en) * 1991-01-24 1993-01-12 Space Systems/Loral, Inc. Hybrid dielectric resonator/high temperature superconductor filter
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JPH07147504A (ja) * 1993-11-22 1995-06-06 Nippon Dengiyou Kosaku Kk 誘電体共振器より成る帯域通過ろ波器
JPH07212106A (ja) * 1994-01-13 1995-08-11 Nippon Dengiyou Kosaku Kk 分波器
JPH07221502A (ja) * 1994-01-28 1995-08-18 Nippon Dengiyou Kosaku Kk 二重モ−ド誘電体共振器より成る帯域通過ろ波器及び分波器

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ELECTRONICS LETTERS, Vol.16, no. 17, 14th August 1980, pages 646-647, Hitchin, Herts (GB); P.GUILLON et al.: "Dielectric resonator dual modes filter" *The whole document* *
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Cited By (42)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0188367A3 (en) * 1985-01-14 1988-07-06 Com Dev Ltd. Triple mode dielectric loaded bandpass filters
EP0188367A2 (de) * 1985-01-14 1986-07-23 Com Dev Ltd. Dreifachmodus mit dielektrischen Resonatoren belastete Bandpassfilter
DE3706965A1 (de) * 1986-03-04 1987-09-10 Murata Manufacturing Co Doppel-modenfilter
GB2188788A (en) * 1986-03-04 1987-10-07 Murata Manufacturing Co Double-mode filter
US4760361A (en) * 1986-03-04 1988-07-26 Murata Manufacturing Co., Ltd. Double-mode filter
GB2188788B (en) * 1986-03-04 1989-11-29 Murata Manufacturing Co Double-mode filter
GB2242319A (en) * 1990-03-12 1991-09-25 Marconi Gec Ltd Waveguide filter
GB2276039A (en) * 1993-03-12 1994-09-14 Matra Marconi Space Uk Ltd Support arrangement for a dielectric element within a cavity, for a dieletric resonator filter
GB2276040A (en) * 1993-03-12 1994-09-14 Matra Marconi Space Uk Ltd Dielectric resonator demultiplexer
US5493258A (en) * 1993-03-12 1996-02-20 Matra Marconi Space Uk Limited Dielectric resonator demultiplexer with MIC circulators located within the support structure
US5781080A (en) * 1993-10-15 1998-07-14 Murata Manufacturing Co., Ltd. Dielectric duplexer
US5796318A (en) * 1994-01-24 1998-08-18 Murata Manufacturing Co., Ltd. Dual TM-mode dielectric resonator apparatus equipped with window for electromagnetic field coupling, and band-pass filter apparatus equipped with the dielectric resonator apparatus
EP0691702A3 (de) * 1994-07-07 1997-03-26 Com Dev Ltd Temperaturkompensiertes Multimodefilter und Verfahren zu seiner Herstellung und Kompensierung
EP0742603A1 (de) * 1995-05-12 1996-11-13 Alcatel N.V. Dielektrischer Resonator für Mikrowellenfilter und Filter damit
FR2734084A1 (fr) * 1995-05-12 1996-11-15 Alcatel Espace Resonateur dielectrique pour filtre hyperfrequence, et filtre comportant un tel resonateur
US5880650A (en) * 1995-05-12 1999-03-09 Alcatel N.V. Dielectric resonator for a microwave filter, and a filter including such a resonator
US6359534B2 (en) 1996-12-06 2002-03-19 Filtronic Plc Microwave resonator
WO1998025321A1 (en) * 1996-12-06 1998-06-11 Filtronic Plc Microwave resonator
AU732191B2 (en) * 1996-12-06 2001-04-12 Filtronic Plc Microwave resonator
EP1014474A4 (de) * 1997-09-04 2002-01-02 Murata Manufacturing Co Multimodale dielektrische resonanzvorrichtung, dielktrisches filter, synthesierer, verteiler und kommunikationsgerät
EP1014474A1 (de) * 1997-09-04 2000-06-28 Murata Manufacturing Co., Ltd. Multimodale dielektrische resonanzvorrichtung, dielktrisches filter, synthesierer, verteiler und kommunikationsgerät
EP1014473A1 (de) * 1997-09-04 2000-06-28 Murata Manufacturing Co., Ltd. Multimodale dielektrische resonanzvorrichtungen, dielektrisches filter,zusammengestelltes deeltkrisches filter, sythetisierer, verteiler und kommunikationsgerät
EP1014473A4 (de) * 1997-09-04 2002-01-02 Murata Manufacturing Co Multimodale dielektrische resonanzvorrichtungen, dielektrisches filter,zusammengestelltes deeltkrisches filter, sythetisierer, verteiler und kommunikationsgerät
CN100392911C (zh) * 1997-09-04 2008-06-04 株式会社村田制作所 多模式介质谐振器装置、介质滤波器、复合介质滤波器、合成器、分配器和通信装置
US6496087B1 (en) 1997-09-04 2002-12-17 Murata Manufacturing Co., Ltd. Multi-mode dielectric resonance devices, dielectric filter, composite dielectric filter, synthesizer, distributor, and communication equipment
US6507254B1 (en) 1997-09-04 2003-01-14 Murata Manufacturing Co. Ltd Multimodal dielectric resonance device, dielectric filter, composite dielectric filter, synthesizer, distributor, and communication apparatus
EP1041663A1 (de) * 1999-03-27 2000-10-04 Space Systems / Loral, Inc. Zweimoden-Hohlraumfilter mit dielektrischem Resonator und allgemeiner Filterkurve
WO2000079640A1 (de) * 1999-06-18 2000-12-28 Forschungszentrum Jülich GmbH Dielektrische resonatorkonfiguration für mikrowellen-mehrpolbandpassfilter
CN104995788A (zh) * 2013-02-21 2015-10-21 梅萨普莱克斯私人有限公司 多模腔体滤波器
CN104995786A (zh) * 2013-02-21 2015-10-21 梅萨普莱克斯私人有限公司 具有带有耦合段的孔布置的多模式滤波器
CN104995787A (zh) * 2013-02-21 2015-10-21 梅萨普莱克斯私人有限公司 多模腔体滤波器
US10109907B2 (en) 2013-02-21 2018-10-23 Mesaplexx Pty Ltd. Multi-mode cavity filter
CN105161814A (zh) * 2015-09-29 2015-12-16 江苏吴通通讯股份有限公司 双模介质腔体谐振器及滤波器
CN105789792A (zh) * 2016-03-30 2016-07-20 华南理工大学 一种单腔多模的金属圆柱腔滤波器
CN111029697A (zh) * 2019-12-31 2020-04-17 无锡惠虹电子有限公司 一种双模陶瓷介质滤波器
CN111403876A (zh) * 2020-04-27 2020-07-10 江苏贝孚德通讯科技股份有限公司 具有两种谐振腔的小型混合模滤波器
RU206936U1 (ru) * 2021-03-30 2021-10-01 Станислав Константинович Крылов СВЧ-фильтр с термостабилизацией
CN113410603A (zh) * 2021-06-16 2021-09-17 聪微科技(深圳)有限公司 一种微波滤波器的制造方法及微波滤波器
CN113410603B (zh) * 2021-06-16 2022-08-02 聪微科技(深圳)有限公司 一种微波滤波器的制造方法及微波滤波器
CN114039187A (zh) * 2021-12-03 2022-02-11 大富科技(安徽)股份有限公司 介质双模谐振器及滤波器
CN114824723A (zh) * 2022-05-11 2022-07-29 南通至晟微电子技术有限公司 一种水平极化双模介质谐振器
CN114824723B (zh) * 2022-05-11 2023-12-22 南通至晟微电子技术有限公司 一种水平极化双模介质谐振器

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