EP0057485B1 - Mécanisme de commande pour un tube à rayons X à anode rotative - Google Patents

Mécanisme de commande pour un tube à rayons X à anode rotative Download PDF

Info

Publication number
EP0057485B1
EP0057485B1 EP82200101A EP82200101A EP0057485B1 EP 0057485 B1 EP0057485 B1 EP 0057485B1 EP 82200101 A EP82200101 A EP 82200101A EP 82200101 A EP82200101 A EP 82200101A EP 0057485 B1 EP0057485 B1 EP 0057485B1
Authority
EP
European Patent Office
Prior art keywords
frequency
current
digital
value
speed
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Expired
Application number
EP82200101A
Other languages
German (de)
English (en)
Other versions
EP0057485A2 (fr
EP0057485A3 (en
Inventor
Gerd Vogler
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Philips Intellectual Property and Standards GmbH
Koninklijke Philips NV
Original Assignee
Philips Patentverwaltung GmbH
Philips Gloeilampenfabrieken NV
Koninklijke Philips Electronics NV
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Philips Patentverwaltung GmbH, Philips Gloeilampenfabrieken NV, Koninklijke Philips Electronics NV filed Critical Philips Patentverwaltung GmbH
Publication of EP0057485A2 publication Critical patent/EP0057485A2/fr
Publication of EP0057485A3 publication Critical patent/EP0057485A3/de
Application granted granted Critical
Publication of EP0057485B1 publication Critical patent/EP0057485B1/fr
Expired legal-status Critical Current

Links

Images

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P23/00—Arrangements or methods for the control of AC motors characterised by a control method other than vector control
    • H02P23/08—Controlling based on slip frequency, e.g. adding slip frequency and speed proportional frequency

Definitions

  • the invention relates to a drive device according to the preamble of the main claim.
  • a drive device is essentially known from GB-A-2 034 938; however, the known device is without specifying a preferred area of application, i. H. not described in connection with the drive of a rotating anode X-ray tube.
  • the greatest possible drive torque is achieved when there is a phase shift of 45 ° between the rotor current and the rotor voltage.
  • the phase shift between the stator current and the stator voltage is measured instead and the frequency of the clock generator is regulated in dependence on load fluctuations so that there is a phase shift of 45 ° between the stator voltage and the stator current.
  • the desired phase shift of the same size between the rotor voltage and the rotor current only results if an asynchronous motor with a small air gap is used.
  • the rotor is namely inside the piston of the rotating anode X-ray tube and carries high voltage potential, while the stator is arranged outside the piston and carries almost earth potential, which requires a relatively large air gap between the rotor and stator.
  • a drive device for a rotating anode X-ray tube with an asynchronous motor is known, the stator windings of which are fed via an switching amplifier with an alternating current with a predeterminable frequency.
  • the switching amplifiers are part of an inverter that generates two square-wave voltages with a controlled frequency and a 1: 1 duty cycle to supply the single-phase asynchronous motor with main and auxiliary stator windings, which are staggered in time by a quarter period.
  • the frequency is increased in accordance with the tilting torque curve of the asynchronous motor.
  • a disadvantage of the known drive device is that the square-wave voltages generate harmonics in the current through the stator windings, which reduce the efficiency.
  • the amplitude of the alternating current through the stator windings cannot be controlled and depends on the respective frequency, because the impedance of the stator winding is frequency-dependent.
  • an electric vehicle drive is known from EP-A-122 267, which generates a three-phase voltage for an induction motor by means of a pulse width modulator.
  • the frequency of this three-phase voltage is equal to the speed of a tachometer generator measuring the speed of the vehicle, increased (in start-up mode) or reduced (in braking mode) by the slip speed.
  • a voltage control generator converts this frequency into a proportional voltage setpoint, which is compared with the actual voltage value at the output of the pulse duration modulator. The actual current value is also compared with a setpoint.
  • a priority circuit ensures that the smaller of the two control deviations is corrected.
  • the object of the present invention is to design a drive device of the type mentioned in the introduction such that largely sinusoidal alternating currents with predeterminable frequency and amplitude result in the stator windings.
  • the sinusoidal signals of the AC voltage generator are converted by the pulse width modulator into a square wave voltage with a fixed frequency and a duration dependent on the instantaneous value of the sinusoidal signal and amplified by the switching amplifier.
  • the output signal can be connected directly to the stator windings, because the carrier frequency of the pulse width modulator to generate the sinusoid must be significantly higher than the resulting drive frequency for the stator.
  • the inductive part of the stator resistance predominates and the current through the windings is proportional to the integral of the square-wave voltages - d. H. it is sinusoidal.
  • the current through the stator windings is by a current measuring element, for. B. a current transformer, measured and compared in a comparison circuit with a predetermined target value.
  • a current measuring element for. B. a current transformer, measured and compared in a comparison circuit with a predetermined target value.
  • the pulse duration is additionally varied in the sense of a regulation, so that the difference between the setpoint and actual value of the current through the stator windings tends to a minimum. If, for example, the current through a stator winding is too large, the control can, for. B. done in that the amplitude of the pulse width modulator fed sinusoidal AC voltage is reduced by the comparison circuit.
  • the AC voltage generators only have to be designed for a relatively small electrical output.
  • the frequency of the sinusoidal alternating current in the stator windings can be generated by changing the frequency of the sinusoidal voltage generated by the alternating voltage generator; AC voltage generators for sinusoidal AC voltages with a controllable frequency for relatively low output powers can be produced with relatively little effort.
  • the control loop changes the frequency of the si nus-shaped AC voltage by changing the clock frequency of the clock generator, in such a way that the frequency of the current in the stator windings is greater or smaller by the slip speed - depending on whether the speed setpoint exceeds or falls below the actual speed value by a predeterminable amount - as is the speed of the rotor, which has the consequence that the acceleration or deceleration of the rotor takes place with the highest torque. It is particularly advantageous that only two values have to be specified (the target speed and the slip speed), although the frequency of the current in the stator windings has to be varied continuously.
  • Fig. 1 denotes a modulo-32 counter, which counts the clock pulses of a clock generator 20 with an electronically controllable frequency and whose output signal, which has the same counter state after every 32 clock pulses, is fed in parallel to the address inputs of a read-only memory (PROM) 31 is stored in the memory locations of a sine function, the values of which are called up cyclically in accordance with the respective counter reading and converted into an analog signal with a temporally almost sinusoidal shape via a downstream multiplying digital-to-analog converter 41.
  • PROM read-only memory
  • the counter reading of the binary counter 10 controls, via a digital inverting circuit 30, a read-only memory 32 which can have the same structure as the read-only memory 31 and in which the values of a cosine function are stored, which by means of a further multiplying digital-to-analog converter 42 in an analog, temporally cosine-shaped signal are implemented so that the output voltages of the digital-to-analog converters are mutually offset by 90 °.
  • the digital inverter 30, which can be controlled via the dashed-line control line 33, either passes the counter reading of the counter 10 unchanged to the read-only memory 32 or adds (modulo 32) the value 16 to it, which calls up the cosine values which are offset by 180 °, so that the output voltage of the digital-to-analog converter 42 can be rotated through the control line 33 by 180 °.
  • a sine read-only memory can also be used if the value 8 is added to the counter reading before it is supplied to the address inputs of this memory.
  • the output signals u and U2 of the digital-to-analog converters 41 and 42 are each fed to a pulse width modulator 51 and 52, the modulation inputs of which are also supplied with a triangular voltage u o , the frequency (for example 20 kHz) of which is high compared to the highest frequency of the signals u 1 , U2 and their amplitude is always greater than the amplitude of the signals U 1 , U2 .
  • Pulse width modulator 51 is the rectangular and pulse width modulated voltage denoted by u 3 in FIG. 2b, the mean value of which is indicated by dashed lines in FIG. 2b and denoted by U4 .
  • the output voltages of the pulse width modulators 51 and 52 are supplied to switching amplifiers 61 and 62, whose - unsmoothed - output voltage has the same time profile as the output voltage of the preceding amplitude modulators.
  • the switching amplifiers can have the same structure as described in DE-AS 20 53 077.
  • Each switching amplifier consists of four controllable switching elements operated in a bridge circuit, of which two switching elements located in opposite branches are conductive and the other two are blocked and the control inputs of which are optionally coupled to the outputs of the pulse width modulators via a transformer (not shown) for potential isolation. Precautions must be taken to prevent all switching elements from being conductive at the same time.
  • Transistors in particular so-called power MOS FETs, or GTO thyristors are used.
  • the two stator windings 71 and 72 of a single-phase asynchronous motor are connected to the outputs of the two switching amplifiers 61 and 62, the schematically indicated rotor 13 of which is rigidly connected to the rotating anode of the X-ray tube (not shown in more detail).
  • the connection can be made using a smoothing filter; however, the stator windings can also be connected directly to the outputs of the switching amplifiers, because the impedances of the switching amplifiers at the switching frequencies are almost inductive, so that the current through the winding corresponds to the time integral of the modulated square-wave voltage.
  • the current flowing through the stator windings 71 and 72 is from a current measuring element 81 and 82, z. B.
  • a current transformer measured and fed to the input of a comparison circuit 91 and 92, respectively another input, a switchable setpoint for the current through the respective stator winding is supplied by means of a switch 14.
  • the comparison circuits 91 and 92 compare this nominal value with the peak value of the current through the stator windings (for this purpose the comparison devices 91, 92 can each contain a peak value rectifier) and each generate an output signal which corresponds to the difference between the two values.
  • These output signals are supplied as reference voltages to the multiplying digital-to-analog converters 41 and 42, so that their output signal corresponds to the product of the digital output signal of the read-only memory 31 and 32 and the analog output signal of the comparison circuit 91 and 92, respectively.
  • the polarity of the output signals of the comparator circuits 91 and 92 must be selected so that the current through the stator windings is regulated to the setpoint specified by the switch 14. This current control ensures that the current through the stator windings 71, 72 is independent of the frequency of the AC voltages at the outputs of the digital-to-analog converters 41 and 42 despite their frequency-dependent impedance.
  • the clock generator 20 with a controllable clock frequency can be, for example, a voltage-frequency converter with a linear relationship between the input voltage and the clock frequency.
  • a control device 15 which contains a comparator 16 which compares the target value u 5, the speed of rotation of the rotating anode, with the actual value u o .
  • the speed can be measured directly, as is known from US Pat. No. 3,214,589, and converted into the actual value signal U 6 , which is proportional to it.
  • an indirect measurement is also possible, as is the case, for.
  • the comparator 16 may include two threshold arrangements which cause the switch 17 to be closed when the setpoint u 5 of the speed is greater than the actual value u 6 by the threshold value and which cause the switch 18 to be closed when the setpoint u 5 is smaller than the actual value u 6 by the threshold value. If the amount of the difference between the target value and the actual value is smaller than the threshold value, the two switches 17, 18 are open.
  • the two switches 17, 18 are connected to a voltage source which supplies a DC voltage U7 proportional to the slip speed (the quotient of the DC voltage and the slip speed must have the same size as the quotient of the voltage u 6 and the actual one Speed value).
  • the slip speed is the difference between the frequency of the current in the stator windings and the speed at which the greatest possible torque is exerted on the rotor of an asynchronous motor. For a given rotor-stator configuration, it is essentially constant.
  • the value u 7 which is proportional to the slip speed, is added to the actual value u 6 in a superimposition circuit 19 when the switch 17 is closed, that is to say when the setpoint u 5 is higher than the voltage u 6 by the threshold value and it is dependent on the actual value u 6 subtracts when the switch 18 is closed, ie when the actual value u o is greater than the target value u 5 by the threshold value.
  • a signal appears at the output of the superimposition circuit 19 which is proportional to the sum U 6 + U 7 or the difference U 6 -U 7 and which is converted by the clock generator 20 into a clock frequency proportional thereto.
  • the clock frequency is therefore specified so that the frequency of the sinusoidal AC signals u l , u 2 is greater than the respective speed by the slip frequency , so that the transmitted torque has its greatest value and the rotor is accelerated or braked to the desired speed in the shortest possible time.
  • the difference between the speed and the frequency of the current is practically zero, so that no acceleration or deceleration torque can occur and the rotating anode continues to run at an almost constant speed.
  • Fig. 3 the time course of the speed or the voltage u 6 in solid lines and the time course of the frequency of the current in the stator windings is dashed, which is the time course of the voltage at the input of the clock generator 20 or the clock frequency for a typical X-ray examination corresponds.
  • the rotor is set to a predetermined first speed, e.g. B. 2700 rpm, accelerated.
  • a predetermined first speed e.g. B. 2700 rpm
  • the desired value u 5 corresponding to this speed is always considerably larger than the actual value u o , so that the comparator 16 closes the switch 17 and adds the value U7 proportional to the slip speed to the actual value u 6 , which has the consequence that that the frequency of the current in the stator windings by the slip speed is higher than the respective speed of the rotor, whereby this is accelerated to the desired speed in the shortest possible time.
  • u 5 u 6 and switch 17 is opened again.
  • the output voltage of the superimposition circuit 19 then corresponds to u e - or as explained above U 5 - and the rotor practically continues to run at the same frequency. Since the drive energy required for this (e.g. 40 W) is considerably less than the energy required for acceleration, which is of the order of kW, it is necessary to reduce the power loss in the stator windings by reducing the stator current. For this purpose, the stator current setpoint is switched from a high value to a substantially lower value by means of the switch 14. The switch 14 is controlled in a manner not shown by the control device 15 via the line 23. The frequency of the current in the stator windings practically corresponds to the speed. This operating state is given during the period t 2 .
  • the speed zero is specified as the setpoint, which results in a renewed closing of the switch 18 and a renewed switching of the switch 14, so that the output signal of the superposition circuit 19 again corresponds to the difference U 6 - U7 and Speed decreases.
  • the frequency in the stator windings also follows this decrease - but offset by the slip speed.
  • this frequency has reached a limit value which is preferably below the slip speed and which can just about be processed with reasonable effort, e.g. B. 10 Hz, from then on the input voltage of the clock generator 20 is held in a manner not shown in detail, so that the frequency of the current in the stator windings no longer changes.
  • the digital inverting circuit is switched over the control line 33, so that the cos oscillation at the output of the digital-to-analog converter 42 is replaced by a -cos oscillation.
  • the rotating field is reversed, which leads to further braking.
  • a reset pulse is given to the counter 10 so that the counter reading and thus also the output of the sine read-only memory 31 are set to zero and at the same time a correction signal is sent to the cosine read-only memory 32 given so that its binary output signal or the output signal of the digital-to-analog converter 42 also becomes zero.
  • the current in both stator windings is then zero, ie when the rotor 13 is at a standstill there is no longer an accelerating or decelerating field, so that the rotor 13 finally stops.
  • the drive device described is to be used to operate X-ray tubes whose asynchronous motor has a different rotor-stator configuration or whose anode disk has a different moment of inertia, a different slip speed or a different setpoint value for the current through the stator windings when accelerating is required (Braking) and continuing to be specified.
  • the control device 15 can be implemented with the aid of a microprocessor to which the actual speed value is supplied digitally and which automatically specifies the speed in response to the various commands (“fluoroscopy”, “recording”, etc.).
  • the counter 10 the digital inverting circuit 30 and the read-only memories 31 and 32 can also be implemented with the aid of this microprocessor.
  • a standard frequency generator can also be used as the clock generator 20, the frequency of which is significantly higher than the clock frequency and is followed by a frequency divider that can be controlled by the control device 15.

Claims (2)

1. Mécanisme de commande pour un tube à rayons X à anode tournante comportant un moteur asynchrone, dont les enroulements de stator (71, 72) alimentés au moyen d'un courant alternatif de fréquence pouvant être prédéfinie chacun par l'intermédiaire d'un amplificateur (61, 62) sont associés chacun à un générateur de tension alternative (31, 41, 32, 42), un circuit numérique qui, sous la commande d'un générateur de signaux d'horloge (20), fournit des signaux numériques correspondant à une fonction sinus ou à une fonction cosinus qui sont convertis par des convertisseurs numériques-analogiques (41, 42) en des signaux analogiques et un circuit de réglage (15) qui influence la fréquence du générateur de signaux d'horloge, caractérisé par les particularités suivantes :
a) les signaux de sortie des convertisseurs numériques-analogiques (41, 42) sont appliqués. respectivement, à des modulateurs d'impulsions en durée (51, 52) présentant une fréquence d'impulsions fixe, élevée par rapport au nombre de tours, commandant chacun un des amplificateurs (61, 62).
b) pour chaque enroulement de stator (71, 72) est prévue une régulation d'intensité, les signaux de sortie de comparateurs de valeurs de consigne/valeurs réelles d'intensité (91, 92) étant appliqués aux convertisseurs numériques-analogiques (41, 42) pour faire varier leurs signaux de sortie dans le sens d'une diminution de la différence entre les valeurs de consigne et les valeurs réelles d'intensité,
c) le circuit de réglage pilote la fréquence du générateur de signaux d'horloge (20) d'une manière telle qu'un comparateur (16) compare la valeur réelle (us) du nombre de tours du tube à rayons X à une valeur de consigne prédéfinie (u5), que dans le cas d'un dépassement par excès ou par défaut de la valeur réelle par la valeur de consigne dans une mesure prédéfinie, une valeur (U7) correspondant au nombre de tours de glissement est ajoutée à la valeur réelle de la vitesse ou est soustraite de celle-ci et que le signal ainsi formé est appliqué au générateur de signaux d'horloge (20) pour le pilotage de la fréquence.
2. Mécanisme de commande suivant la revendication 1, caractérisé en ce que les convertisseurs numériques-analogiques (41, 42) ont la forme de convertisseurs numériques-analogiques multiplicateurs dont l'entrée analogique reçoit le signal de sortie du circuit comparateur (91, 92) associé.
EP82200101A 1981-02-04 1982-01-28 Mécanisme de commande pour un tube à rayons X à anode rotative Expired EP0057485B1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE3103630 1981-02-04
DE3103630A DE3103630A1 (de) 1981-02-04 1981-02-04 Antriebseinrichtung fuer eine drehanoden-roentgenroehre

Publications (3)

Publication Number Publication Date
EP0057485A2 EP0057485A2 (fr) 1982-08-11
EP0057485A3 EP0057485A3 (en) 1982-12-29
EP0057485B1 true EP0057485B1 (fr) 1986-12-30

Family

ID=6123945

Family Applications (1)

Application Number Title Priority Date Filing Date
EP82200101A Expired EP0057485B1 (fr) 1981-02-04 1982-01-28 Mécanisme de commande pour un tube à rayons X à anode rotative

Country Status (4)

Country Link
US (1) US4376894A (fr)
EP (1) EP0057485B1 (fr)
JP (2) JPS57163999A (fr)
DE (2) DE3103630A1 (fr)

Families Citing this family (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPS5944975A (ja) * 1982-09-03 1984-03-13 Hitachi Ltd Ｐｗｍインバ−タの制御方法および装置
DE19911036C1 (de) * 1999-03-12 2000-06-21 Mannesmann Vdo Ag Regler für Heizungs- und Klimageräte in Kraftfahrzeugen
DE102013201154B4 (de) * 2013-01-24 2016-04-21 Siemens Aktiengesellschaft Verfahren zum Betrieb einer Drehanode und Drehanodenanordnung mit Energieverbrauchsoptimierung
CN104302081B (zh) * 2014-09-24 2017-06-16 沈阳东软医疗系统有限公司 一种ct球管中灯丝电流的控制方法和设备

Family Cites Families (9)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
FR2091903B1 (fr) * 1970-04-13 1974-02-01 Signaux Entr Electriques
US3832553A (en) * 1971-10-27 1974-08-27 Siemens Ag Circuit for a rotary anode x-ray tube
US3971972A (en) * 1975-03-14 1976-07-27 Allis-Chalmers Corporation Transistor inverter motor drive having voltage boost at low speeds
JPS5250520A (en) * 1975-10-21 1977-04-22 Toshiba Corp Frequency convertor
JPS5838080B2 (ja) * 1976-10-08 1983-08-20 株式会社東芝 誘導電動機の制御装置
DE2732852C2 (de) * 1977-07-21 1982-05-06 Philips Patentverwaltung Gmbh, 2000 Hamburg Schaltungsanordnung mit einer Drehanoden-Röntgenröhre zum Auslösen eines Schaltvorganges beim Erreichen einer vorgegebenen Drehzahl der Drehanode
GB2034938B (en) * 1978-11-22 1982-12-22 Ferranti Ltd Automatic control systems
JPS55125089A (en) * 1979-03-22 1980-09-26 Fanuc Ltd Variable speed operation system for squirrel-cage induction motor
JPS5612803A (en) * 1979-07-06 1981-02-07 Hitachi Ltd Controller for electric vehicle driven by induction motor

Also Published As

Publication number Publication date
US4376894A (en) 1983-03-15
DE3103630A1 (de) 1982-08-19
JPH0236200U (fr) 1990-03-08
EP0057485A2 (fr) 1982-08-11
EP0057485A3 (en) 1982-12-29
JPS57163999A (en) 1982-10-08
DE3274934D1 (en) 1987-02-05
JPH0314000Y2 (fr) 1991-03-28

Similar Documents

Publication Publication Date Title
DE2457838C3 (de) Anordnung zur Steuerung der Drehzahl eines Wechselstrommotors
DE2629927C2 (de) Anordnung zur Drehzahlregelung eines Synchronmotors
DE3438504A1 (de) Verfahren und einrichtung zur regelung einer drehfeldmaschine
DE2208853C3 (de) Anordnung zur Drehzahlregelung eines über einen Umrichter gespeisten Asynchronmotors
DE2329583B2 (de) Anordnung zur Drehzahlsteuerung eines Wechselstrommotors
DE2225609A1 (de) Mehrphasiger Wechselstrommotorantrieb mit einstellbarer Drehzahl
DE3810870C2 (fr)
DE2939133A1 (de) Induktionsmotor-steuervorrichtung
DE2614650C2 (de) Einrichtung zum Versorgen von einphasigen Verbrauchern mit Wechselspannung konstanter oder regelbarer Frequenz
EP0057485B1 (fr) Mécanisme de commande pour un tube à rayons X à anode rotative
DE2132179A1 (de) Einrichtung zur elektrischen pendelungsdaempfung von drehfeldmaschinen
EP0401901B1 (fr) Générateur pour le fonctionnement d'un tube à rayons x à anode tournante
DE2732852C2 (de) Schaltungsanordnung mit einer Drehanoden-Röntgenröhre zum Auslösen eines Schaltvorganges beim Erreichen einer vorgegebenen Drehzahl der Drehanode
DE3203974A1 (de) Motorregelanordnung
DE3609678C2 (de) Antriebsanordnung mit kollektorlosem Gleichstrommotor
DE1613512A1 (de) Regel-und steuerbare Wechsel- oder Umrichteranordnung zur Speisung von Wechselstrommotoren
EP0717285A2 (fr) Système de surveillance de la rotation d'un moteur d'entraînement d'une anode tournante dans un tube à rayons X
DE3324542A1 (de) Inverterschaltung/wechselrichterschaltung
EP0669791B1 (fr) Tube radiogène à anode tournante avec un circuit d'accélération et de freinage du anode tournante
DE3217900C2 (fr)
DE2739918C2 (de) Stromrichteranordnung
DE1513401A1 (de) Schaltungsvorrichtung zur Steuerung der Drehzahl eines Kommutator- oder Induktionsmotors
DE3046413A1 (de) "roentgendiagnostikgenerator"
DE3230055A1 (de) Steuersatz fuer einen pulswechselrichter
EP0366996B1 (fr) Moteur à induction sur réseau monophasé

Legal Events

Date Code Title Description
PUAI Public reference made under article 153(3) epc to a published international application that has entered the european phase

Free format text: ORIGINAL CODE: 0009012

17P Request for examination filed

Effective date: 19820218

AK Designated contracting states

Designated state(s): DE FR GB NL

RAP1 Party data changed (applicant data changed or rights of an application transferred)

Owner name: N.V. PHILIPS' GLOEILAMPENFABRIEKEN

Owner name: PHILIPS PATENTVERWALTUNG GMBH

PUAL Search report despatched

Free format text: ORIGINAL CODE: 0009013

AK Designated contracting states

Designated state(s): DE FR GB NL

GRAA (expected) grant

Free format text: ORIGINAL CODE: 0009210

AK Designated contracting states

Kind code of ref document: B1

Designated state(s): DE FR GB NL

PG25 Lapsed in a contracting state [announced via postgrant information from national office to epo]

Ref country code: NL

Effective date: 19861230

REF Corresponds to:

Ref document number: 3274934

Country of ref document: DE

Date of ref document: 19870205

ET Fr: translation filed
NLV1 Nl: lapsed or annulled due to failure to fulfill the requirements of art. 29p and 29m of the patents act
RAP2 Party data changed (patent owner data changed or rights of a patent transferred)

Owner name: N.V. PHILIPS' GLOEILAMPENFABRIEKEN

Owner name: PHILIPS PATENTVERWALTUNG GMBH

PLBE No opposition filed within time limit

Free format text: ORIGINAL CODE: 0009261

STAA Information on the status of an ep patent application or granted ep patent

Free format text: STATUS: NO OPPOSITION FILED WITHIN TIME LIMIT

26N No opposition filed
PGFP Annual fee paid to national office [announced via postgrant information from national office to epo]

Ref country code: GB

Payment date: 19921223

Year of fee payment: 12

PGFP Annual fee paid to national office [announced via postgrant information from national office to epo]

Ref country code: FR

Payment date: 19930120

Year of fee payment: 12

PGFP Annual fee paid to national office [announced via postgrant information from national office to epo]

Ref country code: DE

Payment date: 19930326

Year of fee payment: 12

PG25 Lapsed in a contracting state [announced via postgrant information from national office to epo]

Ref country code: GB

Effective date: 19940128

GBPC Gb: european patent ceased through non-payment of renewal fee

Effective date: 19940128

PG25 Lapsed in a contracting state [announced via postgrant information from national office to epo]

Ref country code: FR

Effective date: 19940930

PG25 Lapsed in a contracting state [announced via postgrant information from national office to epo]

Ref country code: DE

Effective date: 19941001

REG Reference to a national code

Ref country code: FR

Ref legal event code: ST