CN103973246A - Low-noise transimpedance amplifier for optical receiver - Google Patents
Low-noise transimpedance amplifier for optical receiver Download PDFInfo
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Abstract
The invention discloses a low-noise transimpedance amplifier for an optical receiver. The low-noise transimpedance amplifier for the optical receiver comprises an inverting amplifier body (011) and a feedback resistor (012), wherein the inverting amplifier body (011) and the feedback resistor (012) are connected in parallel. The inverting amplifier body (011) is composed of a cascode input stage, a differential intermediate stage, a source electrode follower output stage, a direct-current feedback circuit, an NMOS transistor (100) and a current source (112). The low-noise transimpedance amplifier is mainly used in a front amplifier of the optical receiver. The NMOS transistor (100) is controlled through an automatic gain control unit so that the transimpedance gain of the low-noise trans-impedance amplifier can be controlled. The nonlinear problem caused by too large alternating current output amplitude during signal amplification is solved, and the dynamic range is enlarged. Meanwhile, the problem of serious offset of a circuit direct-current work point during signal amplification is solved, and a direct-current signal is eliminated; in addition, the current injection technology is promoted, noise is lowered, and the sensitivity is effectively improved.
Description
Technical field
The present invention relates to the optoelectronic IC OEIC(Optical ElectronicIntegrated Circuits of optical communication electronic technology) field, relate in particular to a kind of low noise trans-impedance amplifier with automatic gain control of the optical receiver for communication system before light.
Background technology
Along with the fast development of optical fiber communication, effectively promote the extensive use of optical communication product, its performance has also been proposed to harsh requirement simultaneously.Optical receiver chip is as the important component part of optical communication system, and its performance is related to (comprising sensitivity, dynamic range etc.) transmission quality of light signal.Wherein, trans-impedance amplifier (Transimpedence Amp, TIA) is positioned at receiver foremost, is most important chip in optical receiver, and its noise and dynamic range performance have directly determined sensitivity and the dynamic range of optical receiver.As can be seen here, the performance of trans-impedance amplifier has determined the performance of optical receiver and even whole optical fiber telecommunications system to a great extent.Therefore, the Trans-impedance preamplifier of research and design high speed, high-gain, low noise, wide dynamic range, for the performance that improves optical receiver, structure at a high speed, capacity, long-distance optical fiber communication system have important value greatly, and the optical communication industry to China and IC industry all have very important impetus.
Optical communication system is converted to current pulse signal with photodiode by light pulse signal conventionally.Trans-impedance amplifier (TIA) is converted to corresponding voltage pulse signal by this current pulse signal and amplifies for follow-up circuit and process.Because the dynamic range of the photoelectric current receiving is in actual use very large, trans-impedance amplifier also corresponding requirements has very large input dynamic range.Therefore; trans-impedance amplifier will have corresponding automatic gain control (Automatic GainControl; AGC) and DC maladjustment adjust mechanism, but the DC maladjustment Circuit tuning of main flow usually can bring adverse effect or structure too complicated to the noiseproof feature of circuit.
Therefore, those skilled in the art is devoted to develop the automatic gain control of a kind of band and DC maladjustment control, but can not affect the low noise trans-impedance amplifier of trans-impedance amplifier noiseproof feature.
Summary of the invention
Because the above-mentioned defect of prior art, technical problem to be solved by this invention is to provide a kind of a kind of low noise trans-impedance amplifier with automatic gain control for optical receiver that can not affect trans-impedance amplifier noiseproof feature.
For achieving the above object, the invention provides a kind of low noise trans-impedance amplifier for optical receiver, it is characterized in that, comprise sign-changing amplifier (011) and feedback resistance (012); Described sign-changing amplifier (011) and described feedback resistance (012) are connected in parallel;
Described sign-changing amplifier (011) is realized by cascade input stage, difference intergrade, source follower output stage, D.C. feedback circuit, NMOS pipe (100) and current source (112);
Described D.C. feedback circuit is RC low pass filter.
Further, described cascade input stage comprises that NMOS pipe (101), NMOS manage (102) and resistance (103);
The grid of described NMOS pipe (101) is connected with the MINUS end of input signal (IN), described NMOS pipe (100) and described feedback resistance (012); The direct ground connection of source electrode (VGND); Drain electrode is connected with the drain electrode of described NMOS pipe (100), the described NMOS pipe source electrode of (102) and the MINUS of described current source (112) end;
The grid of described NMOS pipe (102) is connected with described D.C. feedback circuit; Drain electrode is connected with MINUS end and the described difference intergrade of described resistance (103); Source electrode manages the drain electrode of (100) with described NMOS and the drain electrode of described NMOS pipe (101) is connected;
The PLUS termination power (VDD) of described resistance (103); MINUS end is connected with drain electrode and the described difference intergrade of described NMOS pipe (102) respectively.
Further, described difference intergrade comprises NMOS pipe (104), NMOS pipe (105), resistance (106) and NMOS pipe (109);
The grid of described NMOS pipe (104) is connected with described cascade input stage; Source electrode is connected with the source electrode of described NMOS pipe (105) and the drain electrode of described NMOS pipe (109) respectively; Drain electrode is connected with described power supply (VDD);
The external DC level of grid of described NMOS pipe (105); Source electrode is connected with the source electrode of described NMOS pipe (104) and the drain electrode of described NMOS pipe (109) respectively; Drain electrode is connected with the MINUS end of described resistance (106), described D.C. feedback circuit and described source follower output stage;
The MINUS end of described resistance (106) is connected with drain electrode, described D.C. feedback circuit and the described source follower output stage of described NMOS pipe (105) respectively; PLUS end is connected with described power supply (VDD);
The grid of described NMOS pipe (109) is connected with described source follower output stage; Drain electrode is connected with the source electrode of described NMOS pipe (104) and the source electrode of described NMOS pipe (105) respectively; Source electrode source ground (VGND).
Further, described source follower output stage comprises NMOS pipe (110) and NMOS pipe (111);
The grid of described NMOS pipe (110) is connected with described D.C. feedback circuit and described difference intergrade; Source electrode is connected with output point (OUT), the described NMOS pipe drain electrode of (111) and the PLUS of described feedback resistance (012) end; Drain electrode is connected with described power supply (VDD);
The direct ground connection of source electrode (VGND) of described NMOS pipe (111); Drain electrode is connected with the PLUS end of output point (OUT) and described feedback resistance (012) and the source electrode of described NMOS pipe (110); The direct ground connection of source electrode (VGND).
Further, described RC low pass filter comprises resistance (107) and electric capacity (108);
The PLUS end of described resistance (107) is connected with the MINUS end of the drain electrode of described NMOS pipe (105), described resistance (106) and the grid of described NMOS pipe (110); MINUS end is connected with the described NMOS pipe grid of (102) and the PLUS of described electric capacity (108) end;
The PLUS end of described electric capacity (108) is connected with the described NMOS pipe grid of (102) and the MINUS of described resistance (107) end; MINUS end ground connection (VGND).
Further, described NMOS pipe (100) source electrode is connected with described input signal (IN), the described NMOS pipe grid of (101) and the MINUS of described resistance (012) end respectively; Drain electrode is connected with described NMOS pipe (101) drain electrode, the described NMOS pipe source electrode of (102) and the MINUS of described current source (112) end.
Further, power supply (VDD) described in described current source (112) PLUS termination; MINUS end is connected with the source electrode of the drain electrode of described NMOS pipe (101), described NMOS pipe (102) and the drain electrode of NMOS pipe (100) respectively.
Use the Optical Receiver Preamplifier for the low noise trans-impedance amplifier of optical receiver, wherein, comprised trans-impedance amplifier (01), singly turn differential amplifier (02), export driving (03) and automatic gain control unit (04);
The input of described trans-impedance amplifier (01) connects input signal, and output is connected with the described input that singly turns differential amplifier (02); The described output that singly turns differential amplifier (02) drives the input of (03) and the input of described automatic gain control unit (04) to be connected with described output respectively; Described output drives the output output signal of (03); The output of described automatic gain control unit (04) is connected with described trans-impedance amplifier (1);
Described automatic gain control unit (04) is connected with the grid of the described NMOS pipe (100) of described trans-impedance amplifier (01).
In a preferred embodiment of the present invention, described Optical Receiver Preamplifier also comprises photodiode bias voltage generation module (305), band-gap reference module (306) and benchmark generation module (307);
Described photodiode bias voltage generation module (305) is connected with photodiode; Be used to photodiode that bias voltage is provided;
Described band-gap reference module (306) and described benchmark generation module (307) link together with described power supply (VDD), for reference voltage and reference current are provided.
In preferred embodiments of the present invention, input signal is the current pulse signal being obtained by photodiode induction light signal.Sign-changing amplifier 011 with across resistance, feedback resistance 012 forms trans-impedance amplifier 01, trans-impedance amplifier is changed current pulse signal be enlarged into the voltage pulse signal of certain amplitude; Singly turn differential amplifier 02 this single-ended voltage signal is converted into both-end differential signal; Drive 03 finally output through output again, output drives 03 output resistance 50 Ω, is convenient to transmission line coupling.Trans-impedance amplifier 01 adopts parallel feedback structure, i.e. sign-changing amplifier 011 form in parallel with feedback resistance (across resistance) 012, and this structure has the advantages such as low input resistance, low output impedance and is widely adopted.Automatic gain control unit 04, in the time that input signal is larger, can reduce the transimpedance gain of trans-impedance amplifier, and while making large-signal, the amplitude of ac output voltage still remains in output voltage swing claimed range, improves dynamic range.
The low noise trans-impedance amplifier with automatic gain control for optical receiver of the present invention, the beneficial effect of some below having reached:
(1) when the present invention has solved large-signal by automatic gain control, exchange the excessive nonlinear problem causing of output amplitude, improve dynamic range: NMOS pipe 100 reduces transimpedance gain by two aspects: on the one hand, part alternating current flows through NMOS pipe 100, reduce to flow through the AC signal current across resistance 012, reduced output amplitude; On the other hand, NMOS pipe 100 has reduced the gain of sign-changing amplifier 011, has also reduced transimpedance gain.By this two aspect, the mode with respect to one-side adjusting across resistance resistance or amplifier gain, this kind of structure can more effectively regulate transimpedance gain, improved significantly dynamic range;
(2) the present invention, by the DC feedback loop of the compositions such as difference intergrade (NMOS pipe 104, NMOS pipe 105, NMOS pipe 106, NMOS manage 109), RC low pass filter (resistance 107, electric capacity 108) and common gate NMOS pipe 102 and load resistance 103, has solved large signal delay circuit DC point the serious problem being offset has occurred.This loop is negative feedback, add NMOS and manage 100 pipes for average electric current provides circulation path, has reached the function that direct current is eliminated, and makes to flow through direct current across resistance 012 very little, has therefore stablized output DC point, has improved dynamic range;
(3) the present invention is used for eliminating direct current signal, improve the DC feedback loop of dynamic range, structure is relatively simple, and and difference intergrade (NMOS pipe 104, NMOS pipe 105, NMOS pipe 106, NMOS pipe 109) common circuit, solved traditional direct current and eliminated the complexity of circuit;
(4) the present invention proposes current injection, inject extra Yi road electric current to NMOS pipe 101, on the basis that does not affect gain and bandwidth, increased the mutual conductance of NMOS pipe 101, reduced noise, effectively improved sensitivity;
(5) the present invention can be applied to the front end circuit of numerous optical receiver systems, comprises GePON, gigabit Ethernet and optical-fibre channel etc.
Below with reference to accompanying drawing, the technique effect of design of the present invention, concrete structure and generation is described further, to understand fully object of the present invention, feature and effect.
Brief description of the drawings
Fig. 1 is the electrical block diagram of a kind of low noise trans-impedance amplifier for optical receiver of the present invention;
Fig. 2 is the electrical block diagram of having applied the Optical Receiver Preamplifier chip of trans-impedance amplifier of the present invention;
Fig. 3 is the electrical block diagram of having applied another preferred embodiment of the Optical Receiver Preamplifier of trans-impedance amplifier of the present invention.
Embodiment
Below in conjunction with accompanying drawing, embodiments of the invention are elaborated, the present embodiment is implemented under with technical solution of the present invention prerequisite, provided detailed execution mode and concrete operating process, but protection scope of the present invention is not limited to following embodiment.
The circuit structure of the low noise trans-impedance amplifier that is applied to optical receiver of the present invention specifically as shown in Figure 1, comprises sign-changing amplifier 011, feedback resistance 012.Feedback resistance 012 is connected between the output OUT and input IN of sign-changing amplifier 011, and sign-changing amplifier 011 is made up of three-stage amplifier and D.C. feedback circuit.
Wherein inverting amplifier 011 is realized by cascade input stage, difference intergrade, source follower output stage, RC low pass filter, NMOS pipe 100 and current source 112:
Cascade input stage comprises NMOS pipe 101, NMOS pipe 102 and resistance 103:
The grid of NMOS pipe 101 is connected with the MINUS end of input signal IN, NMOS pipe 100 and feedback resistance 012; The direct ground connection VGND of source electrode; Drain electrode is connected with drain electrode, the source electrode of NMOS pipe 102 and the MINUS end of current source 112 of NMOS pipe 100;
The grid of NMOS pipe 102 is connected with the MINUS end of resistance 107 and the PLUS end of electric capacity 108; Drain electrode is connected with the MINUS end of resistance 103 and the grid of NMOS pipe 104; Source electrode is connected with the drain electrode of NMOS pipe 100 and the drain electrode of NMOS pipe 101;
The PLUS termination power VDD of resistance 103; MINUS end is connected with the drain electrode of NMOS pipe 102 and the grid of NMOS pipe 104 respectively.
Difference intergrade comprises NMOS pipe 104, NMOS pipe 105, resistance 106 and NMOS pipe 109:
The grid of NMOS pipe 104 is connected with the MINUS end of resistance 103 and the drain electrode of NMOS pipe 102; Source electrode is connected with the source electrode of NMOS pipe 105 and the drain electrode of NMOS pipe 109 respectively; Drain electrode is connected with power vd D;
The external DC level of grid of NMOS pipe 105; Source electrode is connected with the source electrode of NMOS pipe 104 and the drain electrode of NMOS pipe 109 respectively; Drain electrode is connected with MINUS end, the PLUS end of resistance 107 and the grid of NMOS pipe 110 of resistance 106;
The PLUS termination power VDD of resistance 106; MINUS connects the drain electrode of NMOS pipe 105, the PLUS end of resistance 107, the grid of NMOS pipe 110;
NMOS manages 109 grids and is connected with the grid of NMOS pipe 111; Source ground VGND; Drain electrode is connected with the source electrode of NMOS pipe 104 and the source electrode of NMOS pipe 105.
Source follower output stage comprises NMOS pipe 110 and NMOS pipe 111:
NMOS manages 110 source electrodes and is connected with the drain electrode of output point OUT, NMOS pipe 111 and the PLUS end of feedback resistance 012; Drain electrode is connected with power vd D; Grid connects 105 drain electrodes, the MINUS end of resistance 106 and the PLUS end of resistance 107 of NMOS pipe;
The direct ground connection VGND of source electrode of NMOS pipe 111; Drain electrode is connected with the source electrode of output point OUT and NMOS pipe 110; Grid is connected with the grid of NMOS pipe 109.
RC low pass filter comprises resistance 107 and electric capacity 108:
The PLUS end of resistance 107 is connected with the MINUS end of the drain electrode of NMOS pipe 105, resistance 106 and the grid of NMOS pipe 110; MINUS end is connected with the grid of NMOS pipe 102 and the PLUS end of electric capacity 108;
The PLUS end of electric capacity 108 is connected with the MINUS end of the grid of NMOS pipe 102 and resistance 107; MINUS end ground connection VGND.
NMOS pipe 100NMOS pipe 100, as automatic gain adjustment pipe, between the grid and drain electrode of input pipe 101, is operated in linear zone, is equivalent to an adjustable resistance by gate voltage control, is used for regulating transimpedance gain; Source electrode is connected with the grid of input signal IN, NMOS pipe 101 and the MINUS end of resistance 012 respectively; Drain electrode is connected with the source electrode of 101 drain electrodes of NMOS pipe, NMOS pipe 102 and the MINUS end of current source 112.
The PLUS termination power VDD of current source 112; MINUS end is connected with drain electrode, the source electrode of NMOS pipe 102 and the drain electrode of NMOS pipe 100 of NMOS pipe 101 respectively.
The low noise trans-impedance amplifier that is applied to optical receiver of the present invention is a part for Optical Receiver Preamplifier chip, wherein Optical Receiver Preamplifier chip specifically as shown in Figure 2, comprises that low noise amplifying circuit comprises trans-impedance amplifier 01, singly turns differential amplifier 02, exports driving 03 and automatic gain control unit 04.Wherein, input signal is the current pulse signal being obtained by photodiode 05 induction light signal.Sign-changing amplifier 011 with across resistance, feedback resistance 012 forms trans-impedance amplifier 01, trans-impedance amplifier is changed current pulse signal be enlarged into the voltage pulse signal of certain amplitude; Singly turn differential amplifier 02 this single-ended voltage signal is converted into both-end differential signal; Drive 03 finally output through output again, output driver output resistance 50 Ω, are convenient to transmission line coupling.Trans-impedance amplifier 01 in Fig. 2, singly turn differential amplifier 02, output and drive 03 and automatic gain control unit 04 is common forms whole preamplifier 10.Wherein, OUTP and OUTN represent output.
Trans-impedance amplifier 01 in Fig. 2 adopts parallel feedback structure, i.e. sign-changing amplifier 011 and feedback resistance (across resistance) the 012nd, and form in parallel, this structure has the advantages such as low input resistance, low output impedance and is widely adopted.Automatic gain control unit 04, in the time that input signal is larger, can reduce the transimpedance gain of trans-impedance amplifier, and while making large-signal, the amplitude of ac output voltage still remains in output voltage swing claimed range, improves dynamic range.
The reason of restriction trans-impedance amplifier dynamic range has two:
The first, along with the increase of input signal, ac output voltage amplitude is excessive, has exceeded the restriction of output voltage swing;
The second, there is Non-zero Mean in the input signal of trans-impedance amplifier, and average electric current flows through across resistance, in the time that average electric current is excessive, can produce larger pressure drop, causes exporting DC level serious skew occurs, and makes amplifier depart from normal operation region.
Automatic gain control unit 04 can solve the problem being caused by first reason.The overload being caused by second reason has still limited the dynamic range of trans-impedance amplifier.This just need to adopt direct current elimination (DCCancellation) to suppress the impact of average current on amplifier DC point.
NMOS pipe 100 of the present invention, as automatic gain adjustment pipe, is used for regulating transimpedance gain, and its grid-control voltage is generated by the automatic gain control unit 04 in Fig. 2.The output of difference intergrade (NMOS pipe 104, NMOS pipe 105, NMOS pipe 106 and NMOS pipe 109) through RC low pass filter (resistance 107, electric capacity 108) afterwards as the gate bias voltage of bank tube 102 altogether.NMOS pipe 104, NMOS pipe 105, NMOS pipe 106, resistance 107, electric capacity 108 and NMOS pipe 109 have formed DC feedback loop, in the time of large-signal, can play the effect of stabilizing circuit DC point, this feedback control loop is exactly the direct current elimination functional unit that this invention carries, its structure is relatively simple, and shares a part of circuit (NMOS pipe 104, NMOS pipe 105, NMOS pipe 106, NMOS pipe 109) with difference intergrade.The introducing in Injection Current source 112 has increased the mutual conductance of input pipe 101, has reduced the input noise of whole trans-impedance amplifier.
Automatic gain control unit 04 is for detection of the AC signal amplitude singly turning between the output difference sub-signal of differential amplifier 02, and the output of automatic gain control unit 04 connects the grid of NMOS pipe 100.Detailed automatic gain control unit 04 circuit does not specifically provide here.
Whether activate the working region of trans-impedance amplifier 01 to be divided according to automatic gain control unit 04 and can be divided into " activation " region and " inactive " region:
(1) " inactive " region:
Hour, signal amplitude and average electric current are all less for input current signal, and automatic gain control unit 04 and direct current are eliminated functional unit and do not worked, and trans-impedance amplifier 01 is in linear work district.The grid-control voltage of now adjusting pipe 100 keeps the minimum output voltage of automatic gain control unit 04, adjusts pipe 100 in cut-off state, and un-activation is controlled in gain.Do not have electric current (direct current with exchange) to manage 100 by adjustment, electric current all flows through across resistance 012.Automatic gain control unit 04 is not worked, and difference intergrade is only for enlarging function.In the time of small-signal, automatic gain control unit 04 and direct current are eliminated and are not all activated, and trans-impedance amplifier 01 is operated in " inactive " region.
The noiseproof feature in " inactive " region has determined the sensitivity of trans-impedance amplifier 01, the mutual conductance that reduce input noise and must increase input pipe 101.Amplify the bias current in flow through NMOS pipe 101, NMOS pipe 102 and resistance 103 paths, can increase the mutual conductance of NMOS pipe 101, but this mode has two shortcomings: 1. the electric current that will increase the resistance 103 of flowing through must reduce the resistance of resistance 103, cause the gain of preamplifier to decline, bandwidth declines; 2. the electric current of the NMOS that flows through pipe 102 increases the mutual conductance increase that makes NMOS pipe 102, will increase input noise.
In order to overcome this two shortcomings, the present invention has adopted current injection.Use current source 112 to the extra road electric currents that inject of NMOS pipe 101, most of bias current of NMOS pipe 101 will be provided by current source 112 like this, the NMOS that flows through manage 102 and resistance 103 only have sub-fraction bias current.Under the condition of not losing gain and bandwidth, reduce noise so, improved sensitivity.
(2) " activation " region:
When input current signal increases to a certain degree, because output AC amplitude is excessive or output DC point is seriously offset, distortion now must operate at " activation " region guarantee trans-impedance amplifier 01 and keeps normal operating state trans-impedance amplifier 01.
Automatic gain control unit 04 produces the grid-control voltage of NMOS pipe 100 according to signal magnitude, regulate its equivalent resistance, and signal is larger, and grid-control voltage is larger, and equivalent resistance is less.In " activation " region, NMOS manages 100 conductings, is operated in linear zone, now, has electric current to flow through NMOS pipe 100, comprises direct current and exchanges.
In the time of large-signal, a part for input exchange signal flows through NMOS pipe 100, has reduced by the AC signal across resistance 012, and amplitude output signal is corresponding to diminish, and has reduced transimpedance gain; The equivalent resistance of NMOS pipe 100 has reduced the gain of cascade input stage simultaneously, has also just reduced the gain of sign-changing amplifier 011, and therefore whole loop gain also increases and reduces with signal, and loop stability does not increase and worsens with signal.Input signal is larger, and it is larger that NMOS manages 100 grid-control voltages, flows through the shared ratio of the ac current signal of NMOS pipe 100 larger, and equivalent resistance is less, and the transimpedance gain of trans-impedance amplifier 01 is less.In a word, manage 100 control by NMOS, reduced transimpedance gain, solved and exchanged the excessive impact on dynamic range of output amplitude.
When NMOS pipe 100 regulates transimpedance gain, eliminate unit for direct current the circulation path of input-mean electric current is provided.When large-signal, due to the effect of direct current negative feedback loop (NMOS pipe 104, NMOS pipe 105, NMOS pipe 106, resistance 107, electric capacity 108, NMOS pipe 109), a big chunk of average electric current flows through NMOS pipe 100, only has a very little part to flow through across resistance 012, just very little across the pressure drop in resistance 012.And input signal is larger, the ratio of direct current that flows through NMOS pipe 100 is also larger, makes across the pressure drop in resistance 012 relatively stablely, and output DC level remains in normal range (NR).DC feedback loop has completed the direct current of input current signal and has eliminated function, the relatively stable DC point of circuit, and while having solved large-signal, DC point is offset the nonlinear problem of the trans-impedance amplifier causing.
Trans-impedance amplifier circuit structure of the present invention has wide dynamic range, highly sensitive advantage, chip power-consumption and area have been saved simultaneously, can be applied in the Trans-impedance preamplifier chip of high-performance optical receiver system, be positioned at chip foremost, complete the function that photo-signal is converted into voltage signal, it is the most crucial module of whole trans-impedance amplifier chip.
A specific embodiment of the present invention as shown in Figure 3.The 300th, external photodiode, it in solid line boxes, is the composition of preamplifier entirety chip, its module consists of: 301 is the trans-impedance amplifier of the present invention shown in Fig. 2, the 302nd, single slip parallel circuit, the 303rd, output driving circuit, the 304th, automatic gain control module, the 305th, photodiode bias voltage generation module, the 306th, band-gap reference module, 307 is benchmark generation module.Wherein, VDD is power supply, and GND represents ground connection, and OUTP and OUTN represent output.
In the present embodiment, trans-impedance amplifier circuit 301 is applied to preamplifier entirety chip foremost, it is most crucial module, the anode of its input termination photodiode 300, and the negative electrode of photodiode 300 connects photodiode bias voltage generation module 305, photodiode bias voltage generation module 305, for photodiode 300 provides bias voltage, makes photodiode 300 in reverse-biased state, and the intensity of induction light signal generates the current pulse signal of corresponding amplitude.Trans-impedance amplifier 301 receives these current signals, by its conversion and be enlarged into the voltage pulse signal of certain amplitude.This voltage pulse signal outputs to follow-up single-ended transfer difference circuit 302 and is converted into differential signal, and differential signal is conducive to suppress common-mode noise, is convenient to subsequent treatment simultaneously.Differential signal is finally exported through output driving circuit 303 again, and the object of output driving circuit 303 is to improve driving force, mates with transmission line simultaneously.Automatic gain control module 304 produces voltage control signal according to the size of signal, and this control signal offers trans-impedance amplifier 301 and realizes gain control.In addition, band-gap reference module 306 and benchmark generation module 307 provide reference voltage and reference current for circuit.
The present invention has solved the relevant issues such as dynamic range, sensitivity effectively, a kind of structure of new trans-impedance amplifier circuit has been proposed, its wide dynamic range, highly sensitive feature performance benefit, and the advantage of saving power consumption and area, can be applied in the Trans-impedance preamplifier chip of high-performance optical receiver system (GePON, gigabit Ethernet, optical-fibre channel etc.).
More than describe preferred embodiment of the present invention in detail.The ordinary skill that should be appreciated that this area just can design according to the present invention be made many modifications and variations without creative work.Therefore, all technical staff in the art, all should be in by the determined protection range of claims under this invention's idea on the basis of existing technology by the available technical scheme of logical analysis, reasoning, or a limited experiment.
Claims (9)
1. for a low noise trans-impedance amplifier for optical receiver, it is characterized in that, comprise sign-changing amplifier (011) and feedback resistance (012); Described sign-changing amplifier (011) and described feedback resistance (012) are connected in parallel;
Described sign-changing amplifier (011) is realized by cascade input stage, difference intergrade, source follower output stage, D.C. feedback circuit, NMOS pipe (100) and current source (112);
Described D.C. feedback circuit is RC low pass filter.
2. the low noise trans-impedance amplifier for optical receiver as claimed in claim 1, wherein, described cascade input stage comprises that NMOS pipe (101), NMOS manage (102) and resistance (103);
The grid of described NMOS pipe (101) is connected with the MINUS end of input signal (IN), described NMOS pipe (100) and described feedback resistance (012); The direct ground connection of source electrode (VGND); Drain electrode is connected with the drain electrode of described NMOS pipe (100), the described NMOS pipe source electrode of (102) and the MINUS of described current source (112) end;
The grid of described NMOS pipe (102) is connected with described D.C. feedback circuit; Drain electrode is connected with MINUS end and the described difference intergrade of described resistance (103); Source electrode manages the drain electrode of (100) with described NMOS and the drain electrode of described NMOS pipe (101) is connected;
The PLUS termination power (VDD) of described resistance (103); MINUS end is connected with drain electrode and the described difference intergrade of described NMOS pipe (102) respectively.
3. the low noise trans-impedance amplifier for optical receiver as claimed in claim 2, wherein, described difference intergrade comprises NMOS pipe (104), NMOS pipe (105), resistance (106) and NMOS pipe (109);
The grid of described NMOS pipe (104) is connected with described cascade input stage; Source electrode is connected with the source electrode of described NMOS pipe (105) and the drain electrode of described NMOS pipe (109) respectively; Drain electrode is connected with described power supply (VDD);
The external DC level of grid of described NMOS pipe (105); Source electrode is connected with the source electrode of described NMOS pipe (104) and the drain electrode of described NMOS pipe (109) respectively; Drain electrode is connected with the MINUS end of described resistance (106), described D.C. feedback circuit and described source follower output stage;
The MINUS end of described resistance (106) is connected with drain electrode, described D.C. feedback circuit and the described source follower output stage of described NMOS pipe (105) respectively; PLUS end is connected with described power supply (VDD);
The grid of described NMOS pipe (109) is connected with described source follower output stage; Drain electrode is connected with the source electrode of described NMOS pipe (104) and the source electrode of described NMOS pipe (105) respectively; Source ground (VGND).
4. the low noise trans-impedance amplifier for optical receiver as claimed in claim 3, wherein, described source follower output stage comprises NMOS pipe (110) and NMOS pipe (111);
The grid of described NMOS pipe (110) is connected with described D.C. feedback circuit and described difference intergrade;
Source electrode is connected with output point (OUT), the described NMOS pipe drain electrode of (111) and the PLUS of described feedback resistance (012) end; Drain electrode is connected with described power supply (VDD);
The direct ground connection of source electrode (VGND) of described NMOS pipe (111); Drain electrode is connected with the PLUS end of output point (OUT) and described feedback resistance (012) and the source electrode of described NMOS pipe (110); The direct ground connection of source electrode (VGND).
5. the low noise trans-impedance amplifier for optical receiver as claimed in claim 4, wherein, described RC low pass filter comprises resistance (107) and electric capacity (108);
The PLUS end of described resistance (107) is connected with the MINUS end of the drain electrode of described NMOS pipe (105), described resistance (106) and the grid of described NMOS pipe (110); MINUS end is connected with the described NMOS pipe grid of (102) and the PLUS of described electric capacity (108) end;
The PLUS end of described electric capacity (108) is connected with the described NMOS pipe grid of (102) and the MINUS of described resistance (107) end; MINUS end ground connection (VGND).
6. the low noise trans-impedance amplifier for optical receiver as claimed in claim 1, wherein, described NMOS pipe (100) source electrode is connected with described input signal (IN), the described NMOS pipe grid of (101) and the MINUS of described resistance (012) end respectively; Drain electrode is connected with described NMOS pipe (101) drain electrode, the described NMOS pipe source electrode of (102) and the MINUS of described current source (112) end.
7. the low noise trans-impedance amplifier for optical receiver as claimed in claim 1, wherein, power supply (VDD) described in described current source (112) PLUS termination; MINUS end is connected with the source electrode of the drain electrode of described NMOS pipe (101), described NMOS pipe (102) and the drain electrode of NMOS pipe (100) respectively.
8. one kind uses the Optical Receiver Preamplifier of the low noise trans-impedance amplifier for optical receiver as claimed in claim 1, wherein, comprise trans-impedance amplifier (01), singly turn differential amplifier (02), export driving (03) and automatic gain control unit (04);
The input of described trans-impedance amplifier (01) connects input signal, and output is connected with the described input that singly turns differential amplifier (02); The described output that singly turns differential amplifier (02) drives the input of (03) and the input of described automatic gain control unit (04) to be connected with described output respectively; Described output drives the output output signal of (03); The output of described automatic gain control unit (04) is connected with described trans-impedance amplifier (1);
Described automatic gain control unit (04) is connected with the grid of the described NMOS pipe (100) of described trans-impedance amplifier (01).
9. Optical Receiver Preamplifier as claimed in claim 8, is characterized in that, also comprises photodiode bias voltage generation module (305), band-gap reference module (306) and benchmark generation module (307); Described photodiode bias voltage generation module (305) is connected with photodiode; Be used to photodiode that bias voltage is provided;
Described band-gap reference module (306) and described benchmark generation module (307) link together with described power supply (VDD), for reference voltage and reference current are provided.
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| CN201420163707.XU CN204046530U (en) | 2014-04-04 | 2014-04-04 | A kind of low noise trans-impedance amplifier and Optical Receiver Preamplifier thereof |
| CN201410135951.XA CN103973246A (en) | 2014-04-04 | 2014-04-04 | Low-noise transimpedance amplifier for optical receiver |
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| CN201410135951.XA CN103973246A (en) | 2014-04-04 | 2014-04-04 | Low-noise transimpedance amplifier for optical receiver |
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| CN201410135951.XA Pending CN103973246A (en) | 2014-04-04 | 2014-04-04 | Low-noise transimpedance amplifier for optical receiver |
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