WO2024185004A1 - 電力変換装置 - Google Patents

電力変換装置 Download PDF

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Publication number
WO2024185004A1
WO2024185004A1 PCT/JP2023/008310 JP2023008310W WO2024185004A1 WO 2024185004 A1 WO2024185004 A1 WO 2024185004A1 JP 2023008310 W JP2023008310 W JP 2023008310W WO 2024185004 A1 WO2024185004 A1 WO 2024185004A1
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WO
WIPO (PCT)
Prior art keywords
zero
current
phase
phase current
conversion device
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PCT/JP2023/008310
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English (en)
French (fr)
Japanese (ja)
Inventor
遼司 鶴田
智大 田中
博史 益永
Original Assignee
三菱電機株式会社
株式会社Tmeic
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Priority to JP2025504937A priority Critical patent/JPWO2024185004A1/ja
Priority to PCT/JP2023/008310 priority patent/WO2024185004A1/ja
Publication of WO2024185004A1 publication Critical patent/WO2024185004A1/ja

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/02—Conversion of AC power input into DC power output without possibility of reversal
    • H02M7/04—Conversion of AC power input into DC power output without possibility of reversal by static converters
    • H02M7/12—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode

Definitions

  • This disclosure relates to power conversion devices, and in particular to AC/DC converters.
  • the secondary side of the transformer when connecting to a commercial power source, the secondary side of the transformer may be star-connected and its neutral point may be floating.
  • the voltage utilization rate of the AC/DC converter is improved by superimposing a third harmonic on the output voltage using the degree of freedom of the zero-phase voltage (for example, Patent Document 1).
  • Patent Document 2 targets a three-phase, four-wire system in which the secondary side of the transformer is star-connected and its neutral point is grounded, and feedback control is performed by separating the zero-phase current from the normal mode current, so that the zero-phase current is controlled to be zero.
  • the present disclosure is intended to solve the above problems, and aims to provide a power conversion device capable of stable operation in AC current control.
  • a power conversion device includes an AC/DC converter connected to a three-phase AC power source and converting AC power into a DC voltage, and a controller for controlling the AC/DC converter.
  • the AC/DC converter includes a plurality of semiconductor switching elements provided between positive and negative electrodes and driven by AC power, a DC capacitor provided in parallel with the plurality of semiconductor switching elements and for holding the converted DC voltage, a filter circuit provided between the three-phase AC power source and the plurality of semiconductor switching elements and composed of an AC filter reactor and an AC filter capacitor, a neutral line connected to the DC capacitor via a neutral point of the AC filter capacitor and serving as a path for a zero-phase current, and a current detector for detecting the current of each phase between the filter circuit and the plurality of semiconductor switching elements.
  • the controller includes an AC current control unit that outputs an AC output voltage command for each phase based on the current detection value detected by the current detector, a third harmonic superimposing unit that performs control to superimpose a frequency three times the fundamental wave frequency on the AC output voltage command, a PWM unit that determines the switching pattern of multiple semiconductor switching elements by comparing the signal superimposed by the third harmonic superimposing unit with the carrier wave, and a zero-phase current calculation unit that calculates the zero-phase current based on the current detection value.
  • the AC current control unit excludes frequency components within a predetermined range of the zero-phase current from the control target based on the zero-phase current value obtained by the zero-phase current calculation unit.
  • the power conversion device according to this disclosure is capable of stable operation in AC current control.
  • FIG. 1 is a diagram illustrating an example of a circuit configuration of a power conversion device 101 according to a first embodiment of the present disclosure.
  • 1 is a diagram illustrating a function of a controller 107 of a power conversion device 101 according to a first embodiment of the present disclosure.
  • FIG. FIG. 11 is a diagram illustrating superposition of a third harmonic according to the first embodiment of the present disclosure.
  • FIG. 2 is a block diagram illustrating an example of the function of a zero-phase current calculation unit 302 according to the first embodiment of the present disclosure.
  • FIG. 11 is a diagram illustrating functions of an ACR unit 301 according to the first embodiment of the present disclosure.
  • FIG. 13 is a diagram illustrating an example of a circuit configuration of a power conversion device 101# according to a modification of the first embodiment of the present disclosure.
  • FIG. 11 is a diagram illustrating a controller 107# according to a second embodiment of the present disclosure.
  • FIG. 11 is a diagram illustrating a configuration of ACR units 701 and 702 according to a second embodiment of the present disclosure.
  • FIG. 11 is a diagram illustrating a schematic comparison of flow paths of a normal mode current and a zero-phase current according to a second embodiment of the present disclosure.
  • FIG. 13 is a diagram illustrating a configuration of a current control unit of a controller 107P according to a third embodiment of the present disclosure.
  • FIG. 11 is a diagram illustrating a configuration of a zero-phase current calculation unit 1110 of a power conversion device according to a fourth embodiment of the present disclosure.
  • FIG. 1 is a diagram illustrating an example of a circuit configuration of a power conversion device 101 according to a first embodiment of the present disclosure.
  • the power conversion device 101 is an AC/DC converter that converts input AC power into DC power and provides bidirectional power interchange between the AC input and the DC output.
  • the power conversion device 101 is connected to a commercial power source 102, which supplies power using three-phase AC voltage, via a transformer 103.
  • the primary side and secondary side are electrically insulated from each other by the transformer 103.
  • the side connected to the commercial power source 102 is called the primary side
  • the side connected to the AC/DC converter is called the secondary side.
  • the power conversion device 101 includes current detectors 104a, 104b, and 104c, AC voltage detectors 105a, 105b, and 105c, a DC voltage detector 106, an AC filter reactor 112, an AC filter capacitor 113, semiconductor switching elements 108a_P, 108a_N, 108b_P, 108b_N, 108c_P, and 108c_N, DC capacitors 110P and 110N, and a controller 107.
  • a filter circuit is formed by an AC filter reactor 112 and an AC filter capacitor 113.
  • AC voltage detectors 105a, 105b, and 105c detect the AC voltage of each phase transformed by transformer 103.
  • the DC voltage detector 106 detects the DC voltage that is the output of the power conversion device 101 .
  • the controller 107 controls the input AC voltage to an arbitrarily set DC voltage based on the current values of each phase from the current detectors 104a, 104b, and 104c, the AC voltage values of each phase from the AC voltage detectors 105a, 105b, and 105c, and the DC voltage value of the DC voltage detector 106.
  • the semiconductor switching elements 108a_P, 108a_N are connected in series between the positive and negative DC terminals 111P, 111N.
  • the semiconductor switching elements 108b_P, 108b_N are connected in series between the positive and negative DC terminals 111P, 111N.
  • the semiconductor switching elements 108c_P, 108c_N are connected in series between the positive and negative DC terminals 111P, 111N. In addition, the midpoints of each are connected to the AC side terminals of each phase.
  • freewheeling diodes 109a_P, 109a_N, 109b_P, 109b_N, 109c_P, and 109c_N are connected in anti-parallel to the semiconductor switching elements 108a_P, 108a_N, 108b_P, 108b_N, 108c_P, and 108c_N, respectively.
  • DC capacitors 110P, 110N are connected in series between positive and negative DC terminals 111P, 111N, and the midpoint is connected to AC filter capacitor 113.
  • the controller 107 controls the input AC voltage to an arbitrarily set DC voltage by controlling the on/off of the semiconductor switching elements 108a_P, 108a_N, 108b_P, 108b_N, 108c_P, and 108c_N.
  • IGBTs Insulated Gate Bipolar Transistors
  • MOSFETs Metal-Oxide-Semiconductor Field Effect Transistors
  • DC terminals 111P and 111N supply DC power by connecting to a load device or other power conversion device that is driven by DC voltage.
  • a three-phase coupled reactor is used as the AC filter reactor 112, but it is also possible to configure three separate reactors for each phase.
  • the AC filter capacitor is configured in a three-phase star connection and has a neutral point.
  • FIG. 2 is a diagram illustrating the function of the controller 107 of the power conversion device 101 according to the first embodiment of the present disclosure. Referring to FIG. 2, in the controller 107 according to the first embodiment, a control block of a portion that generates a gate signal that controls the on/off of a semiconductor switching element from AC current control is shown.
  • the controller 107 includes an ACR unit 301, a zero-phase current calculation unit 302, a third harmonic superimposition unit 303, a PWM unit 305, an inverter 306, and a gate driver 307.
  • control is performed in the ACR (Auto Current Regulator) unit 301 based on the current detection value isens_R detected by the current detector 104a so that the current command value iref_R is calculated by the upper control system.
  • ACR Auto Current Regulator
  • the zero-phase current calculation value calculated by the zero-phase current calculation unit 302 is also input.
  • the zero-phase current calculation unit 302 calculates the zero-phase current using the current detection values for the three phases as input. If the three-phase current detection values are separated into normal mode current components innormal_X (X: R, S, T) and zero-phase current components izero, they can be expressed as shown in the following equation. Note that the zero-phase current components have a common value for each phase.
  • the third harmonic superimposing unit 303 adds a third harmonic voltage command value Vtriref to the output of the ACR unit 301 by an adder 304.
  • This third harmonic voltage command value Vtriref is a zero-phase sequence voltage command value for each phase.
  • the signal is input to the PWM unit 305, where it is pulse-width modulated to generate a pulse signal for controlling the on/off of the semiconductor switching element.
  • the two series-connected semiconductor switching elements are turned on/off in a mutually opposite manner, so that, for example, an inverter 306 can be used for the pulse signal of the upper semiconductor switching element to An on/off pulse signal for the lower semiconductor switching element is obtained. At this time, a dead time may be inserted to prevent the upper and lower semiconductor switching elements from being turned on simultaneously.
  • FIG. 3 is a diagram illustrating superimposition of a third harmonic according to the first embodiment of the present disclosure.
  • the schematic waveforms of the modulated wave vref1 before the third harmonic is superimposed, the modulated wave vref2 after the third harmonic is superimposed, and the superimposed third harmonic vreftri are shown for the modulated wave input to the PWM unit 305.
  • the peak value of the modulated wave which is the output voltage command, is reduced, and the voltage utilization rate can be improved. Therefore, although the third harmonic appears in the phase voltage of the output voltage, the third harmonic does not appear in the line voltage because it is a zero-phase voltage, so it is applicable to a three-phase three-wire power supply configuration.
  • the potential of the neutral line 114 changes due to the superposition of third harmonics, and a third harmonic current that depends on the impedance of the filter circuit flows. Since this current flows in principle due to the superposition of third harmonics, for example, when the current command value is a value that makes the zero-phase current zero, it contradicts the AC current control.
  • the three-phase AC current command value given to the ACR unit 301 takes into account only the normal mode component, so as a result, the zero-phase current component of the AC current command value becomes zero, and the current of the third harmonic component becomes a deviation. Therefore, if the gain in the AC current control of the ACR unit 301 is set high, there is a risk that the AC current control will become unstable in an attempt to eliminate the deviation.
  • the zero-phase current component may also be the resonant current of the AC filter reactor 112 and the AC filter capacitor 113 in the filter circuit.
  • the above-mentioned resonant current is a disturbance component, so it is a current that should be actively set to zero in the AC current control unit.
  • the ACR unit 301 of the power conversion device 101 according to the present embodiment 1, which performs third harmonic superposition it is preferable to control the zero-phase current component to be zero by the AC current control unit by excluding the third harmonic component, which in principle does not become zero, from the control object, while controlling the resonant frequency component of the filter circuit as the control object.
  • FIG. 4 is a block diagram showing an example of the function of the zero-phase current calculation unit 302 according to the first embodiment of the present disclosure.
  • the zero-phase current calculation unit 302 includes adders 501 and 502, a multiplier 503, and an LPF unit 504.
  • the zero-phase current detection value is obtained by multiplying the sum of the three-phase AC currents by 1/3. Therefore, the sum of each AC current is calculated using adders 501 and 502, and multiplied by 1/3 using multiplier 503. Furthermore, in this embodiment 1, an LPF (Low Pass Filter) unit 504 is provided that performs low-pass filter processing.
  • LPF Low Pass Filter
  • the zero-phase current obtained in this manner, from which components higher than the set frequency have been removed, is output from the zero-phase current calculation unit 302 as the zero-phase current compensation value.
  • FIG. 5 is a diagram illustrating the function of the ACR unit 301 according to the first embodiment of the present disclosure.
  • the ACR unit 301 includes subtractors 601 and 602 and a gain multiplier 603.
  • the subtractor 601 calculates the difference between the current command value iref and the current detection value isens and multiplies it by a gain to perform control, but because the zero-phase current component of the current command value iref is zero, the current detection value isens is controlled to be zero even if a third harmonic current is included.
  • compensation for the zero-phase current component is performed by subtracting the above-mentioned zero-phase current compensation value izero_comp from the current detection value by the subtractor 602.
  • the deviation from the current command value iref is calculated and input to the gain multiplier 603, which becomes the output of the ACR unit 301.
  • a compensation value based on the AC voltage may be added in a feedforward manner to the value after gain multiplication, but this is omitted here.
  • the power conversion device 101 controls the power conversion device 101 to be zero based on the current command value iref.
  • the zero-phase current contains a mixture of components that cannot be made zero by AC current control, such as third harmonic superposition and DC offset of the current detection value, and components that are preferably made zero by AC current control, such as the resonant frequency component of the filter circuit, it is possible to effectively exclude the components that cannot be made zero from the control targets, thereby improving the stability of AC current control in the power conversion device.
  • FIG. 6 is a diagram showing an example of the circuit configuration of a power conversion device 101# according to a modified example of the first embodiment of the present disclosure.
  • DC capacitor 110 is provided between the positive and negative electrodes instead of DC capacitors 110P and 110N.
  • this configuration eliminates the need to configure the DC capacitor 110 as a series circuit, which reduces the number of components.
  • the impedance of the zero-phase current path is different, and the voltage applied to the AC filter capacitor is unipolar.
  • the power conversion device 101# according to the modified example of the first embodiment of the present disclosure, even if there is a path through which the zero-phase current flows and the zero-phase current contains a mixture of components that cannot be made zero by AC current control, such as third harmonic superposition and DC offset of the current detection value, and components that are preferably made zero by AC current control, such as the resonant frequency component of the filter circuit, it is possible to effectively exclude the components that cannot be made zero from the control targets, thereby improving the stability of the AC current control in the power conversion device.
  • AC current control such as third harmonic superposition and DC offset of the current detection value
  • components that are preferably made zero by AC current control such as the resonant frequency component of the filter circuit
  • FIG. 7 is a diagram illustrating controller 107# according to the second embodiment of the present disclosure.
  • controller 107# differs from controller 107 in that it has ACR units 701 and 702, a zero-phase current calculation unit 703, and an adder 704 instead of ACR unit 301 and zero-phase current calculation unit 302.
  • ACR unit 701 and 702 has ACR units 701 and 702
  • a zero-phase current calculation unit 703 has ACR units 701 and 702
  • an adder 704 instead of ACR unit 301 and zero-phase current calculation unit 302.
  • the rest of the configuration is the same as that described in FIG. 2, so detailed description thereof will not be repeated.
  • the AC current control is carried out independently by separating the current control system for the normal mode component and the current control system for the zero-phase current.
  • ACR unit 701 controls the current of the normal mode component, and ACR unit 702 controls the zero-phase current.
  • Zero-phase current calculation unit 703 calculates the zero-phase current from the three-phase current detection values, but low-pass filter processing that extracts only predetermined frequency components as in embodiment 1 is not performed at this stage. After being controlled independently, the two control amounts are added together by adder 704. Subsequent processing involves third harmonic superposition and pulse signal generation by PWM, as in embodiment 1 described in Figure 2.
  • FIG. 8 is a diagram illustrating the configuration of ACR units 701 and 702 according to the second embodiment of the present disclosure.
  • ACR unit 701 includes subtractors 801 and 802 and a gain multiplier 803.
  • the ACR unit 702 includes an HPF unit 804 and a gain multiplier 805 .
  • the ACR unit 701 which controls the current of the normal mode component will be described.
  • the subtractor 801 of the ACR unit 701 eliminates the zero-phase current component by subtracting the zero-phase current detection value izero_sens obtained by the calculation of the zero-phase current calculation unit 703 from the current detection value isens.
  • subtractor 802 outputs the difference with the current command value iref, which is intended for only the normal mode component.
  • a gain multiplier 803 receives the difference, amplifies it with a predetermined gain, and outputs it.
  • the ACR unit 702 controls the zero-phase current.
  • HPF unit 804. This is to exclude frequency components below the third harmonic from the zero-phase current control targets.
  • the cutoff frequency of the HPF unit 804 must be designed to sufficiently attenuate the third harmonic components while not attenuating the resonant frequency components of the filter circuit.
  • the zero-phase current command value is always zero, the output of the HPF unit 804 becomes the input to the gain multiplier 805 as is.
  • the current control systems are separated for normal mode components and zero-phase current components.
  • FIG. 9 is a diagram that shows a schematic comparison of the flow paths of normal mode current and zero-phase current according to the second embodiment of the present disclosure.
  • the flow path of the normal mode current is shown.
  • the pulse voltage generating units 901a to 901c that accompany the switching of the semiconductor switching element by the gate driver 307 are simply shown.
  • FIG. 9(B) the flow path of the zero-phase current is shown.
  • a case is shown in which a flow path is formed through AC filter reactor 904, AC filter capacitor 905, and DC capacitor 906 in accordance with the generation of a pulse voltage by pulse voltage generating unit 902.
  • the zero-phase current paths are independent and essentially equal for each phase, so we will only consider one phase.
  • the normal mode component current passes through the AC filter reactor and flows so that the sum of the three phases is always zero, whereas the zero-phase current has the same value for each phase, passes through the AC filter capacitor, and is the main component that circulates in the power conversion device 101 via the neutral line.
  • the impedance of the paths through which the normal mode component current and the zero-phase current flow differ, so further stabilization of AC current control can be expected by implementing gain design separately.
  • FIG. 10 is a diagram illustrating a configuration of a current control unit of controller 107P according to the third embodiment of the present disclosure.
  • the controller 107P includes ACR units 1002 and 1005, an ⁇ conversion unit 1001, an inverse ⁇ conversion unit 1003, a zero-phase current calculation unit 10004, and adders 1006, 1007, and 1008.
  • the controller 107P according to the third embodiment explains a method for separating the current detection value detected by the current detector into the normal mode component current and the zero-phase current using a method different from that shown in FIG. 8.
  • the ⁇ conversion unit 1001 performs Clarke transformation, which is a three-phase/two-phase transformation, on the current detection values isens_R, isens_S, and isens_T. This results in the current detection values isens_ ⁇ and isens_ ⁇ on the ⁇ - ⁇ coordinate system.
  • Clarke transformation is a three-phase/two-phase transformation
  • the control is performed by the ACR unit 1002 that receives the current command values iref_ ⁇ and iref_ ⁇ on the ⁇ coordinates as inputs. This enables current control that targets only the normal mode current.
  • the result is converted back into three-phase control amounts.
  • the zero-phase current excluded in the above-mentioned ⁇ conversion unit 1001 is calculated in a zero-phase current calculation unit 1004 based on the three-phase current detection values.
  • the ACR unit 1005 When controlling the zero-phase current, the ACR unit 1005 must exclude third harmonic components and DC components from the control targets, so it performs high-pass filtering in the HPF unit as described in Figure 8.
  • the ACR unit 1005 which is the zero-phase current control unit, is basically the same as the ACR unit 702 shown in FIG. 8.
  • the zero-phase current contains a mixture of components that cannot be made zero by AC current control, such as third harmonic superposition and DC offset of the current detection value, and components that are preferably made zero by AC current control, such as the resonant frequency component of a filter circuit, it is possible to effectively exclude the components that cannot be made zero from the control targets.
  • AC current control such as third harmonic superposition and DC offset of the current detection value
  • components that are preferably made zero by AC current control such as the resonant frequency component of a filter circuit
  • FIG. 11 is a diagram illustrating a configuration of a zero-phase current calculation unit 1110 of a power conversion device according to a fourth embodiment of the present disclosure.
  • the zero-phase current calculation unit 1110 includes adders 1101, 1102, and 1106, multipliers 1103 and 1107, a zero-order hold unit 1104, and a one-sampling delay unit 1105.
  • the zero-phase current detection value is obtained by adding the three-phase current detection values using adders 1101 and 1102 and multiplying them by 1/3 using multiplier 1103.
  • the switching frequency component of this zero-phase current is generally equal to the carrier frequency used in the PWM section and is a component that occurs with switching, so it cannot be suppressed by AC current control and may become a disturbance in current control.
  • the value obtained by removing the switching frequency component from the zero-phase current detection value is used in the subsequent AC current control and zero-phase current control.
  • the average value of two consecutive values sampled at twice the frequency of the carrier wave is taken as the zero-phase current detection value.
  • an example of average value calculation is shown, where sampling is performed at a frequency twice the frequency of the carrier wave in the zero-order hold unit 1104. Furthermore, the previous sampled value is held in the 1-sample delay unit 1105, the sum is calculated in the adder 1106, and the sum is multiplied by 1/2 in the multiplier 1107, making it possible to calculate the average value of two consecutive values sampled at twice the frequency of the carrier wave.
  • the power conversion device can effectively exclude the components that cannot be made zero from the control targets. Since only the switching frequency component of the zero-phase current, which is a disturbance, can be removed by a sampling method, the detection delay that occurs can also be suppressed to the same extent as the switching frequency, improving the stability of AC current control.
  • 101 Power conversion device 102 Commercial power source, 103 Transformer, 104a, 104b, 104c, 105 Current detector, 105a, 105b, 105c AC voltage detector, 106 DC voltage detector, 107, 107P Controller, 108a, 108b, 108c Semiconductor switching element, 109a, 109b, 109c Freewheeling diode, 110, 110N , 110P, 906 DC capacitor, 111N, 111P DC terminal, 112, 903a, 903b, 903c, 904 AC filter reactor, 113, 905 AC filter capacitor, 114 neutral line, 301, 701, 702, 1002, 1005 ACR section, 305 PWM section, 303 third harmonic superposition section, 307 gate driver.

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PCT/JP2023/008310 2023-03-06 2023-03-06 電力変換装置 WO2024185004A1 (ja)

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Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH10164846A (ja) * 1996-11-29 1998-06-19 Meidensha Corp 電力変換装置の制御装置
JP2005045846A (ja) * 2003-07-22 2005-02-17 Hitachi Ltd 電力変換装置
WO2013145248A1 (ja) * 2012-03-30 2013-10-03 東芝三菱電機産業システム株式会社 電源装置
JP2014082901A (ja) * 2012-10-18 2014-05-08 Toshiba Mitsubishi-Electric Industrial System Corp 電力変換装置および電力変換装置の制御装置

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH10164846A (ja) * 1996-11-29 1998-06-19 Meidensha Corp 電力変換装置の制御装置
JP2005045846A (ja) * 2003-07-22 2005-02-17 Hitachi Ltd 電力変換装置
WO2013145248A1 (ja) * 2012-03-30 2013-10-03 東芝三菱電機産業システム株式会社 電源装置
JP2014082901A (ja) * 2012-10-18 2014-05-08 Toshiba Mitsubishi-Electric Industrial System Corp 電力変換装置および電力変換装置の制御装置

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