WO2024070731A1 - Dispositif de commande de moteur - Google Patents

Dispositif de commande de moteur Download PDF

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Publication number
WO2024070731A1
WO2024070731A1 PCT/JP2023/033547 JP2023033547W WO2024070731A1 WO 2024070731 A1 WO2024070731 A1 WO 2024070731A1 JP 2023033547 W JP2023033547 W JP 2023033547W WO 2024070731 A1 WO2024070731 A1 WO 2024070731A1
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WIPO (PCT)
Prior art keywords
motor
current
control device
phase
correction amount
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PCT/JP2023/033547
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English (en)
Japanese (ja)
Inventor
広大 武田
峻 谷口
健太郎 松尾
渉 初瀬
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日立Astemo株式会社
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Publication of WO2024070731A1 publication Critical patent/WO2024070731A1/fr

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/05—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation specially adapted for damping motor oscillations, e.g. for reducing hunting
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P23/00—Arrangements or methods for the control of AC motors characterised by a control method other than vector control
    • H02P23/04—Arrangements or methods for the control of AC motors characterised by a control method other than vector control specially adapted for damping motor oscillations, e.g. for reducing hunting
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters

Definitions

  • the present invention relates to a motor control device that controls the torque and speed of a motor.
  • the motor control device controls the motor current so that the motor torque and speed follow the command values. At this time, torque ripple occurs due to time harmonics of the motor current and spatial harmonics of the motor magnetic flux. Torque ripple is a cause of vibration and noise. In order to reduce the torque ripple, the motor control device executes torque ripple suppression control. In torque ripple suppression control, the current command value is corrected according to the torque ripple estimate value.
  • Torque ripple can also occur due to a gain error in the current sensor. If there is a gain error in the current sensor, a secondary vibration component occurs in the dq axis current converted from the motor current detection value (see, for example, "Equation (2)" in Patent Document 1 described below). The motor control device executes current control to remove this vibration component. This causes a current ripple in the motor current, which in turn generates a torque ripple.
  • Patent Document 1 The technology described in Patent Document 1 is known as a conventional technology for estimating and correcting the gain error of such a current sensor.
  • the motor control device has two operating modes: a normal operating mode and a CT correction drive mode.
  • the CT correction drive mode in the current control section, the d-axis current control section and the q-axis current control section are stopped, and only the non-interference control section continues to operate.
  • either the d-axis current command value Id* or the q-axis current command value Iq* is set to zero, and current flows only in one of the d and q axes.
  • only the pulsating component contained in either the d-axis current detection value or the q-axis current detection value is extracted to calculate the CT gain error.
  • the gain in the three-phase current calculation section is corrected based on the calculated CT gain error.
  • the motor control device has an operating sequence in which it starts up in a normal operating mode, goes through a CT correction drive mode, and then returns to the normal operating mode.
  • the motor control device is equipped with a special operation sequence to estimate and correct the gain error of the current sensor. This means that the development time and development costs of the motor control device may increase due to the need to set sequence execution conditions and stabilize control when switching sequences.
  • the present invention provides a motor control device that can stably and accurately estimate and compensate for the gain error of a current sensor without requiring a special operating sequence.
  • the motor control device generates a control signal for an inverter that drives an AC motor, and includes an error calculation unit that calculates the gain error of the current sensor using the amplitude value of the three-phase motor current detected by the current sensor, and a correction amount calculation unit that calculates a current correction amount to compensate for the gain error based on the gain error estimated by the error calculation unit.
  • FIG. 1 is a functional block diagram illustrating a configuration of a motor control device according to a first embodiment.
  • FIG. 4 is a functional block diagram illustrating a configuration of an error calculation unit in the first embodiment.
  • FIG. 4 is a functional block diagram illustrating a configuration of a correction amount calculation unit in the first embodiment.
  • 10 is a state transition diagram showing a change in the operation of the error estimating unit 102.
  • FIG. 4 is a flowchart showing an operation of a motor state determination unit 103.
  • 10 is a flowchart showing an operation of a correction destination selection unit 203.
  • FIG. 11 is a functional block diagram showing a configuration of a motor control device according to a second embodiment.
  • FIG. 11 is a functional block diagram illustrating a configuration of an error calculation unit in the second embodiment.
  • FIG. 11 is a functional block diagram illustrating a configuration of a correction amount calculation unit in the second embodiment.
  • 10 is a flowchart showing the operation of a correction destination selection unit
  • FIG. 1 is a functional block diagram showing the configuration of a motor control device according to a first embodiment of the present invention.
  • dq axis refers to the "d axis and q axis.”
  • X such as “i”
  • X dq refers to a “vector quantity (X d , X q )
  • X uvw refers to a “vector quantity (X u , X v , X w ).
  • uvw refers to three phases of AC, that is, "U phase, V phase, and W phase.”
  • the motor control device 1 controls the speed and torque of the motor 5 by controlling the switching of the inverter 4 that supplies AC power to the motor 5.
  • the motor control device 1 is configured with a processing device such as a microcomputer, and functions as each part by executing a specific program.
  • the inverter 4 is a three-phase inverter whose main circuit is a three-phase full-bridge circuit composed of semiconductor switching elements such as IGBTs and MOSFETs.
  • the control signal D* uvw generated by the motor control device 1 controls the on/off of the semiconductor switching elements that constitute the main circuit of the inverter 4.
  • the inverter 4 converts DC power input from a DC power source such as a storage battery into three-phase AC power and outputs a three-phase AC voltage v uvw .
  • the control signal D* uvw is a gate control signal for the semiconductor switching elements when the semiconductor switching elements are IGBTs or MOSFETs.
  • the control signal D* uvw is composed of six control signals, namely, a control signal for the U-phase upper arm (D* up ), a control signal for the U-phase lower arm (D* un ), a control signal for the V-phase upper arm (D* vp ), a control signal for the V-phase lower arm (D* vn ), a control signal for the W-phase upper arm (D* wp ) and a control signal for the W-phase lower arm (D* wn ), in order to control the switching of the three-phase full-bridge circuit which is the main circuit of the inverter 4.
  • the subscripts p and n represent the upper arm and lower arm, respectively.
  • the motor 5 is a three-phase AC synchronous motor, which is a rotating machine, such as a permanent magnet synchronous motor.
  • the motor 5 is not limited to a synchronous machine, and an induction machine may be used.
  • the motor 5 is not limited to a rotating machine, and a linear motor may be used.
  • the motor 5 may have a power generation function.
  • the motor control device 1 includes a dq-axis current command value 2 (i* dq ), a controller 3, an electrical angle calculation unit 6, an electrical angular velocity calculation unit 7, an A/D converter 8, a three-phase/dq-axis converter 9, a dq-axis current correction unit 10a, a three-phase current correction unit 10b, a current sensor 11, an error calculation unit 100, and a correction amount calculation unit 200.
  • the controller 3 generates a control signal D uvw * for controlling the switching of the inverter 4 in accordance with the difference between the dq-axis current detection value i dq and the dq-axis current command value i* dq (2) so that i dq coincides with i * dq .
  • the dq-axis current correction unit 10a corrects the difference input to the controller 3 by a dq-axis current correction amount ⁇ i dq .
  • ⁇ i dq is the correction amount of i dq , and compensates for the generation of vibration components of the dq-axis current detection value i dq caused by the gain error of the current sensor 11, as will be described later.
  • the controller 3 has a known configuration.
  • the controller 3 is composed of a dq-axis current controller that creates dq-axis voltage command values by PI calculation, a dq/three-phase converter that converts the dq-axis voltage command values into three-phase voltage command values, and a PWM controller that generates inverter control signals according to the three-phase voltage command values.
  • the dq-axis voltage command values may be created using known voltage equations.
  • the electrical angle calculation unit 6 calculates and outputs the electrical angle ⁇ e based on a rotational position signal from a rotation sensor (not shown) provided in the motor 5.
  • Resolvers Hall sensors, rotary encoders, etc. can be used as rotation sensors.
  • the electrical angular velocity calculation unit 7 calculates and outputs the electrical angular velocity ⁇ e based on a rotational position signal from a rotation sensor (not shown) provided in the motor 5.
  • the electrical angular velocity calculation unit 7 may be configured by a differentiator that differentiates ⁇ e output from the electrical angle calculation unit 6 to calculate ⁇ e .
  • the A/D converter 8 converts the current detection signal of the current sensor 11, obtained when the current sensor 11 acquires the three-phase motor actual current value i real uvw flowing in the distribution cable between the output of the inverter 4 and the motor 5, into a digital value handled by the motor control device 1, and outputs it as the three-phase motor current detection value i meas uvw .
  • the three-phase/dq-axis converter 9 calculates the dq-axis current detection value i dq based on the three-phase motor current detection value i meas uvw from the A/D converter 8 and the electrical angle ⁇ e from the electrical angle calculation unit 6.
  • the three-phase current correction unit 10b corrects i meas uvw by a correction coefficient m uvw described later.
  • the corrected three-phase motor current detection value is input to the three-phase/dq-axis converter 9.
  • the correction coefficient m uvw compensates for the generation of vibration components in the dq-axis current detection value i dq caused by a gain error (hereinafter referred to as "error") of the current sensor 11.
  • Current sensors 11 are provided on each of the three-phase distribution cables, or on two of the three-phase distribution cables.
  • A/D converter 8 converts the detection signals for the two phases into digital values, which are used as motor current detection values for the two phases.
  • a calculator (adder/subtractor) (not shown) calculates the motor current value for the remaining phase.
  • CT current transformer
  • Hall element a Hall element
  • the error calculation unit 100 calculates the error err uvw of the current sensor 11 based on the three-phase motor current detection value imeas uvw , the electrical angle ⁇ e , the electrical angular velocity ⁇ e , and the dq-axis current command value i dq *.
  • the correction amount calculation unit 200 calculates the dq-axis current correction amount ⁇ i dq used in the dq-axis current correction unit 10a and the correction coefficient m uvw used in the three-phase current correction unit 10b, based on the err uvw calculated by the error calculation unit 100 and the dq-axis current command value i* dq .
  • FIG. 2 is a functional block diagram showing the configuration of the error calculation unit 100 (FIG. 1) in the first embodiment.
  • the error calculation unit 100 includes a three-phase current amplitude estimation unit 101, an error estimation unit 102, and a motor state determination unit 103.
  • the subscripts “UVW” represent the three phases of AC, i.e., “U phase, V phase, and W phase.”
  • the motor state determination unit 103 determines the state of the motor 5 (FIG. 1) based on the dq axis current command values i* dq .
  • the error estimation unit 102 calculates and estimates the error err uvw of the current sensor 11 ( FIG. 1 ) based on the three-phase motor current amplitude values I UVW estimated by the three-phase current amplitude estimation unit 101 in accordance with the state of the motor 5 determined by the motor state determination unit 103.
  • FIG. 3 is a functional block diagram showing the configuration of the correction amount calculation unit 200 (FIG. 1) in the first embodiment.
  • the correction amount calculation unit 200 includes a dq-axis current correction amount calculation unit 201, a three-phase current correction amount calculation unit 202, and a correction destination selection unit 203.
  • the correction destination selection unit 203 selects, from ⁇ i dq and m uvw , a correction amount used to compensate for the occurrence of vibration components in the dq-axis current detection value i dq caused by the error of the current sensor 11. That is, the correction destination selection unit 203 selects, from the dq-axis current correction amount calculation unit 201 and the three-phase current correction amount calculation unit 202, a correction amount calculation unit that executes calculation of the correction amount.
  • the dq-axis current detection value i dq is expressed by the formula (1).
  • i dq is expressed as a column vector.
  • the column vector in the first term on the right side represents i real dq obtained by coordinate transformation of i real uvw .
  • the phase ⁇ in the second and third terms on the right side is a constant phase amount, as described later (see equation (12)).
  • the three-phase current correction unit 10b (FIG. 1) corrects the three-phase motor current detection values i meas uvw based on the equation (2).
  • the three-phase/dq-axis converter 9 calculates the dq-axis current detection value i dq from the corrected three-phase motor current detection value i meas uvw ′ and the electrical angle ⁇ e according to equation (3).
  • the controller 3 uses such dq-axis current detection values i_dq to generate the control signal D* uvw for controlling the switching of the inverter 4 (FIG. 1) as described above.
  • the means for estimating the three-phase motor current amplitude values IUVW in the three-phase current amplitude estimator 101 will be described using the U-phase motor current amplitude value IU as an example.
  • the U-phase motor current detection value i_meas u and the U-phase motor current amplitude value IU have the relationship shown in Equation (4).
  • the electrical angle ⁇ e may be corrected to be advanced by ⁇ e ⁇ t.
  • ⁇ c in equations (4) and (5) is a current phase in a rotating coordinate system and can be calculated from the dq-axis current detection values i dq . In this embodiment, however, it is calculated from the dq-axis current command values i* dq using equation (6).
  • ⁇ c may be calculated based on i* dq that has been passed through a low-pass filter (LPF) equivalent to a current control response expressed as a frequency.
  • LPF low-pass filter
  • table data representing the correspondence between ⁇ c and i dq may be used.
  • V-phase and W-phase motor current amplitude values I V and I W are expressed by equations (7) and (8) with phases shifted by ⁇ 2/3 ⁇ and 2/3 ⁇ , respectively, from the phase reference.
  • the denominators of equations (6) to (8) are trigonometric functions, a state of division by zero or very close to zero occurs twice per electrical angle cycle. Because the actual three-phase motor current is distorted from a sine wave, the current amplitude value may fluctuate significantly near the current zero crossing. This may reduce the accuracy of the error calculation in the error estimation unit 102. For this reason, when the value of the trigonometric function in the denominator falls below a certain value, the three-phase current amplitude estimation unit 101 may stop the calculation operation and output a predetermined value that is set in advance.
  • the error estimation unit 102 changes its operation based on the output (determination result) of the motor state determination unit 103.
  • FIG. 4 is a state transition diagram showing changes in the operation of the error estimation unit 102.
  • the initial value is (1, 1, 1).
  • the error may be set as the initial value.
  • the error estimation unit 102 calculates and outputs the error based on equation (9).
  • FIG. 5 is a flowchart showing the operation of the motor state determination unit 103.
  • step S101 When the motor state determination unit 103 starts processing (step S101), it determines in step S102 whether the time rate of change of the current phase amount ⁇ c of the motor 5, expressed by equation (6), is equal to or less than a predetermined constant value. If the motor state determination unit 103 determines that it is equal to or less than the constant value (YES in step S102), it then executes step S103, and if it determines that it is not equal to or less than the constant value, i.e., that it is greater than the constant value (NO in step S102), it then executes step S105.
  • step S103 the motor state determination unit 103 determines whether to perform error estimation. If the motor state determination unit 103 determines that an error estimation should be performed (YES in step S103), it next executes step S104, and if it determines that an error estimation should not be performed (NO in step S103), it next executes step S105.
  • step S104 the motor state determination unit 103 outputs "error estimation possible" as the motor state determination result. After executing step S104, the motor state determination unit 103 ends the series of processes.
  • step S105 the motor state determination unit 103 outputs "error estimation not possible" as the motor state determination result. After executing step S105, the motor state determination unit 103 ends the series of processes.
  • step S103 The criteria in step S103 are set appropriately, taking into account cases where the error estimation accuracy decreases or the calculation load increases.
  • step S103 may be omitted.
  • the error calculation includes division by the current amplitude value, so if the current amplitude value is small, the accuracy of the error calculation may decrease.
  • a conditional branch may be added to the operation of the motor state determination unit 103 so that "error estimation cannot be performed" is output when the current amplitude value is equal to or less than a predetermined constant value.
  • the second-order vibration component in the dq-axis current detection value i dq as shown in the third term on the right side of equation (1) is compensated for. Note that in this embodiment, the occurrence of the DC component of the dq-axis current as shown in the second term on the right side of equation (1) is not compensated for. Therefore, it is possible to suppress an unexpected decrease in torque accuracy due to compensation for the DC component.
  • the correction amount may be gradually adjusted according to the rotation speed of the motor 5.
  • the three-phase current correction amount calculation unit 202 calculates a correction coefficient m uvw based on the equation (14) using err uvw .
  • the correction of the three-phase motor current detection values using m uvw requires less calculation and has a smaller calculation load than the correction of the dq axis currents using ⁇ i dq .
  • the correction destination selection unit 203 selects the amount of correction to be calculated using the error err uvw from among m uvw and ⁇ i dq according to the conditions. That is, the correction destination selection unit 203 selects either the correction of the three-phase motor current detection value imeas uvw using the calculated m uvw or the correction of the dq-axis current detection value using the calculated ⁇ i dq . Note that if either one of them is selected in advance, the correction destination selection unit 203 may be omitted.
  • FIG. 6 is a flowchart showing the operation of the correction destination selection unit 203.
  • step S201 When the correction destination selection unit 203 starts processing (step S201), it determines in step S202 whether to perform error correction. If the correction destination selection unit 203 determines that error correction is to be performed (YES in step S202), it then executes step S204, and if it determines that error correction is not to be performed (NO in step S202), it then executes step S203.
  • step S204 the correction destination selection unit 203 determines whether to perform error correction on the d- and q-axis currents. If the correction destination selection unit 203 determines that error correction is to be performed on the d- and q-axis currents (YES in step S204), it next executes step S205, and if it determines that error correction is not to be performed on the d- and q-axis currents (NO in step S203), it next executes step S206.
  • step S203 the correction destination selection unit 203 instructs the dq-axis current correction amount calculation unit 201 to output "0" (vector amount) as ⁇ i dq , and instructs the three-phase current correction amount calculation unit 202 to output "1" (vector amount) as m uvw .
  • step S207 the correction destination selection unit 203 ends the series of processes.
  • step S205 the correction destination selection unit 203 instructs the dq-axis current correction amount calculation unit 201 to calculate and output ⁇ i dq using the error err uvw , and instructs the three-phase current correction amount calculation unit 202 to output "1" (vector amount) as m uvw .
  • step S207 the correction destination selection unit 203 ends the series of processes.
  • step S206 the correction destination selection unit 203 instructs the dq-axis current correction amount calculation unit 201 to output "0" (vector amount) as ⁇ i dq , and instructs the three-phase current correction amount calculation unit 202 to calculate and output m uvw using err uvw .
  • step S207 the correction destination selection unit 203 ends the series of processes.
  • error correction is performed on only one of the three-phase currents and the d- and q-axis currents. This improves the stability of the error correction operation in the motor control device.
  • step S204 The criteria in step S204 are set appropriately, taking into consideration cases where the error estimation accuracy decreases or the calculation load increases. Depending on the criteria in step S204, error correction may be performed on both the three-phase currents and the d- and q-axis currents.
  • the gain error of the current sensor is calculated based on the three-phase AC current amplitude value, and one of the three-phase current detection values and the dq-axis current detection values is corrected based on the calculated gain error.
  • the offset error of the current sensor has been compensated for in advance.
  • the offset error compensation of the current sensor can be performed, for example, by subtracting the average current value indicated by the output signal of the current sensor when no motor current is flowing from the motor current detection value.
  • the control unit for compensating for the gain error of the current sensor 11 is divided into an error calculation unit 100 that performs error estimation, and a correction amount calculation unit 200 that performs error correction.
  • the error calculation unit 100 may be operated to perform error estimation, and then the correction amount calculation unit 200 may be operated to perform error correction.
  • the correction amount calculation unit 200 may be operated to perform error correction based on the estimated error. Note that error estimation may be performed every time the motor 5 is started, or when a specified operation is performed on the motor control device 1.
  • FIG. 7 is a functional block diagram showing the configuration of a motor control device according to a second embodiment of the present invention.
  • the motor control device 1 of this embodiment does not have a current control system. Therefore, the dq-axis current detection values are not corrected to compensate for the gain error of the current sensor 11.
  • the motor control device 1 of this embodiment operates when current control is not being performed while the motor is being driven but motor current is flowing, i.e., when the dq-axis current command value and the actual dq-axis current flowing do not match, for example, when a three-phase short circuit of the inverter 4 is performed for overvoltage protection, etc.
  • the configuration of the motor control device 1 of this embodiment 2 is the part that operates in the above case in the motor control device of embodiment 1 ( Figure 1).
  • FIG. 8 is a functional block diagram showing the configuration of the error calculation unit 100 (FIG. 7) in the second embodiment.
  • the three-phase current amplitude estimation unit 101 calculates the three-phase motor current amplitude values I UVW based on the above-mentioned equations (5), (7), and (8), where the current phase ⁇ c in the rotating coordinate system is calculated from the d-axis and q-axis current detection values i dq using equation (15).
  • the motor state determination unit 103 in the second embodiment determines the state of the motor 5 (FIG. 7) by using the dq-axis current detection values i dq instead of the dq-axis current command values i* dq (FIG. 2).
  • FIG. 9 is a functional block diagram showing the configuration of the correction amount calculation unit 200 (FIG. 7) in the second embodiment.
  • FIG. 10 is a flowchart showing the operation of the correction destination selection unit 303.
  • Steps S301, S303, S304, S305, S306, S307, and S308 shown in FIG. 10 correspond to steps S201, S202, S204, S205, S206, S203, and S207 in FIG. 6 (Example 1), respectively.
  • step S301 when the correction destination selection unit 303 starts processing (step S301), it determines in step S302 whether current control is enabled. In this embodiment 2, since current control is not executed, the correction destination selection unit 303 determines that current control is not enabled (NO in step S302) and then executes step S306.
  • step S306 the correction destination selection unit 203 instructs the dq-axis current correction amount calculation unit 201 to output "0" (vector amount) as ⁇ i dq , and instructs the three-phase current correction amount calculation unit 202 to calculate and output m uvw using err uvw .
  • step S308 the correction destination selection unit 303 ends the series of processes.
  • the gain error of the current sensor is calculated based on the three-phase AC current amplitude value, and the three-phase current detection value is corrected based on the calculated gain error.
  • the present invention is not limited to the above-described embodiments, but includes various modified examples.
  • the above-described embodiments have been described in detail to clearly explain the present invention, and the present invention is not necessarily limited to those having all of the configurations described.
  • 1 Motor control device 2 dq axis current command value, 3 Controller, 4 Inverter, 5 Motor, 6 Electrical angle calculation unit, 7 Electrical angular velocity calculation unit, 8 A/D converter, 9 Three-phase/dq axis converter, 10a dq axis current correction unit, 10b Three-phase current correction unit, 100 Error calculation unit, 200 Correction amount calculation unit, 101 Three-phase current amplitude estimation unit, 102 Error estimation unit, 103 Motor state determination unit, 201 dq axis current correction amount calculation unit, 202 Three-phase current correction amount calculation unit, 203 Correction destination selection unit, 303 Correction destination selection unit.

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  • Power Engineering (AREA)
  • Control Of Ac Motors In General (AREA)

Abstract

L'invention divulgue un dispositif de commande de moteur qui est apte à estimer et à compenser une erreur de gain d'un capteur de courant électrique d'une manière stable et précise, sans être équipé d'une séquence de fonctionnement spéciale. Ce dispositif de commande de moteur (1) génère un signal de commande (D*uvw) pour un onduleur (4) qui entraîne un moteur à courant alternatif (5), le dispositif de commande de moteur comprenant : une unité de calcul d'erreur (100) qui calcule une erreur de gain (erruvw) d'un capteur de courant électrique (11) à l'aide d'une valeur d'amplitude d'un courant électrique de moteur triphasé détecté par le capteur de courant électrique ; et une unité de calcul de quantité de correction (200) qui, sur la base de l'erreur de gain estimée par l'unité de calcul d'erreur, calcule des quantités de correction de courant électrique (muvw, Δidp) pour compenser l'erreur de gain.
PCT/JP2023/033547 2022-09-28 2023-09-14 Dispositif de commande de moteur WO2024070731A1 (fr)

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JP2022154790A JP2024048720A (ja) 2022-09-28 2022-09-28 モータ制御装置
JP2022-154790 2022-09-28

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Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH07274411A (ja) * 1994-03-30 1995-10-20 Mitsubishi Electric Corp 車両用発電制御装置
JP2011078295A (ja) * 2008-10-30 2011-04-14 Denso Corp 自動車のモータ制御装置
JP2013219988A (ja) * 2012-04-12 2013-10-24 Denso Corp 回転機の制御装置

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH07274411A (ja) * 1994-03-30 1995-10-20 Mitsubishi Electric Corp 車両用発電制御装置
JP2011078295A (ja) * 2008-10-30 2011-04-14 Denso Corp 自動車のモータ制御装置
JP2013219988A (ja) * 2012-04-12 2013-10-24 Denso Corp 回転機の制御装置

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