WO2023213292A1 - 一种组合控制电压变换器、控制方法、电源和新能源汽车 - Google Patents

一种组合控制电压变换器、控制方法、电源和新能源汽车 Download PDF

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Publication number
WO2023213292A1
WO2023213292A1 PCT/CN2023/092230 CN2023092230W WO2023213292A1 WO 2023213292 A1 WO2023213292 A1 WO 2023213292A1 CN 2023092230 W CN2023092230 W CN 2023092230W WO 2023213292 A1 WO2023213292 A1 WO 2023213292A1
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WIPO (PCT)
Prior art keywords
voltage
resistor
switch tube
input
output
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PCT/CN2023/092230
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English (en)
French (fr)
Inventor
王超
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Changchun Jetty Automotive Parts Co Ltd
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Changchun Jetty Automotive Parts Co Ltd
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Publication of WO2023213292A1 publication Critical patent/WO2023213292A1/zh
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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
    • H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
    • H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1582—Buck-boost converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
    • H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
    • H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/157—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators with digital control
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • This application relates to the technical field of adjustable DC power supply, especially a combined control voltage converter, control method, power supply and new energy vehicle.
  • the power supply is an important part of the DC charging pile (DC Wallbox). Normally, the power supply is not only required to have high efficiency, small size, high power, etc., it is also required to have good dynamic performance and provide a wide output voltage with an adjustable range. ability. When the adjustable range of the input voltage is limited and the output voltage is required to be wide and adjustable, the output voltage will be required to both step up and step down.
  • Buck and Boost converters are the two simplest structures among buck and boost converters respectively. When these two circuits are combined, there are often more diodes and capacitors in the circuit structure, resulting in a larger circuit size. Moreover, the cost of high-voltage diodes is relatively high and cannot meet product requirements.
  • the purpose of this article is to provide a combined control voltage converter, control method, power supply and new energy vehicle to solve the problem of the single function of the voltage converter and the traditional buck-boost structure in the existing technology.
  • the cost is too high and the circuit structure and control methods are complex.
  • the embodiment of the first aspect of the present application provides a combined control voltage converter, including: a buck-boost circuit, the buck-boost circuit is provided between an input port and an output port;
  • the buck-boost circuit includes a first switch tube, a second switch tube, a third switch tube that is in complementary conduction with the first switch tube, a fourth switch tube that is in complementary conduction with the second switch tube, an energy storage inductor, an energy storage capacitor and a control unit;
  • the drain of the first switch tube and the input port The anode of the switch is connected to the anode, the source of the first switch is connected to the drain of the third switch, the source of the third switch is connected to the cathode of the input port; one end of the energy storage inductor
  • the drain of the third switch is connected, the other end is connected to the drain of the second switch, the source of the second switch is connected to the source of the third switch;
  • the drains of the four switching tubes are connected to the drain of the second switching
  • An embodiment of the second aspect of the present application provides a control method for the combined control voltage converter according to any one of the above, including: when receiving an instruction to make the output voltage of the output port lower than the input voltage of the input port, determining In the current voltage range where the output voltage is located, if the output voltage is lower than the first threshold, the first switch is controlled to be turned on/off periodically, and the second switch is controlled to be continuously turned off to reduce the output voltage.
  • the first switch tube When receiving an instruction to make the output voltage higher than the input voltage, determine the voltage interval in which the current output voltage is located, and if the output voltage is higher than the second threshold, control the second switching tube cycle
  • the first switch tube is turned on/off to control the conduction of the first switch tube to increase the output voltage; wherein, the on/off period of the first switch tube is determined according to the voltage loop signal, and the degree of reduction is determined according to the voltage loop signal.
  • the duty cycle of the voltage loop signal is determined; the on/off period of the second switch tube is determined based on the voltage loop signal, and the degree of improvement is determined based on the duty cycle of the voltage loop signal.
  • a third embodiment of the present application provides a power supply provided with any of the combined control voltage converters described above.
  • An embodiment of the fourth aspect of the present application provides a new energy vehicle, which is provided with the power supply.
  • the buck-boost circuit includes a first switch tube, a second switch tube, and a third switch that is in complementary conduction with the first switch tube. tube, a fourth switch tube that is complementary to the second switch tube, an energy storage inductor, an energy storage capacitor and a control unit.
  • the control unit obtains the voltage of the output port and compares it with the voltage of the input port, thereby controlling the first switch tube,
  • the second switching tube, the third switching tube and the fourth switching tube are turned on, off or periodically turned on and off to realize boosting or reducing the output voltage of the output port.
  • this solution uses fewer devices and does not install large high-voltage diodes in the integrated circuit, which reduces the volume and manufacturing cost of the voltage converter.
  • Figure 1 shows a schematic diagram of a circuit of a combined control voltage converter according to an embodiment of this article.
  • FIG. 2 shows a schematic diagram of the control unit in the embodiment of this article.
  • FIG. 3 shows a detailed schematic diagram of the control unit of the embodiment of this article.
  • Figure 4 shows the circuit diagram of the control unit of the embodiment of this article.
  • Figure 5 shows a schematic diagram of the isolation module according to the embodiment of this article.
  • Figure 6 shows a schematic diagram of a control method for a combined control voltage converter according to the embodiment of this article.
  • Figure 7 shows a schematic diagram of the buffering method of a control method for a combined control voltage converter according to the embodiment of this article.
  • the embodiment of the first aspect of the present application provides a circuit for a combined control voltage converter as shown in FIG. 1 , including: a buck-boost circuit 12 , and the buck-boost circuit 12 is provided between the input port 11 and the output port 13 .
  • the voltage-boosting and bucking circuit 12 includes a first switch tube 201, a second switch tube 202, a third switch tube 203 that is in complementary conduction with the first switch tube 201, a fourth switch tube 204 that is in complementary conduction with the second switch tube 202, Energy storage inductor 15, energy storage capacitor 16 and control unit 14.
  • the drain of the first switch 201 is connected to the anode of the input port 11 , the source of the first switch 201 is connected to the drain of the third switch 203 , and the source of the third switch 203 is connected to the cathode of the input port 11 .
  • One end of the energy storage inductor 15 is connected to the drain of the third switch 203 , the other end is connected to the drain of the second switch 202 , and the source of the second switch 202 is connected to the source of the third switch 203 .
  • the drain of the fourth switch 204 is connected to the drain of the second switch 202 , and the source of the fourth switch 204 is connected to one end of the energy storage capacitor 16 .
  • the control unit 14 is connected to the input port 11 and the gates of the first switch tube 201 , the second switch tube 202 , the third switch tube 203 and the fourth switch tube 204 respectively.
  • the voltage-boost and buck circuit 12 is provided between the input port 11 and the output port 13 of the power supply.
  • the voltage-boost and buck circuit 12 includes a first switch tube 201, a second switch tube 202, and a first switch tube 201.
  • the third switching tube 203 which is in complementary conduction, the fourth switching tube 204 which is in complementary conduction with the second switching tube 202 , the energy storage inductor 15 , the energy storage capacitor 16 and the control unit 14 obtain the voltage of the output port 13 through the control unit 14 Compare it with the voltage of the input port 11, and then control the first switching tube 201, the second switching tube 202, the third switching tube 203 and the fourth switching tube 204 to be turned on, off or periodically turned on and off to achieve the output Boost or step down the output voltage of port 13.
  • this solution uses fewer devices and is not included in the integrated circuit Setting up a larger high-voltage diode reduces the size and manufacturing cost of the voltage converter.
  • the control unit 14 controls the third The first switch tube 201 and the second switch tube 202 are turned on/off synchronously.
  • control unit 14 controls the second switch tube 202 to turn off, and controls the first switch tube 201 to turn on/off periodically.
  • control unit 14 controls the first switch tube 201 to be turned on and the second switch tube 202 to be turned on/off periodically.
  • the first threshold value in this article may be 90%, and the second threshold value may be 110%.
  • the output voltage When the voltage converter is working, the output voltage may be a step-up or a step-down relative to the input voltage.
  • the on/off state of different switching tubes is quickly switched, which will cause the output Drastic changes in voltage cause fluctuations, which is unacceptable for the power supply and new energy vehicle fields that require high voltage stability. Therefore, in this article, when controlling the voltage converter, in order to avoid the above situation, a buffering method is set up.
  • the output voltage has a larger boost compared to the input voltage, or the output voltage has a larger boost compared to the input voltage
  • time-sharing modulation can be used.
  • pulse width modulation of simultaneous on and simultaneous off can be used.
  • the first switching tube 201 When determining the output voltage that needs to be outputted, the first switching tube 201 needs to be periodically turned on/off.
  • the periodic turning on/off is called pulse width adjustment control. Because the first switch tube 201 and the third switch tube 203 are in complementary conduction, that is, when the first switch tube 201 is on, the third switch tube 203 is off, so the third switch tube 203 is also under pulse width adjustment control. At this time, the second switch tube 202 is always turned off. Because the second switch tube 202 and the fourth switch tube 204 are in complementary conduction, the fourth switch tube 204 is always turned on.
  • the output port 13 cannot obtain the entire input voltage, so the output voltage is a step-down relative to the input voltage.
  • the energy storage inductor 15 is equivalent to a power supply and inputs voltage to the output port 13, so that when the first switch tube 201 is turned off, the output port 13 can still output voltage.
  • the voltage of the energy storage inductor 15 cannot be greater than the voltage of the input port 11, so the input voltage obtained by the output port 13 is also lower than the input voltage of the input port 11. Therefore, through the above process, it is realized that when the first switch tube 201 is turned on/off, the output port 13 will output a voltage that is reduced relative to the input voltage.
  • the second switching transistor 202 When determining the output voltage that needs to be boosted, the second switching transistor 202 needs to be periodically turned on/off.
  • the periodic turning on/off is called pulse width adjustment control. Because the second switch transistor 202 and the fourth switch transistor 204 are in complementary conduction, that is, when the second switch transistor 202 is on, the fourth switch transistor 204 is off, so the fourth switch transistor 204 is also under pulse width adjustment control. At this time, the first switch tube 201 is always on. Because the first switch tube 201 and the third switch tube 203 are in complementary conduction, the third switch tube 203 is always off.
  • the output port 13 can output a voltage greater than the input port 11 when the second switch 202 is turned on/off.
  • the first switching transistor 201 or the second switching transistor 202 needs to be controlled by pulse width adjustment.
  • This sudden change in the pulse width adjustment control may cause the output port 13 to The output voltage of the switch suddenly changes, so that the output port 13 cannot provide a normal voltage, so it is necessary to use the following method to control the first switch transistor 201 and the second switch transistor 202 to further reduce the sudden change.
  • the first switching tube 201 and the second switching tube 202 can be controlled by pulse width adjustment at the same time.
  • the energy storage inductor 15 is charged, and the output voltage is zero. Then the first switching tube 201 and the second switching tube 202 are turned off. At this time, the energy storage inductor 15 discharges the output port 13.
  • This control method does not have the advantage of a wide adjustment range of time-sharing control duty cycle, but its switching between voltage increase and decrease is very smooth.
  • the above-mentioned on/off switching of the first switching tube 201, the second switching tube 202, the third switching tube 203 and the fourth switching tube 204 is realized through the control unit 14, and the control unit 14 obtains the output voltage and the input voltage to control the first switching tube 201 , the second switching tube 202 , the third switching tube 203 and the fourth switching tube 204 .
  • this article will describe the specific circuit principles and topology of the control unit 14 in detail. In the control unit 14, the specific functions of some modules have been explained. The technical knowledge in the art can be based on the technology of this article. Enlightenment, equivalent replacement of conventional technology or existing technology, but they should all fall within the protection scope of this article. As for conventional technology, this article will not elaborate here.
  • the control unit 14 includes a sampling comparison module 21 and a driving module 22 .
  • the sampling comparison module 21 is used to collect the reference voltage and the output voltage of the output port 13 to generate a voltage loop signal, and is used to collect the reference voltage and the input voltage of the input port 11 and generate a boost signal or a buck signal.
  • the driving module 22 is used to receive a voltage loop signal, a boost signal or a buck signal, and generate a driving signal to drive the first switching tube 201, the second switching tube 202, the third switching tube 203 and the fourth switching tube 204 to turn on or off. Deadline.
  • the sampling comparison module 21 can receive a reference voltage, an input voltage and an output voltage. Through comparison, the sampling comparison module 21 can output the voltage loop signal and the boost signal at the same time, or output the voltage loop signal and the buck signal at the same time.
  • the driving module 22 receives one of the boost signal and the buck signal and the voltage loop signal respectively, and drives the first switching tube 201, the second switching tube 202, the third switching tube 203 and the fourth switching tube 204 to be turned on or off to achieve Reduce or increase the output voltage.
  • the driving module 22 includes a first waveform comparison component 34 and a second waveform comparison component 35 .
  • the first waveform comparison component 34 is used to compare the voltage loop signal and the boost signal to drive the first switching tube 201 and the third switching tube 203;
  • the second waveform comparison component 35 is used to compare the voltage loop signal and the buck signal to drive the second switch tube 202 and the fourth switch tube 204 .
  • the voltage loop signal is used to control the duty cycle of the pulse width adjustment control of the first switching tube 201 or the second switching tube 202
  • the boost signal is used to send to the first switching tube 201 and the third switching tube 203 to
  • the buck signal is used to send to the second switch transistor 202 and the fourth switch transistor 204 to realize the step-down function of the output voltage.
  • the sample comparison module 21 includes a first category comparison component 31 .
  • the first type comparison component 31 is used to collect the reference voltage and the output voltage to generate a voltage loop signal.
  • the sample comparison module 21 includes a second category comparison component 32 .
  • the second type comparison component 32 is used to collect the reference voltage and the amplified input voltage, and generate a boost signal.
  • the amplified input voltage may be, for example, a larger voltage than a conventional input voltage, which The voltage is the input voltage that has not been amplified or reduced. For example, it can be a voltage range or a fixed value. In the case of a fixed value, when the input voltage is higher than the value, the input voltage is determined to be the amplified input voltage. If it is a voltage value interval, when the input voltage is higher than the maximum value of the voltage value interval, the input voltage is determined to be an amplified input voltage.
  • the sample comparison module 21 includes a third category comparison component 33 .
  • the third category comparison component 33 is used to collect the reference voltage and the reduced input voltage, and generate a buck signal. It should be noted that the reduced input voltage may be, for example, a voltage smaller than the conventional input voltage.
  • the third type comparison component 33 is configured to receive the reference voltage and the reduced input voltage, and send a buck signal to the second waveform comparison component 35 .
  • the first waveform comparison component 34 is used to drive the first switching tube 201 and the third switching tube 203 .
  • the second waveform comparison component 35 is used to drive the second switching transistor 202 and the fourth switching transistor 204 .
  • the voltage loop signal is used to control the duty cycle of the pulse width adjustment control of the first switching tube 201 or the second switching tube 202
  • the boost signal is used to send to the first switching tube 201 and the third switching tube 203 to
  • the buck signal is used to send to the second switch transistor 202 and the fourth switch transistor 204 to realize the step-down function of the output voltage.
  • the reference voltage can be adjusted according to the input voltage, which is not limited in this article.
  • the output terminal and the input terminal of the first type operator 401 and the third type operator 403 can be Set the PI adjustment combination.
  • the duty cycle of the second switching transistor 202 can be gradually increased or decreased, and at this time, the duty cycle of the first switching transistor 201 is changed synchronously to ensure the stability of the output voltage.
  • the specific circuit is shown in Figure 4.
  • the first category comparison component 31 (shown in Figure 3) includes a first category operator 401, a first resistor 101, a second resistor 102, a third resistor 103 and a first capacitor 301 .
  • One end of the first resistor 101 is connected to the output voltage, and the other end is connected to the inverting input end of the first type operator 401 .
  • One end of the second resistor 102 is connected to the reference voltage, and the other end is connected to the positive input end of the first type operator 401 .
  • the output terminal of the first type operator 401 outputs a voltage loop signal and is connected to one end of the first capacitor 301,
  • the other end of the first capacitor 301 is connected to one end of the third resistor 103, and the other end of the third resistor 103 is connected to the inverting input end.
  • the third resistor 103 and the first capacitor 301 form a PI adjustment structure.
  • the output end of the first type operator 401 can output a voltage loop signal to realize control of the first switch tube 201 (such as (shown in Figure 1) and the control of the second switch tube 202 (shown in Figure 1).
  • the second category comparison component 32 (shown in FIG. 3 ) includes a second category operator 402, a fourth resistor 104, a fifth resistor 105, a sixth resistor 106, a seventh resistor 107 and a second capacitor 302.
  • One end of the fourth resistor 104 is connected to the amplified input voltage, and the other end is connected to the positive input end of the second type operator 402 .
  • One end of the fifth resistor 105 is connected to the reference voltage, and the other end is connected to the inverting input end of the second type operator 402 .
  • the output end of the second type operator 402 outputs a boost signal and is connected to one end of the sixth resistor 106.
  • the other end of the sixth resistor 106 is connected to VCC.
  • the power input end of the second type operator 402 is connected to VCC.
  • One end of the seventh resistor 107 is connected to one end of the sixth resistor 106, the other end of the seventh resistor 107 is connected to one end of the second capacitor 302, and the other end of the second capacitor 302 is connected to ground.
  • the seventh resistor 107 and the second capacitor 302 form a buffer.
  • the seventh resistor 107 can reduce the input voltage to implement a protection circuit.
  • the second capacitor 302 can output the second type operator 402.
  • the waveform is filtered, and the output end of the second category operator 402 can output a boost signal to control the first switch tube 201 and the third switch tube 203 .
  • the third category comparison component 33 (shown in FIG. 3 ) includes a third category operator 403 , an eighth resistor 108 , a ninth resistor 109 , a tenth resistor 110 and a third capacitor 303 .
  • One end of the eighth resistor 108 is connected to the reduced input voltage, and the other end is connected to the positive input end of the third category operator 403 .
  • One end of the ninth resistor 109 is connected to the reference voltage, and the other end is connected to the inverting input end of the third category operator 403 .
  • the output end of the third category operator 403 outputs a buck signal and is connected to one end of the third capacitor 303.
  • the other end of the third capacitor 303 is connected to one end of the tenth resistor 110.
  • the other end of the tenth resistor 110 is connected to the third category
  • the inverting input terminal of the operator 403 is connected.
  • the tenth resistor 110 and the third capacitor 303 form a PI adjustment structure.
  • the output terminal of the third type operator 403 can output a buck signal to control the second switching tube 202 and the fourth switching tube 204 .
  • the first waveform comparison component 34 (shown in FIG. 3 ) includes an eleventh resistor 111 , a twelfth resistor 112 , a thirteenth resistor 113 , a first waveform comparator 404 , a first driver 501 , a third driver 503 and a third resistor 111 .
  • One end of the twelfth resistor 112 receives the sawtooth wave, and the other end is connected to the first waveform.
  • the inverting input of comparator 404 is connected.
  • the forward voltage input terminal of the first waveform comparator 404 is connected to VCC through the thirteenth resistor 113, and the reverse voltage input terminal of the first waveform comparator 404 is connected to the second waveform comparator 405 through a synchronizer.
  • the output terminal of the first waveform comparator 404 is connected to one terminal of the first driver 501 and one terminal of the first inverter 601 respectively.
  • the first inverter 601 is connected to one end of the third driver 503 .
  • the other end of the first driver 501 is connected to the gate of the first switch tube 201 .
  • the other end of the third driver 503 is connected to the gate of the third switch tube 203 .
  • an energy storage inductor 15 (as shown in Figure 1) and an energy storage resistor are used for buffering.
  • the energy storage capacitor 16 (as shown in Figure 1) is charged and discharged, and the voltage intersecting with the sawtooth wave gradually changes, and the duty cycle of the first switch tube 201 gradually increases or decreases.
  • the second switch tube 202 The duty cycle is still adjusted to ensure the stability of the output voltage.
  • the second waveform comparison component 35 (shown in FIG. 3 ) includes a fourteenth resistor 114 , a fifteenth resistor 115 , a sixteenth resistor 116 , a second waveform comparator 405 , a second driver 502 , a fourth driver 504 and a Two inverters 602.
  • One end of the fourteenth resistor 114 receives the voltage loop signal and the buck signal respectively, and the other end is connected to the forward input end of the second waveform comparator 405 .
  • One end of the fifteenth resistor 115 receives the sawtooth wave, and the other end is connected to the inverting input end of the second waveform comparator 405 .
  • the forward voltage input terminal of the second waveform comparator 405 is connected to VCC, and the reverse voltage input terminal of the second waveform comparator 405 is connected to the first waveform comparison component 34 through a synchronizer.
  • the output terminal of the second waveform comparator 405 is connected to one terminal of the sixteenth resistor 116, and the other terminal of the sixteenth resistor 116 is connected to VCC, one terminal of the second driver 502 and one terminal of the second inverter 602 respectively.
  • the second inverter 602 is connected to one end of the fourth driver 504 .
  • the other end of the second driver 502 is connected to the second switch tube 202 .
  • the other end of the fourth driver 504 is connected to the fourth switch tube 204 .
  • first inverter 601 and second inverter 602 complementary conduction is achieved, and the corresponding potential is: when the first waveform comparator 404 sends a high level, the first switch tube 201 is turned on, and After the high level passes through the first inverter, a low level is generated, and then the low level is sent to the third switch transistor 203, causing the third switch transistor 203 to turn off. Therefore, complementary conduction of the first switching transistor 201 and the third switching transistor 203 can be achieved through the first inverter.
  • the complementary conduction of the second switch transistor 202 and the fourth switch transistor 204 is also the above-mentioned process. In order to reduce the length, the details will not be described in the embodiment of this article.
  • the sampling comparison module An isolation module 23 is also provided between the block 21 and the drive module 22 .
  • the isolation module 23 is used to prevent the output voltage from flowing back to the input port 11 .
  • the isolation module 23 includes a first isolation component.
  • the first isolation component includes a first isolator 901, a first diode 801, a second diode 802, a seventeenth resistor 117 and an eighteenth resistor 118.
  • One end of the first isolator 901 is connected to the output end of the first type operator 401 , and the other end is connected to the anode of the first diode 801 .
  • the cathode of the first diode 801 is connected to one end of the seventeenth resistor 117 .
  • the other end of the seventeenth resistor 117 is connected to one end of the eighteenth resistor 118 .
  • the other end of the eighteenth resistor 118 is connected to ground.
  • the anode of the second diode 802 is connected to the other end of the seventh resistor 107 .
  • the cathode of the second diode 802 is connected to one end of the twelfth resistor 112 .
  • the isolation module 23 may also comprise a second isolation component, for example.
  • the second isolation component includes a second isolator 902, a third diode 803, a fourth diode 804, a nineteenth resistor 119 and a twentieth resistor 120.
  • One end of the second isolator 902 is connected to the output end of the first type operator 401 , and the other end is connected to the anode of the third diode 803 .
  • the cathode of the third diode 803 is connected to one end of the nineteenth resistor 119 .
  • the other end of the nineteenth resistor 119 is connected to one end of the twentieth resistor 120 .
  • the other end of the twentieth resistor 120 is connected to ground.
  • the cathode of the fourth diode 804 is connected to one end of the third capacitor 303 .
  • the anode of the fourth diode 804 is connected to one end of the fourteenth resistor 114 .
  • Figure 6 provides a control method for combined control of a voltage converter, including:
  • Step 601 When receiving an instruction to make the output voltage of the output port 13 lower than the input voltage of the input port 11, determine the voltage range in which the current output voltage is located. If the output voltage is lower than the first threshold, control the first switch 201 The second switching tube 202 is controlled to be turned off by periodic on/off, so that the output voltage is reduced, where the degree of reduction is determined according to the on/off cycle of the first switching tube 201 .
  • Step 602 When receiving an instruction to make the output voltage of the output port 13 higher than the input voltage of the input port 11, determine the voltage range in which the current output voltage is located. If the output voltage is higher than the second threshold, control the second switch 202. Periodically turning on/off controls the first switching transistor 201 to turn on, so as to increase the output voltage, where the degree of improvement is determined according to the on/off cycle of the second switching transistor 202 .
  • the on/off period of the first switching tube is determined according to the voltage loop signal, and the degree of reduction is determined according to the duty cycle of the voltage loop signal.
  • the on/off period of the second switch tube is determined according to the voltage loop signal, and the degree of improvement is determined according to the duty cycle of the voltage loop signal.
  • the voltage loop signal is similar to a square wave signal.
  • the frequency of the square wave signal is certain, it can be changed by By changing the duty cycle, that is, taking 0-2 seconds as a cycle, the high level can be maintained for 1.5 seconds, the low level can be maintained for 0.5 seconds, etc. within 2 seconds. In this way, the output voltage can be changed.
  • the maximum value of the output voltage is 100V.
  • the duty cycle of the square wave signal is 100%, a voltage of 100V can be output.
  • the duty cycle of the square wave signal is 50% , can output 50V voltage, etc.
  • the total output voltage is 30V
  • the duty cycle corresponding to the output of 2-22V is 2/30-22/30, that is, the duty cycle is about 7%--73%.
  • the output voltage can be obtained and the voltage range in which the output voltage is located can be determined.
  • the output voltage can be reduced through the cooperation of the first switch tube 201 and the second switch tube 202 .
  • the output voltage can be increased through the cooperation of the first switching transistor 201 and the second switching transistor 202 .
  • the degree of reduction or improvement can be determined according to the formula.
  • voltage reduction that is, when the output voltage is lower than the input voltage
  • the output voltage can be adjusted by adjusting the duty ratio of the first switching tube 201 .
  • determining the voltage interval in which the current output voltage is located further includes:
  • This article uses simultaneous on and off control.
  • the voltage needs to be boosted from below the first threshold to above the second threshold, It is necessary to make the first switching tube 201 and the second switching tube 202 switch on and off at the same time, so that the energy storage inductor 15 in the converter can store or discharge energy, and the sudden change of the output voltage can be alleviated through the buffering of the LC circuit.
  • the degree of increase/decrease of the output voltage is determined according to the duty cycle of the voltage loop signal, which further includes: if the duty cycle of the voltage loop signal is less than fifty percent, the output voltage is reduced, and if the duty cycle of the voltage loop signal When the duty cycle of the signal is greater than 50%, the output voltage increases.
  • a third embodiment of the present application provides a power supply provided with the above-mentioned combined control voltage converter.
  • An embodiment of the fourth aspect of the present application provides a new energy vehicle, which is equipped with the above-mentioned power supply.
  • a unit described as a separate component may or may not be physically separate.
  • a component shown as a unit may or may not be a physical unit, that is, it may be located in one place, or it may be distributed to multiple network units.

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Abstract

本文提供了一种组合控制电压变换器、控制方法、电源和新能源汽车，变换器包括：第一开关管、第二开关管、与第一开关管互补导通的第三开关管、与第二开关管互补导通的第四开关管、储能电感、储能电容及控制单元，控制单元用于获取输出端口的输出电压，并与参考电压进行比较，导通/截止第一开关管或者第二开关管，以实现对输出端口的输出电压的升压或者降压。另外的，本方案所采用的器件较少，并且没有在集成电路中设置较大的高压二极管，降低了电压变换器的体积以及制作成本。

Description

一种组合控制电压变换器、控制方法、电源和新能源汽车
相关申请
本申请要求于2022年05月06日递交的申请号为202210486689.8的中国发明专利申请的优先权，并引用上述专利申请公开的全部内容作为本申请的一部分。
技术领域
本申请涉及可调直流电源技术领域，尤其是一种组合控制电压变换器、控制方法、电源和新能源汽车。
背景技术
电源是直流充电桩(DC Wallbox)重要的组成部分，通常情况下电源不仅要求其具有效率高、体积小、功率大等特点，还要求有良好的动态性能和提供输出电压宽且范围可调的能力。当输入电压可调范围有限，要求输出电压宽且范围可调时，就会面临输出电压既要升压又要降压的需求。
Buck和Boost变换器分别是降压和升压变换器中结构最简单的两种，而将这两种电路进行结合时，往往电路结构存在较多的二极管和电容，导致电路的体积较大，且高压二极管的造价较高，无法满足产品要求。
因此需要一种电路可以解决现有技术中的电压变换器功能单一和传统的升降压结构成本过高，电路结构和控制方式复杂的问题。
发明内容
针对现有技术的上述问题，本文的目的在于，提供一种组合控制电压变换器、控制方法、电源和新能源汽车，以解决现有技术中的电压变换器功能单一和传统的升降压结构成本过高，电路结构和控制方式复杂的问题。
为了解决上述技术问题，本文的具体技术方案如下。
本申请第一方面的实施例提供一种组合控制电压变换器，包括：升降压电路，所述升降压电路设于输入端口和输出端口之间；所述升降压电路包括第一开关管、第二开关管、与所述第一开关管互补导通的第三开关管、与所述第二开关管互补导通的第四开关管、储能电感、储能电容及控制单元；所述第一开关管的漏极与所述输入端口 的正极相连，所述第一开关管的源极与所述第三开关管的漏极相连，所述第三开关管的源极与所述输入端口的负极相连；所述储能电感的一端与所述第三开关管的漏极相连，另一端与所述第二开关管的漏极相连，所述第二开关管的源极与所述第三开关管的源极相连；所述第四开关管的漏极与所述第二开关管的漏极相连，所述第四开关管的源极与所述储能电容的一端相连；所述控制单元分别与所述输入端口、所述第一开关管、所述第二开关管、所述第三开关管和所述第四开关管的栅极相连。
本申请第二方面的实施例提供一种根据任一项所述的组合控制电压变换器的控制方法，包括：当接收到令输出端口的输出电压低于输入端口的输入电压的指令时，确定当前所述输出电压所在的电压区间，若所述输出电压低于第一阈值，则控制第一开关管周期性导通/截止，控制第二开关管持续关断，以使所述输出电压降低；当接收到令所述输出电压高于所述输入电压的指令时，确定当前所述输出电压所在的电压区间，若所述输出电压高于第二阈值，则控制所述第二开关管周期性导通/截止，控制所述第一开关管导通，以使所述输出电压提升；其中，所述第一开关管的导通/截止的周期根据电压环信号确定，降低的程度根据所述电压环信号的占空比确定；所述第二开关管的导通/截止的周期根据所述电压环信号确定，提升的程度根据所述电压环信号的占空比确定。
本申请第三方面的实施例提供一种电源，所述电源设有任一项所述的组合控制电压变换器。
本申请第四方面的实施例提供一种新能源汽车，所述新能源汽车设有所述的电源。
采用上述技术方案，实现了在电源的输入端口和输出端口之间设置升降压电路，升降压电路包括第一开关管、第二开关管、与第一开关管互补导通的第三开关管、与第二开关管互补导通的第四开关管、储能电感、储能电容及控制单元，通过控制单元获取输出端口的电压与输入端口的电压相比较，进而控制第一开关管、第二开关管、第三开关管和第四开关管导通、截止或者周期性导通截止的方式，实现对输出端口的输出电压的升压或者降压。另外的，本方案所采用的器件较少，并且没有在集成电路中设置较大的高压二极管，降低了电压变换器的体积以及制作成本。
为让本文的上述和其他目的、特征和优点能更明显易懂，下文特举较佳实施例，并配合所附图式，作详细说明如下。
附图说明
为了更清楚地说明本文实施例或现有技术中的技术方案，下面将对实施例或现有技术描述中所需要使用的附图作简单地介绍。
图1示出了本文实施例一种组合控制电压变换器的电路的示意图。
图2示出了本文实施例控制单元示意图。
图3示出了本文实施例控制单元详细示意图。
图4示出了本文实施例控制单元电路图。
图5示出了本文实施例隔离模块示意图。
图6示出了本文实施例一种组合控制电压变换器的控制方法的示意图。
图7示出了本文实施例一种组合控制电压变换器的控制方法的缓冲方法示意图。
具体实施方式
下面将结合本文实施例中的附图，对本文实施例中的技术方案进行清楚、完整地描述。
本申请第一方面的实施例提供如图1所示一种组合控制电压变换器的电路，包括：升降压电路12，升降压电路12设于输入端口11和输出端口13之间。升降压电路12包括第一开关管201、第二开关管202、与第一开关管201互补导通的第三开关管203、与第二开关管202互补导通的第四开关管204、储能电感15、储能电容16及控制单元14。第一开关管201的漏极与输入端口11的正极相连，第一开关管201的源极与第三开关管203的漏极相连，第三开关管203的源极与输入端口11的负极相连。储能电感15的一端与第三开关管203的漏极相连，另一端与第二开关管202的漏极相连，第二开关管202的源极与第三开关管203的源极相连。第四开关管204的漏极与第二开关管202的漏极相连，第四开关管204的源极与储能电容16的一端相连。控制单元14分别与输入端口11、第一开关管201、第二开关管202、第三开关管203和第四开关管204的栅极相连。
采用上述技术方案，实现了在电源的输入端口11和输出端口13之间设置升降压电路12，升降压电路12包括第一开关管201、第二开关管202、与第一开关管201互补导通的第三开关管203、与第二开关管202互补导通的第四开关管204、储能电感15、储能电容16及控制单元14，通过控制单元14获取输出端口13的电压与输入端口11的电压相比较，进而控制第一开关管201、第二开关管202、第三开关管203和第四开关管204导通、截止或者周期性导通截止的方式，实现对输出端口13的输出电压的升压或者降压。另外的，本方案所采用的器件较少，并且没有在集成电路中 设置较大的高压二极管，降低了电压变换器的体积以及制作成本。
作为本文的一个实施例，当输出端口13的输出电压高于输入端口11的输入电压的第一门限值且低于输入端口11的输入电压的第二门限值时，控制单元14控制第一开关管201和第二开关管202同步导通/截止。
当输出端口13的输出电压低于输入端口11的输入电压的第一门限值时，控制单元14控制第二开关管202截止，控制第一开关管201周期性导通/截止。
当输出端口13的输出电压高于输入端口11的输入电压的第二门限值时，控制单元14控制第一开关管201导通，控制第二开关管202周期性导通/截止。
需要说明的是，本文中的第一门限值可以是90％，第二门限值可以是110％。
在电压变换器进行工作时，输出电压相对于输入电压可能是升压或者是降压，在升压或者降压进行切换时，由于快速的切换不同开关管的导通/截止状态，会导致输出电压出现剧烈变化造成波动，这对于电压稳定性要求较高的电源、新能源汽车领域是无法接受的。所以在本文中，对于电压变换器进行控制时，为了避免上述情况，设置了一种缓冲的方式，在输出电压相对于输入电压有较大的升压时，或者输出电压相对于输入电压有较大的降压时，输出电压高于第二门限值或者输出电压低于第一门限值，可以采用分时调制。在输出电压相对于输入电压没有较大的升压或者降低时，输出电压高于第一门限值且低于第二门限值，可以采用同开同关的脉冲宽度调制。下面详细说明分时调制和同开同关的脉冲宽度调制。
在确定需要输出降压的输出电压时，需要对第一开关管201进行周期性导通/截止，为了方便说明将周期性导通/截止称为脉宽调节控制。因为第一开关管201与第三开关管203为互补导通，即第一开关管201导通时，第三开关管203截止，所以第三开关管203也为脉宽调节控制。此时第二开关管202一直关断，因为第二开关管202与第四开关管204为互补导通，所以第四开关管204一直导通，那么在第一开关管201导通时，输入电压的一部分电压输入至储能电感15，一部分通过第四开关管204输入到输出端口13，显然，输出端口13无法得到全部的输入电压，那么输出电压相对于输入电压来说，是降压。而在第一开关管201截止时，储能电感15相当于电源，向输出端口13输入电压，以使第一开关管201在截止时，输出端口13还能输出电压。但是根据电路原理，储能电感15的电压不可能大于输入端口11的电压，所以输出端口13得到的输入电压同样相对于输入端口11的输入电压来说是降低了。所以通过上述过程，实现了第一开关管201在导通/截止时，输出端口13都会输出相对于输入电压降低后的电压。
在本文中“*”为乘法运算符号。
其中，输出电压与输入电压的关系符合Ui＝D1*Uo，D1为第一开关管201的占空比，Ui为输入电压，Uo为输出电压。从而通过调节第一开关管201导通或者截止的周期，实现了调节输出电压的大小。
在确定需要输出升压的输出电压时，需要对第二开关管202进行周期性导通/截止，为了方便说明将周期性导通/截止称为脉宽调节控制。因为第二开关管202与第四开关管204为互补导通，即第二开关管202导通时，第四开关管204截止，所以第四开关管204也为脉宽调节控制。此时第一开关管201一直导通，因为第一开关管201和第三开关管203为互补导通，所以第三开关管203一直截止，那么在第二开关管202导通时，输入电压输入至储能电感15，所以在第二开关管202导通时，输出端口13处输出电压为零。而在第二开关管202截止时，储能电感15相当于电源，向输出端口13输入电压，并且储能电容16同样也储能放电，所以输出端口13的输出电压相当于储能电感15和储能电容16共同作用的电压，所以输出端口13得到的输入电压同样相对于输入端口11的输入电压来说是提升了。所以通过上述过程，实现了第二开关管202在导通/截止时，输出端口13可以输出大于输入端口11的电压。
其中，输出电压与输入电压的关系符合Ui＝Uo/(1-D2)，D2为第二开关管202的占空比，Ui为输入电压，Uo为输出电压。从而通过调节第二开关管202的导通与截止的周期，实现了调节输出电压的大小。
通过上述过程，可以看出，在升压或者降压过程中，需要对第一开关管201或者第二开关管202进行脉宽调节控制，这种突然改变脉宽调节控制可能会令输出端口13的输出电压发生突变，以至于输出端口13无法提供正常的电压，所以需要使用下述方式，对第一开关管201和第二开关管202进行控制，来进一步削减突变。
在进行切换时，可以同时对第一开关管201和第二开关管202进行脉宽调节控制，在第一开关管201和第二开关管202导通时，储能电感15充电，输出电压为零。然后再令第一开关管201和第二开关管202截止，此时储能电感15对输出端口13放电，根据电感充电和放电的伏秒平衡，可以得到的是关系式是Ui＝D*Uo/(1-D)，D为第一开关管201和第二开关管202同时导通的占空比，Ui为输入电压，Uo为输出电压，可推导得到当D>0.5时，实现升压；D<0.5时，实现降压，这种控制方式不具备分时控制占空比调节范围宽的优点，但是其升降压之间的切换非常平滑。
作为本文的一个实施例，上述的第一开关管201、第二开关管202、第三开关管203和第四开关管204的导通/截止是通过控制单元14实现的，控制单元14获取输出 电压以及输入电压，以实现对第一开关管201、第二开关管202、第三开关管203和第四开关管204的控制。为了本领域技术人员可以更清楚的实施本方案，本文将详细的描述控制单元14的具体电路原理以及拓扑结构，在控制单元14中，一些模块的具体功能已经说明，本领域可以根据本文的技术启示，等效替代常规技术或者现有技术，但都理应属于本文的保护范围，对于常规技术，本文在此不再赘述。
如图2所示控制单元14示意图，控制单元14包括采样比较模块21和驱动模块22。采样比较模块21，用于采集参考电压和输出端口13的输出电压生成电压环信号，用于采集参考电压与输入端口11的输入电压并生成boost信号或buck信号。驱动模块22，用于接收电压环信号、boost信号或buck信号，生成驱动信号，以驱动第一开关管201、第二开关管202、第三开关管203和第四开关管204的导通或截止。
需要说明的是，采样比较模块21可以接收参考电压、输入电压和输出电压。通过比较，采样比较模块21可以同时输出电压环信号和boost信号，或者同时输出电压环信号和buck信号。
驱动模块22分别接收boost信号和buck信号中的一个和电压环信号，驱动第一开关管201、第二开关管202、第三开关管203和第四开关管204的导通或截止，以实现对输出电压的降低或者提升。
如图3所示，作为本文的一个实施例驱动模块22包括第一波形比较组件34和第二波形比较组件35。
第一波形比较组件34用于将电压环信号和boost信号进行比较，以驱动第一开关管201和第三开关管203；
第二波形比较组件35用于将电压环信号和buck信号进行比较，以驱动第二开关管202和第四开关管204。
需要说明的是，电压环信号用于控制第一开关管201或第二开关管202的脉宽调节控制的占空比，boost信号用于发送至第一开关管201和第三开关管203以实现输出电压的升压功能，buck信号用于发送至第二开关管202和第四开关管204以实现输出电压的降压功能。
作为本文的一个实施例，采样比较模块21包括第一类别比较组件31。第一类别比较组件31用于采集参考电压与输出电压，生成电压环信号。
作为本文的一个实施例，采样比较模块21包括第二类别比较组件32。第二类别比较组件32用于采集参考电压和放大的输入电压，并生成boost信号。需要说明的是，该放大的输入电压例如可以为对比于常规的输入电压较大的电压，该常规的输入 电压为未放大或缩小的输入电压，例如可以为一个电压数值区间或者一个固定的数值。在为一个固定的数值的情况下，在输入电压高于该数值时，确定该输入电压为放大的输入电压。若为一个电压数值区间的情况下，在输入电压高于该电压数值区间的最大值时，确定该输入电压为放大的输入电压。
作为本文的一个实施例，采样比较模块21包括第三类别比较组件33。第三类别比较组件33用于采集参考电压和缩小的输入电压，并生成buck信号。需要说明的是，该缩小的输入电压例如可以为对比于常规的输入电压较小的电压。
作为本文的一个实施例，如图3所示控制单元14详细示意图，采样比较模块21包括第一类别比较组件31、第二类别比较组件32、第三类别比较组件33。驱动模块22包括第一波形比较组件34、第二波形比较组件35。第一类别比较组件31用于接收输出端口13的输出电压与参考电压，并分别发送电压环信号至第一波形比较组件34和第二波形比较组件35。第二类别比较组件32用于接收参考电压和放大的输入电压，并发送boost信号至第一波形比较组件34。第三类别比较组件33用于接收参考电压和缩小的输入电压，并发送buck信号至第二波形比较组件35。第一波形比较组件34用于驱动第一开关管201和第三开关管203。第二波形比较组件35用于驱动第二开关管202和第四开关管204。
需要说明的是，电压环信号用于控制第一开关管201或第二开关管202的脉宽调节控制的占空比，boost信号用于发送至第一开关管201和第三开关管203以实现输出电压的升压功能，buck信号用于发送至第二开关管202和第四开关管204以实现输出电压的降压功能。
在本文中，参考电压可以根据输入电压进行调整，本文在此不做限定。
为了满足输出电压低于输入电压时，电压环信号与buck产生电压差，在电路工作异常的情况下，可以在第一类别运算器401和第三类别运算器403的输出端和输入端之间设置PI调节组合。通过这种方式，可以令第二开关管202的占空比逐渐增大或者减小，而此时第一开关管201的占空比同步的改变，以保证输出电压的稳定。具体电路如图4所示。
如图4所示控制单元14电路图，第一类别比较组件31(如图3所示)包括第一类别运算器401、第一电阻101、第二电阻102、第三电阻103和第一电容301。第一电阻101的一端与输出电压相连，另一端与第一类别运算器401的反向输入端相连。第二电阻102的一端与参考电压相连，另一端与第一类别运算器401的正向输入端相连。第一类别运算器401的输出端输出电压环信号，并与第一电容301的一端相连， 第一电容301的另一端与第三电阻103的一端相连，第三电阻103的另一端与反向输入端相连。
在上述第一类别运算器401中，第三电阻103和第一电容301组成了PI调节结构，第一类别运算器401的输出端可以输出电压环信号，以实现对第一开关管201(如图1所示)和第二开关管202(如图1所示)的控制。
第二类别比较组件32(如图3所示)包括第二类别运算器402、第四电阻104、第五电阻105、第六电阻106、第七电阻107和第二电容302。第四电阻104的一端与放大的输入电压相连，另一端与第二类别运算器402的正向输入端相连。第五电阻105的一端与参考电压相连，另一端与第二类别运算器402的反向输入端相连。第二类别运算器402的输出端输出boost信号，并与第六电阻106的一端相连，第六电阻106的另一端接VCC，第二类别运算器402的电源输入端与VCC相连。第七电阻107的一端与第六电阻106的一端相连，第七电阻107的另一端接第二电容302的一端，第二电容302的另一端接地。
在上述第二类别运算器402中，第七电阻107和第二电容302组成了缓冲器，第七电阻107可以降低输入电压以实现保护电路，第二电容302可以将第二类别运算器402输出的波形进行过滤，第二类别运算器402的输出端可以输出boost信号，以实现对第一开关管201和第三开关管203的控制。
第三类别比较组件33(如图3所示)包括第三类别运算器403、第八电阻108、第九电阻109、第十电阻110和第三电容303。第八电阻108的一端与缩小的输入电压相连，另一端与第三类别运算器403的正向输入端相连。第九电阻109的一端与参考电压相连，另一端与第三类别运算器403的反向输入端相连。第三类别运算器403的输出端输出buck信号，并与第三电容303的一端相连，第三电容303的另一端与第十电阻110的一端相连，第十电阻110的另一端与第三类别运算器403的反向输入端相连。
在上述第三类别运算器403中，第十电阻110和第三电容303组成了PI调节结构。第三类别运算器403的输出端可以输出buck信号，以实现对第二开关管202和第四开关管204的控制。
第一波形比较组件34(如图3所示)包括第十一电阻111、第十二电阻112、第十三电阻113、第一波形比较器404、第一驱动器501、第三驱动器503和第一反相器601。第十一电阻111的一端接收电压环信号和boost信号，另一端与第一波形比较器404的正向输入端相连。第十二电阻112的一端接收锯齿波，另一端与第一波形 比较器404的反向输入端相连。第一波形比较器404的正向电压输入端通过第十三电阻113连接VCC，第一波形比较器404的反向电压输入端通过同步器连接第二波形比较器405。第一波形比较器404的输出端分别与第一驱动器501的一端和第一反相器601的一端相连。第一反相器601与第三驱动器503的一端相连。第一驱动器501的另一端与第一开关管201的栅极相连。第三驱动器503的另一端与第三开关管203的栅极相连。
本文在切换开关管的导通或者截止时，为了实现平滑切换，采用储能电感15(如图1所示)和储能电阻来进行缓冲。切换时储能电容16(如图1所示)充放电，则与锯齿波交截的电压逐渐变化，第一开关管201的占空比逐渐增大或减小，此时第二开关管202的占空比仍然在调节以保证输出电压的稳定。
第二波形比较组件35(如图3所示)包括第十四电阻114、第十五电阻115、第十六电阻116、第二波形比较器405、第二驱动器502、第四驱动器504和第二反相器602。第十四电阻114的一端分别接收电压环信号和buck信号，另一端与第二波形比较器405的正向输入端相连。第十五电阻115的一端接收锯齿波，另一端与第二波形比较器405的反向输入端相连。第二波形比较器405的正向电压输入端连接VCC，第二波形比较器405的反向电压输入端通过同步器连接第一波形比较组件34。第二波形比较器405的输出端与第十六电阻116的一端相连，第十六电阻116的另一端分别与VCC、第二驱动器502的一端和第二反相器602的一端相连。第二反相器602与第四驱动器504的一端相连。第二驱动器502的另一端与第二开关管202相连。第四驱动器504的另一端与第四开关管204相连。
需要说明的是，同步器701实现第一波形比较器404和第二波形比较器405的反向电压输入端的电压同步，即保持第一波形比较器404和第二波形比较器405的GND同步。通过这种方式，可以令两个波形比较器的比较基准一致，可以更好的导通或者截止开关管。
通过上述的第一反相器601和第二反相器602，实现了互补导通，其对应的电位为，当第一波形比较器404发送高电平时，第一开关管201导通，并且高电平经过第一反相器后，产生低电平，随后低电平发送至第三开关管203，令第三开关管203截止。因此，通过第一反相器可以实现第一开关管201和第三开关管203的互补导通。
第二开关管202和第四开关管204的互补导通同样为上述过程，为了减少篇幅，本文实施例不再赘述。
进一步，如图5所示隔离模块23示意图，作为本文的一个实施例，采样比较模 块21与驱动模块22之间还设有隔离模块23。隔离模块23，用于防止输出电压倒灌至输入端口11。隔离模块23包括第一隔离组件。
第一隔离组件包括第一隔离器901、第一二极管801、第二二极管802、第十七电阻117和第十八电阻118。第一隔离器901一端与第一类别运算器401的输出端相连，另一端与第一二极管801的阳极相连。第一二极管801的阴极与第十七电阻117的一端相连。第十七电阻117的另一端与第十八电阻118的一端相连。第十八电阻118的另一端接地。第二二极管802的阳极与第七电阻107的另一端相连。第二二极管802的阴极与第十二电阻112的一端相连。隔离模块23例如还可以包括第二隔离组件。
第二隔离组件包括第二隔离器902、第三二极管803、第四二极管804、第十九电阻119和第二十电阻120。第二隔离器902一端与第一类别运算器401的输出端相连，另一端与第三二极管803的阳极相连。第三二极管803的阴极与第十九电阻119的一端相连。第十九电阻119的另一端与第二十电阻120的一端相连。第二十电阻120的另一端接地。第四二极管804的阴极与第三电容303的一端相连。第四二极管804的阳极与第十四电阻114的一端相连。
为了防止在降压时，输出电压倒灌，影响开关管的导通/截止周期，需要在电压环信号侧，加个具有隔离功能的电路，以提升电路的稳定性。
本申请第二方面的实施例如图6所示，提供了一种组合控制电压变换器的控制方法，包括：
步骤601、当接收到令输出端口13的输出电压低于输入端口11的输入电压的指令时，确定当前输出电压所在的电压区间，若输出电压低于第一阈值，则控制第一开关管201周期性导通/截止，控制第二开关管202关断，以使输出电压降低，其中降低的程度根据第一开关管201的导通/截止周期确定。
步骤602、当接收到令输出端口13的输出电压高于输入端口11的输入电压的指令时，确定当前输出电压所在的电压区间，若输出电压高于第二阈值，则控制第二开关管202周期性导通/截止，控制第一开关管201导通，以使输出电压提升，其中提升的程度根据第二开关管202的导通/截止周期确定。
第一开关管的导通/截止的周期根据电压环信号确定，降低的程度根据电压环信号的占空比确定。第二开关管的导通/截止的周期根据电压环信号确定，提升的程度根据电压环信号的占空比确定。
具体的讲，电压环信号类似为方波信号，在方波信号的频率一定时，可以通过改 变其占空比的大小，即以0-2秒为一个周期，可以在2秒内，令高电平维持1.5秒，令低电平维持0.5秒等。通过这种方式可以改变输出电压的大小，具体为，输出电压的最大值为100V，当方波信号的占空比为100％时，可以输出100V电压，当方波信号的占空比为50％时，可以输出50V电压等。
在本文中，输出电压总的输出是30V，那么输出2-22V对应的占空比为2/30-22/30，即占空比约为7％--73％。
通过上述控制方法，可以实现获取输出电压，以及确定输出电压所在的电压区间。当确定需要进行降压，且输出电压所在的电压区间低于第一阈值时，可以通过第一开关管201和第二开关管202的配合，降低输出电压。需要说明的是，在确定输出电压所在的电压区间低于第一阈值时，确定输出电压低于第一阈值。进一步，还可以在确定需要进行升压，且输出电压所在的电压区间高于第二阈值时，可以通过第一开关管201和第二开关管202的配合，提升输出电压。需要说明的是，在确定输出电压所在的电压区间高于第二阈值时，确定输出电压高于第一阈值。使用本文控制方法，令输出电压的升降压效果提升，满足了占空比调节的需求。
需要说明的是，降低或者提升的程度，可以根据公式确定，当需要进行降压时，即输出电压低于输入电压时，使用公式Ui＝D1*Uo，其中D1为第一开关管201的占空比，通过调节第一开关管201的占空比即可调节输出电压的大小。
当需要进行升压时，即输出电压大于输入电压时，使用公式Ui＝Uo/(1-D2)，其中D2为第二开关管202的占空比，通过调节第二开关管202的占空比即可调节输出电压的大小。
如图7所示一种组合控制电压变换器的控制方法的缓冲方法示意图，作为本文的一个实施例，确定当前输出电压所在的电压区间，进一步包括：
步骤701、若输出电压高于第一阈值，且低于第二阈值，则第一开关管201和第二开关管202周期性同步导通/截止，以使输出电压提升/降低；其中，输出电压提升/降低的程度，根据第二开关管202的同步导通/截止的周期性确定，输出电压提升/降低的程度根据电压环信号的占空比确定。
需要说明的是，在突然将输出电压由升压状态切换到降压状态时，由于不同开关管的占空比发生变化，会引起输出电压的剧烈波动，这对于集电子原件于一身的新能源汽车是无法接受的，所以需要在电压进行切换时，提出一种缓冲方法，以降低输出电压的波动。
本文中采用同开同关控制，当电压需要从第一阈值以下，升压到第二阈值以上时， 需要令第一开关管201和第二开关管202同开同关，令变换器中的储能电感15进行储能或者放能，通过LC电路的缓冲，缓解输出电压的突变。
作为本文的一个实施例，输出电压提升/降低的程度根据电压环信号的占空比确定，进一步包括：若电压环信号的占空比小于百分之五十，则输出电压降低，若电压环信号的占空比大于百分之五十，则输出电压提升。
需要说明的是，具体的变换方式，可以根据公式Ui＝D*Uo/(1-D)确定，D为第一开关管201和第二开关管202的共同的占空比。显然，当D>0.5时，实现升压；D<0.5时，实现降压。
本申请第三方面的实施例提供一种电源，电源设有如上述的组合控制电压变换器。
本申请第四方面的实施例提供一种新能源汽车，新能源汽车设有以上述的电源。
本领域普通技术人员可以意识到，结合本文中所公开的实施例描述的各示例的单元及算法步骤，能够以电子硬件、计算机软件或者二者的结合来实现，为了清楚地说明硬件和软件的可互换性，在上述说明中已经按照功能一般性地描述了各示例的组成及步骤。
作为分离部件说明的单元可以是或者也可以不是物理上分开的，作为单元显示的部件可以是或者也可以不是物理单元，即可以位于一个地方，或者也可以分布到多个网络单元上。

Claims (20)

  1. 一种组合控制电压变换器，其特征在于，包括：
    升降压电路，所述升降压电路设于输入端口和输出端口之间；
    所述升降压电路包括第一开关管、第二开关管、与所述第一开关管互补导通的第三开关管、与所述第二开关管互补导通的第四开关管、储能电感、储能电容及控制单元；
    所述第一开关管的漏极与所述输入端口的正极相连，所述第一开关管的源极与所述第三开关管的漏极相连，所述第三开关管的源极与所述输入端口的负极相连；
    所述储能电感的一端与所述第三开关管的漏极相连，另一端与所述第二开关管的漏极相连，所述第二开关管的源极与所述第三开关管的源极相连；
    所述第四开关管的漏极与所述第二开关管的漏极相连，所述第四开关管的源极与所述储能电容的一端相连；
    所述控制单元分别与所述输入端口、所述第一开关管、所述第二开关管、所述第三开关管和所述第四开关管的栅极相连。
  2. 根据权利要求1所述的组合控制电压变换器，其特征在于，所述控制单元配置为：
    当所述输出端口的输出电压低于所述输入端口的输入电压的第一门限值时，控制所述第二开关管截止，控制所述第一开关管周期性导通/截止；
    当所述输出端口的输出电压高于所述输入端口的输入电压的第二门限值时，控制所述第一开关管导通，控制所述第二开关管周期性导通/截止；
    当所述输出端口的输出电压高于所述输入端口的输入电压的第一门限值且低于所述输入端口的输入电压的第二门限值时，控制所述第一开关管和所述第二开关管同步导通/截止。
  3. 根据权利要求2所述的组合控制电压变换器，其特征在于，所述控制单元包括采样比较模块、驱动模块；
    所述采样比较模块，用于采集参考电压和所述输出电压并生成电压环信号，用于采集所述参考电压与所述输入电压并生成boost信号或buck信号；
    所述驱动模块，用于接收所述电压环信号、所述boost信号或所述buck信号并生成驱动信号，以驱动所述第一开关管、所述第二开关管、所述第三开关管和所述第四开关管的导通/截止。
  4. 根据权利要求3所述的组合控制电压变换器，其特征在于，所述驱动模块包括 第一波形比较组件和第二波形比较组件；
    所述第一波形比较组件用于将所述电压环信号和所述boost信号进行比较，以驱动所述第一开关管和所述第三开关管；
    所述第二波形比较组件用于将所述电压环信号和所述buck信号进行比较，以驱动所述第二开关管和所述第四开关管。
  5. 根据权利要求4所述的组合控制电压变换器，其特征在于，所述采样比较模块包括第一类别比较组件；
    所述第一类别比较组件用于采集所述参考电压与所述输出电压，并生成所述电压环信号。
  6. 根据权利要求5所述的组合控制电压变换器，其特征在于，所述采样比较模块包括第二类别比较组件；
    所述第二类别比较组件用于采集所述参考电压和放大的所述输入电压，并生成所述boost信号。
  7. 根据权利要求6所述的组合控制电压变换器，其特征在于，所述采样比较模块包括第三类别比较组件；
    所述第三类别比较组件用于采集所述参考电压和缩小的所述输入电压，并生成所述buck信号。
  8. 根据权利要求7所述的组合控制电压变换器，其特征在于，所述第一类别比较组件包括第一类别运算器、第一电阻、第二电阻、第三电阻和第一电容；
    所述第一电阻的一端与所述输出电压相连，另一端与所述第一类别运算器的反向输入端相连；
    所述第二电阻的一端与所述参考电压相连，另一端与所述第一类别运算器的正向输入端相连；
    所述第一类别运算器的输出端输出所述电压环信号，并与所述第一电容的一端相连，所述第一电容的另一端与所述第三电阻的一端相连，所述第三电阻的另一端与所述反向输入端相连。
  9. 根据权利要求8所述的组合控制电压变换器，其特征在于，所述第二类别比较组件包括第二类别运算器、第四电阻、第五电阻、第六电阻、第七电阻和第二电容；
    所述第四电阻的一端与放大的所述输入电压相连，另一端与所述第二类别运算器的正向输入端相连；
    所述第五电阻的一端与所述参考电压相连，另一端与所述第二类别运算器的反向 输入端相连；
    所述第二类别运算器的输出端输出所述boost信号，并与所述第六电阻的一端相连，所述第六电阻的另一端接VCC，所述第二类别运算器的电源输入端与所述VCC相连；
    所述第七电阻的一端与所述第六电阻的一端相连，所述第七电阻的另一端接所述第二电容的一端，所述第二电容的另一端接地。
  10. 根据权利要求9所述的组合控制电压变换器，其特征在于，所述第三类别比较组件包括第三类别运算器、第八电阻、第九电阻、第十电阻和第三电容；
    所述第八电阻的一端与缩小的所述输入电压相连，另一端与所述第三类别运算器的正向输入端相连；
    所述第九电阻的一端与所述参考电压相连，另一端与所述第三类别运算器的反向输入端相连；
    所述第三类别运算器的输出端输出所述buck信号，并与所述第三电容的一端相连，所述第三电容的另一端与所述第十电阻的一端相连，所述第十电阻的另一端与所述第三类别运算器的反向输入端相连。
  11. 根据权利要求10所述的组合控制电压变换器，其特征在于，所述第一波形比较组件包括第十一电阻、第十二电阻、第十三电阻、第一波形比较器、第一驱动器、第三驱动器和第一反相器；
    所述第十一电阻的一端接收所述电压环信号和所述boost信号，另一端与所述第一波形比较器的正向输入端相连；
    所述第十二电阻的一端接收锯齿波，另一端与所述第一波形比较器的反向输入端相连；
    所述第一波形比较器的正向电压输入端连接所述VCC，所述第一波形比较器的反向电压输入端通过同步器连接所述第二波形比较组件；
    所述第一波形比较器的输出端分别与所述第一驱动器的一端和所述第一反相器的一端相连；
    所述第一反相器与所述第三驱动器的一端相连；
    所述第一驱动器的另一端与所述第一开关管的栅极相连；
    所述第三驱动器的另一端与所述第三开关管的栅极相连。
  12. 根据权利要求11所述的组合控制电压变换器，其特征在于，所述第二波形比较组件包括第十四电阻、第十五电阻、第十六电阻、第二波形比较器、第二驱动器、 第四驱动器和第二反相器；
    所述第十四电阻的一端分别接收所述电压环信号和所述buck信号，另一端与所述第二波形比较器的正向输入端相连；
    所述第十五电阻的一端接收锯齿波，另一端与所述第二波形比较器的反向输入端相连；
    所述第二波形比较器的正向电压输入端连接VCC，所述第二波形比较器的反向电压输入端通过同步器连接所述第一波形比较组件；
    所述第二波形比较器的输出端与所述第十六电阻的一端相连，所述第十六电阻的另一端分别与所述VCC、所述第二驱动器的一端和所述第二反相器的一端相连；
    所述第二反相器与所述第四驱动器的一端相连；
    所述第二驱动器的另一端与所述第二开关管相连；
    所述第四驱动器的另一端与所述第四开关管相连。
  13. 根据权利要求12所述的组合控制电压变换器，其特征在于，
    所述采样比较模块与所述驱动模块之间还设有隔离模块；
    所述隔离模块，用于防止所述输出电压倒灌至所述输入端口。
  14. 根据权利要求13所述的组合控制电压变换器，其特征在于，所述隔离模块包括第一隔离组件，用于将所述第一类别比较组件和所述第二类别比较组件分别与所述第一波形比较组件隔离，所述第一隔离组件具体包括：第一隔离器、第一二极管、第二二极管、第十七电阻和第十八电阻；
    所述第一隔离器一端与所述第一类别运算器的输出端相连，另一端与所述第一二极管的阳极相连；
    所述第一二极管的阴极与所述第十七电阻的一端相连；
    所述第十七电阻的另一端与所述第十八电阻的一端相连；
    所述第十八电阻的另一端接地；
    所述第二二极管的阳极与所述第七电阻的另一端相连；
    所述第二二极管的阴极与所述第十一电阻的一端相连。
  15. 根据权利要求14所述的组合控制电压变换器，其特征在于，所述隔离模块包括第二隔离组件，用于将所述第二类别比较组件和所述第三类别比较组件分别与所述第二波形比较组件隔离，所述第二隔离组件具体包括：第二隔离器、第三二极管、第四二极管、第十九电阻和第二十电阻；
    所述第二隔离器一端与所述第一类别运算器的输出端相连，另一端与所述第三二 极管的阳极相连；
    所述第三二极管的阴极与所述第十九电阻的一端相连；
    所述第十九电阻的另一端与所述第二十电阻的一端相连；
    所述第二十电阻的另一端接地；
    所述第四二极管的阴极与所述第三电容的一端相连；
    所述第四二极管的阳极与所述第十四电阻的一端相连。
  16. 根据权利要求1-15任一项所述的组合控制电压变换器的控制方法，其特征在于，包括：
    当接收到令输出端口的输出电压低于输入端口的输入电压的指令时，确定当前所述输出电压所在的电压区间，若所述输出电压低于第一阈值，则控制第一开关管周期性导通/截止，控制第二开关管持续关断，以使所述输出电压降低；
    当接收到令所述输出电压高于所述输入电压的指令时，确定当前所述输出电压所在的电压区间，若所述输出电压高于第二阈值，则控制所述第二开关管周期性导通/截止，控制所述第一开关管导通，以使所述输出电压提升；
    其中，所述第一开关管的导通/截止的周期根据电压环信号确定，降低的程度根据所述电压环信号的占空比确定；
    所述第二开关管的导通/截止的周期根据所述电压环信号确定，提升的程度根据所述电压环信号的占空比确定。
  17. 根据权利要求16所述的组合控制电压变换器的控制方法，其特征在于，所述确定当前所述输出电压所在的电压区间，进一步包括：
    若所述输出电压高于所述第一阈值，且低于所述第二阈值，则控制所述第一开关管和所述第二开关管周期性同步导通/截止，以使所述输出电压提升/降低；
    其中，所述第二开关管周期性同步导通/截止根据所述电压环信号确定，所述输出电压提升/降低的程度根据所述电压环信号的占空比确定。
  18. 根据权利要求17所述的组合控制电压变换器的控制方法，其特征在于，所述输出电压提升/降低的程度根据所述电压环信号的占空比确定，进一步包括：
    若所述电压环信号的占空比小于百分之五十，则所述输出电压降低，若所述电压环信号的占空比大于百分之五十，则所述输出电压提升。
  19. 一种电源，其特征在于，所述电源设有如权利要求1-15任一项所述的组合控制电压变换器。
  20. 一种新能源汽车，其特征在于，所述新能源汽车设有如权利要求19所述的 电源。
PCT/CN2023/092230 2022-05-06 2023-05-05 一种组合控制电压变换器、控制方法、电源和新能源汽车 Ceased WO2023213292A1 (zh)

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