WO2022049720A1 - 電力変換装置および空気調和機 - Google Patents

電力変換装置および空気調和機 Download PDF

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Publication number
WO2022049720A1
WO2022049720A1 PCT/JP2020/033558 JP2020033558W WO2022049720A1 WO 2022049720 A1 WO2022049720 A1 WO 2022049720A1 JP 2020033558 W JP2020033558 W JP 2020033558W WO 2022049720 A1 WO2022049720 A1 WO 2022049720A1
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WO
WIPO (PCT)
Prior art keywords
switching
power
terminal
converter
power supply
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Ceased
Application number
PCT/JP2020/033558
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English (en)
French (fr)
Japanese (ja)
Inventor
啓介 植村
翔太朗 烏山
浩一 有澤
貴昭 ▲高▼原
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Mitsubishi Electric Corp
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Mitsubishi Electric Corp
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Filing date
Publication date
Application filed by Mitsubishi Electric Corp filed Critical Mitsubishi Electric Corp
Priority to CN202080103392.8A priority Critical patent/CN115956335A/zh
Priority to US18/007,106 priority patent/US20230231490A1/en
Priority to JP2022546814A priority patent/JP7278497B2/ja
Priority to PCT/JP2020/033558 priority patent/WO2022049720A1/ja
Publication of WO2022049720A1 publication Critical patent/WO2022049720A1/ja
Anticipated expiration legal-status Critical
Ceased legal-status Critical Current

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/12—Arrangements for reducing harmonics from AC input or output
    • H02M1/123—Suppression of common mode voltage or current
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/02—Conversion of AC power input into DC power output without possibility of reversal
    • H02M7/04—Conversion of AC power input into DC power output without possibility of reversal by static converters
    • H02M7/12—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M7/219—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a bridge configuration
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0009—Devices or circuits for detecting current in a converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/32—Means for protecting converters other than automatic disconnection
    • H02M1/325—Means for protecting converters other than automatic disconnection with means for allowing continuous operation despite a fault, i.e. fault tolerant converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/4233—Arrangements for improving power factor of AC input using a bridge converter comprising active switches
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using DC to AC converters or inverters
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/04—Modifications for accelerating switching
    • H03K17/042—Modifications for accelerating switching by feedback from the output circuit to the control circuit
    • H03K17/04206—Modifications for accelerating switching by feedback from the output circuit to the control circuit in field-effect transistor switches
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/16—Modifications for eliminating interference voltages or currents
    • H03K17/161—Modifications for eliminating interference voltages or currents in field-effect transistor switches
    • H03K17/165—Modifications for eliminating interference voltages or currents in field-effect transistor switches by feedback from the output circuit to the control circuit
    • F—MECHANICAL ENGINEERING; LIGHTING; HEATING; WEAPONS; BLASTING
    • F04—POSITIVE - DISPLACEMENT MACHINES FOR LIQUIDS; PUMPS FOR LIQUIDS OR ELASTIC FLUIDS
    • F04B—POSITIVE-DISPLACEMENT MACHINES FOR LIQUIDS; PUMPS
    • F04B35/00—Piston pumps specially adapted for elastic fluids and characterised by the driving means to their working members, or by combination with, or adaptation to, specific driving engines or motors, not otherwise provided for
    • F04B35/04—Piston pumps specially adapted for elastic fluids and characterised by the driving means to their working members, or by combination with, or adaptation to, specific driving engines or motors, not otherwise provided for the means being electric
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/12—Arrangements for reducing harmonics from AC input or output
    • H02M1/126—Arrangements for reducing harmonics from AC input or output using passive filters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/4283—Arrangements for improving power factor of AC input by adding a controlled rectifier in parallel to a first rectifier feeding a smoothing capacitor
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M5/00—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases
    • H02M5/40—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into DC
    • H02M5/42—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into DC by static converters
    • H02M5/44—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into DC by static converters using discharge tubes or semiconductor devices to convert the intermediate DC into AC
    • H02M5/453—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into DC by static converters using discharge tubes or semiconductor devices to convert the intermediate DC into AC using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M5/458—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into DC by static converters using discharge tubes or semiconductor devices to convert the intermediate DC into AC using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M5/4585—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into DC by static converters using discharge tubes or semiconductor devices to convert the intermediate DC into AC using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only having a rectifier with controlled elements
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K2217/00—Indexing scheme related to electronic switching or gating, i.e. not by contact-making or -breaking covered by H03K17/00
    • H03K2217/0027—Measuring means of, e.g. currents through or voltages across the switch
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K2217/00—Indexing scheme related to electronic switching or gating, i.e. not by contact-making or -breaking covered by H03K17/00
    • H03K2217/0036—Means reducing energy consumption

Definitions

  • This disclosure relates to a power converter and an air conditioner that convert AC power into DC power.
  • Patent Document 1 discloses a technique for stopping switching of a converter during a period when the power supply current is zero.
  • the power factor improving converter is provided with a control for reducing the duty to 1 in the vicinity of the power supply current near zero cross, and Patent Document 1 is no exception.
  • Patent Document 1 in order to suppress noise, switching of the power factor improving converter is stopped when the power supply current is near zero cross. Therefore, in the method of Patent Document 1, two contradictory controls, that is, the control that brings the original duty closer to 1 and the control that stops switching for noise suppression, are incorporated, and it is difficult to achieve both noise suppression and control stability at the same time. There was a problem that it was.
  • the present disclosure has been made in view of the above, and an object of the present disclosure is to obtain a power conversion device capable of achieving both noise suppression and control stability.
  • the power conversion device has four switching elements configured in a full bridge shape, and AC power supplied from an AC power source is converted into DC power.
  • a converter to be converted a reactor provided between the AC power supply and the converter, a smoothing capacitor connected to both ends of the DC terminal of the converter, an AC voltage detector to detect the AC voltage output from the AC power supply, and a reactor. It is provided with an alternating current detector that detects the current flowing through the device and a control circuit that controls the switching operation of the switching element.
  • the control circuit is a GN between the PL terminal between the P terminal, which is the DC terminal of the positive electrode of the converter, and one L terminal of the AC power supply, or the GN between the G terminal, which is the DC terminal of the negative electrode of the converter, and the other N terminal of the AC power supply.
  • the switching element is controlled between the terminals so as to suppress the potential fluctuation caused by the switching operation.
  • the power conversion device has the effect of achieving both noise suppression and control stability.
  • a diagram showing an example of a gate signal for a switching element when a switching element included in a converter of a power converter is switched in synchronization with an alternating current As a comparative example, a diagram showing each signal waveform and a waveform obtained by measuring leakage current when the switching element included in the converter of the power converter operates with the gate signal shown in FIG.
  • the figure which shows the waveform which measured each signal and leakage current when the switching element provided in the converter of the power conversion apparatus which concerns on Embodiment 1 operates with the gate signal shown in FIG.
  • FIG. 2 is a diagram showing a waveform obtained by measuring a leakage current when a power conversion device according to a second embodiment to which a first diode and a second diode are connected shown in FIG. 20 is recirculated by a low-side switching element in a power supply short-circuit mode.
  • FIG. 1 is a diagram showing a configuration example of the power conversion device 100 according to the first embodiment.
  • the power conversion device 100 shown in FIG. 1 includes a converter 2, a reactor 3, a smoothing capacitor 4, an AC voltage detector 5, an AC current detector 6, a DC voltage detector 7, and a control circuit 9. Be prepared.
  • FIG. 1 shows a state in which the AC power supply 1 and the load 10 are connected to the power conversion device 100.
  • the converter 2 includes two AC terminals as input terminals and two DC terminals as output terminals. Of the DC terminals included in the converter 2, the positive electrode terminal is a P terminal and the negative electrode terminal is a G terminal.
  • one L terminal of the AC power supply 1 and one terminal of the reactor 3 are connected, and the other terminal of the reactor 3 and one AC terminal of the converter 2 made of a semiconductor element are connected to each other to make an AC.
  • the other N terminal of the power supply 1 and the other AC terminal of the converter 2 are connected.
  • the reactor 3 is provided between the AC power supply 1 and the converter 2.
  • an AC voltage detector 5 for detecting a power supply voltage output from the AC power supply 1 and input to the converter 2, that is, an AC voltage Vac, is connected in parallel to both ends of the AC power supply 1.
  • An AC current detector 6 for detecting a power supply current output from the AC power supply 1 and input to the converter 2, that is, an AC current Iac, is connected in series between the AC power supply 1 and the converter 2.
  • the AC current detector 6 can detect the current flowing through the reactor 3 by detecting the AC current Iac.
  • the reactor 3 may be configured to be provided between the other N terminal of the AC power supply 1 and the other AC terminal of the converter 2.
  • the converter 2 converts the AC power supplied from the AC power supply 1 into DC power.
  • a smoothing capacitor 4, a load 10, and a DC voltage detector 7 are connected in parallel at both ends of the DC terminal, that is, between the PG terminals between the P terminal and the G terminal.
  • the DC voltage detector 7 detects the bus voltage Vdc, which is the DC voltage output from the converter 2.
  • the control circuit 9 acquires the values detected by the AC voltage detector 5, the AC current detector 6, and the DC voltage detector 7, that is, the detection result.
  • the control circuit 9 generates and outputs a control signal for controlling the semiconductor element of the converter 2 based on the detection results of the AC voltage detector 5, the AC current detector 6, and the DC voltage detector 7.
  • the power converter 100 controls the semiconductor element of the converter 2 based on the detection results of the AC voltage detector 5, the AC current detector 6, and the DC voltage detector 7 for the AC power input to the converter 2. , Power factor improvement, bus voltage control, etc.
  • the converter 2 includes four MOSFETs (Metal Oxide Semiconductor Field Effect Transistor) as the above-mentioned semiconductor elements, specifically, switching elements 21 to 24.
  • MOSFETs Metal Oxide Semiconductor Field Effect Transistor
  • the source of the switching element 21 and the drain of the switching element 22 are connected in series to the first arm, and the source of the switching element 23 and the drain of the switching element 24 are connected in series to the second arm. It is configured.
  • the first arm and the second arm are connected in parallel between the drains of the switching elements 21 and 23 and the sources of the switching elements 22 and 24.
  • One AC terminal is connected to the contact point between the switching element 21 and the switching element 22, and the other AC terminal is connected to the contact point between the switching element 23 and the switching element 24.
  • the converter 2 has four switching elements 21 to 24 configured in a full bridge shape.
  • the control circuit 9 controls the switching operation of the switching elements 21 to 24 as the control of the semiconductor element of the converter 2.
  • the semiconductor element used in the converter 2 is not limited to the MOSFET, and may be an IGBT (Insulated Gate Bipolar Transistor), a diode, or the like. Further, the semiconductor element used in the converter 2 may be a wide bandgap semiconductor such as GaN or SiC.
  • FIG. 2 is a diagram showing a configuration example in which a common mode choke coil 20 and a Y capacitor 30, which are noise filters, are connected to the power conversion device 100 according to the first embodiment.
  • the description of the AC voltage detector 5, the AC current detector 6, the DC voltage detector 7, and the control circuit 9 is omitted, but they are actually connected. It is assumed that there is.
  • the common mode choke coil 20 is connected between the AC power supply 1 and the reactor 3.
  • the common mode choke coil 20 has polarity, and both are connected so as to have the same polarity on the AC power supply 1 side and the load 10 side.
  • the common mode choke coil 20 has an effect of suppressing the imbalance of the potential between the two phases of the AC terminal of the converter 2. Therefore, the power conversion device 100 can obtain the effect of suppressing the potential indefiniteness caused by the imbalance of the potential of the converter 2 and reducing the noise by connecting the common mode choke coil 20.
  • the Y capacitor 30 is composed of a first capacitor 301 and a second capacitor 302.
  • the first capacitor 301 is connected to one L terminal of the AC power supply 1 and the E terminal which is the ground terminal of the AC power supply 1, and is connected in parallel to the AC power supply 1.
  • the second capacitor 302 is connected to the other N terminal of the AC power supply 1 and the E terminal which is the ground terminal of the AC power supply 1, and is connected in parallel to the AC power supply 1.
  • the Y capacitor 30 has an effect of suppressing the potential indefiniteness of the converter 2. Therefore, the power conversion device 100 has the effect of suppressing the potential indefiniteness of the converter 2 and reducing noise by connecting the Y capacitor 30.
  • the power conversion device 100 can obtain more effect of suppressing the potential indefiniteness of the converter 2 by connecting the common mode choke coil 20 and the Y capacitor 30.
  • the connection order and the number of connections of the common mode choke coil 20 and the Y capacitor 30 shown in FIG. 2 are examples, and are not limited thereto.
  • the power conversion device 100 can correspond to various configurations regarding the connection order and the number of connections of the common mode choke coil 20 and the Y capacitor 30.
  • the power conversion device 100 may be configured to include only the common mode choke coil 20 among the common mode choke coil 20 and the Y capacitor 30 shown in FIG. 2, or only the Y capacitor 30. It may be configured to include.
  • FIG. 3 is a diagram showing an example of a switching method of the switching elements 21 to 24 of the converter 2 included in the power conversion device 100 according to the first embodiment.
  • FIG. 3 shows the waveforms of the gate signals Vgs21 to Vgs24 for the AC voltage Vac, the AC current Iac, and the switching elements 21 to 24 in order from the top.
  • the switching elements 21 and 22 perform high-speed switching at a predetermined switching frequency during one cycle of the AC power supply 1 under the control of the control circuit 9.
  • the switching elements 23 and 24 perform low-speed switching based on the frequency of the AC power output from the AC power supply 1 under the control of the control circuit 9.
  • the switching elements 21 and 22 that perform high-speed switching have a faster switching speed than the switching elements 23 and 24 that perform low-speed switching, that is, the intervals between turning on and off are shorter.
  • the power conversion device 100 operates in the power supply short-circuit mode and the load power supply mode by switching the switching elements 21 and 22 at high speed, and can improve the power factor of the AC current Iac.
  • the gate signal Vgs for one switching element is the main, and the gate signal Vgs for the other switching element inverts and synchronizes the main gate signal Vgs. It is supposed to be.
  • one switching element that performs high-speed switching is inverting-synchronized to operate the other switching element, but the other switching element may not be inverting-synchronized.
  • FIG. 4 is a diagram showing an example of a current path when the switching elements 21 to 24 of the converter 2 included in the power conversion device 100 according to the first embodiment are switched by the gate signal Vgs shown in FIG.
  • the power conversion device 100 reverse-synchronizes the other switching element of the switching elements that perform high-speed switching. Therefore, the switching element 21 when the power supply polarity is positive in the load power supply mode and the switching element 22 when the power supply polarity is negative are the paths through which the current passes between the source and drain of the MOSFET. Become.
  • FIG. 5 is a diagram showing a configuration example of a control circuit 9 included in the power conversion device 100 according to the first embodiment.
  • the control circuit 9 includes a power supply current command value control unit 91, an on-duty control unit 92, a power supply voltage phase calculation unit 93, and a pulse generation unit 94.
  • the power supply current command value control unit 91 calculates the power supply current effective value command value Iac_rms * using the bus voltage Vdc detected by the DC voltage detector 7 and the preset bus voltage command value Vdc *.
  • the calculation of the power supply current effective value command value Iac_rms * is realized by controlling the difference between the bus voltage Vdc and the bus voltage command value Vdc * by proportional integration (PI: Proportional Integral).
  • PI Proportional Integral
  • the proportional integral control is an example, and the power supply current command value control unit 91 may adopt proportional (P: Proportional) control or proportional integral differential (PID: Proportional Industrial Differential) control instead of the proportional integral control. ..
  • the switching pattern select signal Tsw and the inverting synchronous rectification select signal Tsy are signals selected by the user of the power conversion device 100.
  • the power supply voltage phase calculation unit 93 generates the power supply voltage phase estimated value ⁇ ac using the AC voltage Vac detected by the AC voltage detector 5, and outputs the sinus value sin ⁇ ac of the power supply voltage phase estimated value ⁇ ac.
  • the on-duty control unit 92 is calculated by the sine value sin ⁇ ac of the power supply current effective value command value Iac_rms * output from the power supply current command value control unit 91 and the power supply voltage phase estimation value ⁇ ac output from the power supply voltage phase calculation unit 93.
  • the reference on-duty DTac is calculated using the power supply current instantaneous command value Iac * and the AC current Iac detected by the AC current detector 6.
  • the calculation of the reference on-duty DTac is realized by proportionally integrating and controlling the difference between the power supply current effective value command value Iac_rms * and the AC current Iac.
  • the proportional integral control is an example, and the on-duty control unit 92 may adopt proportional control or proportional integral differential control instead of the proportional integral control, as in the power supply current command value control unit 91.
  • FIG. 6 is a diagram showing an operation example of the power supply voltage phase calculation unit 93 included in the control circuit 9 of the power conversion device 100 according to the first embodiment. Note that FIG. 6 shows a waveform under ideal conditions that does not consider the delay due to control or the delay due to detection processing.
  • the power supply voltage phase estimated value ⁇ ac is 360 ° at the point where the AC voltage Vac, which is the power supply voltage, switches from the negative electrode property to the positive electrode property.
  • the power supply voltage phase calculation unit 93 detects a point at which the AC voltage Vac switches from the negative electrode property to the positive electrode property, and resets the power supply voltage phase estimated value ⁇ ac at this switching point, that is, returns it to zero.
  • a circuit for detecting the zero cross of the AC voltage Vac may be added to FIG. In any case, any method may be used as long as the phase of the AC voltage Vac can be detected.
  • FIG. 7 is a diagram showing a configuration example of a pulse generation unit 94 included in the control circuit 9 of the power conversion device 100 according to the first embodiment.
  • the pulse generation unit 94 includes an internal carrier generation unit 941, a comparator 942, a NOT circuit 943, and a pulse select unit 944.
  • the internal carrier generation unit 941 generates an internal carrier Car.
  • the pulse generation unit 94 includes the internal carrier generation unit 941, but when using a carrier from the outside, the pulse generation unit 94 may not have the internal carrier generation unit 941.
  • the comparator 942 acquires the reference on-duty DTac calculated by the on-duty control unit 92 and the internal carrier Car generated by the internal carrier generation unit 941.
  • the comparator 942 generates a high-speed switching signal S1 by comparing the magnitude relationship between the reference on-duty DTac and the internal carrier Car.
  • FIG. 8 is a diagram for explaining a method of generating a high-speed switching signal S1 and an inverting synchronous rectification signal S2 generated by the pulse generation unit 94 included in the control circuit 9 of the power conversion device 100 according to the first embodiment.
  • the reference on-duty DTac is input to the plus of the comparator 942, and the internal carrier Car is input to the minus of the comparator 942. Therefore, the comparator 942 outputs 1 as the high-speed switching signal S1 when the reference on-duty DTac> internal carrier Car, and outputs 0 as the high-speed switching signal S1 when the reference on-duty DTac ⁇ internal carrier Car.
  • 1 is a high active whose level is higher than 0, but 1 may be a low active whose level is lower than 0.
  • the comparator 942 outputs the high-speed switching signal S1 to the NOT circuit 943 and the pulse select unit 944.
  • the NOT circuit 943 outputs an inverting synchronous rectified signal S2 in which the high-speed switching signal S1 is inverted to the pulse select unit 944.
  • the inverting synchronous rectification signal S2 is a signal for performing an inverting synchronous rectification operation.
  • FIG. 9 is a first flowchart showing the operation of the pulse select unit 944 included in the control circuit 9 of the power conversion device 100 of the first embodiment.
  • FIG. 10 is a second flowchart showing the operation of the pulse select unit 944 included in the control circuit 9 of the power conversion device 100 of the first embodiment.
  • the pulse select unit 944 controls the first arm or the second arm to perform high-speed switching or low-speed switching, respectively.
  • the pulse select unit 944 controls the low-side switching element or the high-side switching element to switch between high-speed switching and low-speed switching every half cycle of the power supply frequency.
  • the inverting synchronous rectification select signal Tsy 0, the pulse select unit 944 controls so as not to perform the inverting synchronous rectifying operation.
  • the pulse select unit 944 controls to perform the inverting synchronous rectifying operation.
  • the pulse select unit 944 outputs the inverting synchronous rectification signal S2 to the switching element 21 as the gate signal Vgs.
  • the notation “pulse_21 ⁇ S2” means this control.
  • the pulse select unit 944 outputs the high-speed switching signal S1 to the switching element 22 as the gate signal Vgs.
  • the pulse select unit 944 outputs a signal of 0 at all times as the gate signal Vgs because it is always off to the switching element 23.
  • the notation “pulse_23 ⁇ 0” means this control.
  • the pulse select unit 944 always outputs the signal of 1 as the gate signal Vgs because it is always on to the switching element 24 (step S13).
  • the pulse select unit 944 outputs the high-speed switching signal S1 to the switching element 21 as the gate signal Vgs, outputs the inverting synchronous rectification signal S2 to the switching element 22, and always turns on the switching element 23, so that the signal is always 1. Is output, and a signal of 0 is always output because the switching element 24 is always turned off (step S14).
  • Vgs be pattern 1.
  • the gate signal Vgs of the pattern 1 the gate signal Vgs output by the control circuit 9 to the switching elements 21 to 24 of the converter 2, that is, the gate signal input from the control circuit 9 to the switching elements 21 to 24 of the converter 2.
  • Vgs becomes the gate signals Vgs21 to Vgs24 shown in FIG.
  • step S15: Yes as the gate signal Vgs, a signal of 0 is always output to the switching element 21 because it is always off, a high-speed switching signal S1 is output to the switching element 22, and the high-speed switching signal S1 is always turned off to the switching element 23.
  • a signal of 0 is output, and a signal of 1 is always output because the switching element 24 is always on (step S16).
  • step S11 No
  • step S15 No
  • the pulse select unit 944 gates.
  • the signal Vgs the high-speed switching signal S1 is output to the switching element 21, the signal of always 0 is output to the switching element 22 because it is always off, and the signal of always 1 is output to the switching element 23 because it is always on. Since it is always turned off at 24, a signal of 0 is always output (step S17).
  • Vgs be pattern 2.
  • the pulse select unit 944 outputs a signal so that the switching elements 21 and 22, which are the first arms, perform high-speed switching, but the switching elements 23, which are the second arms,
  • the gate signal Vgs may be output so that 24 performs high-speed switching.
  • the control circuit 9 outputs the gate signals Vgs21 to Vgs24 to the switching elements 21 to 24 of the converter 2, but the present invention is not limited to this.
  • the control circuit 9 outputs a drive pulse having a voltage value smaller than that of the gate signals Vgs21 to Vgs24 to the converter 2, and the converter 2 outputs a drive pulse from the drive pulse to the gate signal Vgs21 to Vgs21 in an internal circuit (not shown). Vgs24 may be generated.
  • Step S22: Yes as the gate signal Vgs, the inverting synchronous rectification signal S2 is output to the switching element 21, the high-speed switching signal S1 is output to the switching element 22, the signal of 0 is always output to the switching element 23, and the switching element is switched.
  • the signal of 1 is always output to 24 (step S23).
  • step S22: No the pulse select unit 944 gates.
  • the signal Vgs a signal of always 0 is output to the switching element 21
  • a signal of always 1 is output to the switching element 22
  • an inverting synchronous rectification signal S2 is output to the switching element 23
  • a high-speed switching signal S1 is output to the switching element 24.
  • Output step S24).
  • Vgs be pattern 3.
  • step S25: Yes as the gate signal Vgs, a signal of always 0 is output to the switching element 21, a high-speed switching signal S1 is output to the switching element 22, and a signal of always 0 is output to the switching element 23 for switching.
  • the signal of 1 is always output to the element 24 (step S26).
  • the pulse select unit 944 gates.
  • a signal of always 0 is output to the switching element 21
  • a signal of always 1 is output to the switching element 22
  • a signal of always 0 is output to the switching element 23
  • a high-speed switching signal S1 is output to the switching element 24.
  • Vgs be pattern 4.
  • the pulse select unit 944 outputs a gate signal Vgs so that the switching element on the low side of the converter 2 switches between high-speed switching and low-speed switching every half cycle of the power supply.
  • the pulse select unit 944 may output a gate signal Vgs so that the switching element on the high side of the converter 2 switches between high-speed switching and low-speed switching every half cycle of the power supply.
  • FIG. 11 is a diagram showing an example of a signal waveform in consideration of the dead time dt in the switching elements 21 to 24 included in the converter 2 of the power conversion device 100 according to the first embodiment.
  • each gate signal Vgs is set to be shorter on both sides of the on period by the dead time td.
  • the pulse select unit 944 is a flowchart for determining the switching pattern depending on whether the AC voltage Vac is larger or smaller than 0, but the switching pattern is not limited to this, and the switching pattern is determined by the AC current Iac. May be determined.
  • the pulse select unit 944 controls to turn on one of the switching elements that perform low-speed switching when the AC current Iac is at least in the current discontinuous mode.
  • FIG. 12 is a diagram showing an example of gate signals Vgs21 to Vgs24 in the case of pattern 2 output to the converter 2 by the control circuit 9 of the power conversion device 100 according to the first embodiment.
  • FIG. 13 is a diagram showing an example of gate signals Vgs21 to Vgs24 in the case of pattern 3 output to the converter 2 by the control circuit 9 of the power conversion device 100 according to the first embodiment.
  • FIG. 14 is a diagram showing an example of gate signals Vgs21 to Vgs24 in the case of the pattern 4 output to the converter 2 by the control circuit 9 of the power conversion device 100 according to the first embodiment.
  • the current path inside the converter 2 in the case of pattern 3 is the same as the current path shown in FIG.
  • FIG. 15 is a diagram showing an example of a method for measuring a leakage current flowing through the power conversion device 100 according to the first embodiment.
  • the power conversion device 100 shown in FIG. 15 is a power conversion device 100 shown in FIG. 2 to which a leakage ammeter 50 for detecting a leakage current value is added.
  • One end of the leakage ammeter 50 is connected to the common terminal of the Y capacitor 30, and the other end is connected to one pole of the AC power supply 1.
  • FIG. 15 is a diagram showing an example of a method for measuring a leakage current flowing through the power conversion device 100 according to the first embodiment.
  • the power conversion device 100 shown in FIG. 15 is a power conversion device 100 shown in FIG. 2 to which a leakage ammeter 50 for detecting a leakage current value is added.
  • One end of the leakage ammeter 50 is connected to the common terminal of the Y capacitor 30, and the other end is connected to one pole of the AC power supply 1.
  • one end of the leakage ammeter 50 is connected to the common terminal of the Y capacitor 30, but when the power conversion device 100 does not have the Y capacitor 30, one end of the leakage ammeter 50 is connected. Connect to the ground terminal of the power converter 100. Further, when the leakage ammeter 50 measures the leakage current in the power conversion device 100, the E terminal of the AC power supply 1 is not connected anywhere.
  • the leakage ammeter 50 has a first resistance 501 of 1 k ⁇ , a second resistance 502 of 10 k ⁇ , a third resistance 503 of 579 ⁇ , a third capacitor 504 of 11.225 nF, and an effective value.
  • the connection method of each element is as shown in FIG. Specifically, a second resistance 502, a third capacitor 504, and a third resistance 503 are connected in parallel to the first resistance 501. Further, an effective value meter 505 is connected in parallel to the third capacitor 504 and the third resistance 503.
  • the effective value meter 505 reads the value of the voltage across the second resistance 502, the third resistance 503, and the first resistance 501 attenuated by the third capacitor 504, which is the role of the low-pass filter.
  • the value read by the effective value meter 505 is the leakage current value.
  • the unit of the value to be read is V (volt), but when converting to the leakage current value, the unit is replaced with mA (milliampere). This is because the effective value meter 505 detects the voltage value across the first resistance 501, which is 1 k ⁇ , and adjusts the unit when converting the voltage to the current.
  • FIG. 16 is a diagram showing an example of gate signals Vgs21 to Vgs24 with respect to the switching elements 21 to 24 when the switching elements 23 and 24 included in the converter 2 of the power converter 100 are switched in synchronization with the alternating current Iac as a comparative example. be.
  • the difference from FIG. 3 is the gate signal Vgs23 for the switching element 23 and the gate signal Vgs24 for the switching element 24.
  • the switching elements 23 and 24 switch at the timing when the polarity of the AC voltage Vac changes, whereas in FIG. 16, the switching elements 23 and 24 have the AC current Iac becoming zero or from zero. Switching is performed at the timing of change.
  • FIG. 17 is a diagram showing, as a comparative example, a waveform obtained by measuring each signal waveform and leakage current when the switching elements 21 to 24 included in the converter 2 of the power converter 100 are operated by the gate signals Vgs21 to Vgs24 shown in FIG. be.
  • FIG. 17 shows, in order from the top, AC current Iac, leakage current, drain / source voltage Vds21 of the switching element 21, drain / source voltage Vds22 of the switching element 22, drain / source voltage Vds23 of the switching element 23, and drain of the switching element 24.
  • the waveforms of the source voltage Vds24, the gate signal Vgs23 of the switching element 23, and the gate signal Vgs24 of the switching element 24 are shown.
  • the drain / source voltage Vds indicates the voltage difference between the drain and the source of the switching element.
  • FIG. 18 shows waveforms obtained by measuring each signal and leakage current when the switching elements 21 to 24 included in the converter 2 of the power conversion device 100 according to the first embodiment operate with the gate signals Vgs21 to Vgs24 shown in FIG. It is a figure.
  • FIG. 18 shows waveforms such as leakage current when the power conversion device 100 switches the switching elements 23 and 24 that perform low-speed switching according to the polarity of the AC voltage Vac.
  • FIG. 18 shows, in order from the top, AC current Iac, leakage current, drain / source voltage Vds21 of the switching element 21, drain / source voltage Vds22 of the switching element 22, drain / source voltage Vds23 of the switching element 23, and switching element 24.
  • Each waveform of the drain source voltage Vds24 is shown. From the waveforms of the drain source voltage Vds23 of the switching element 23 and the drain source voltage Vds24 of the switching element 24 shown in FIG. 18, it can be confirmed that the switching elements 23 and 24 are switching according to the polarity of the AC voltage Vac. ..
  • the control circuit 9 switches such control, that is, the switching elements 23 and 24 that perform low-speed switching according to the polarity of the AC voltage Vac, so that the switching elements that perform low-speed switching are both turned off. Is shortened, and an increase in leakage current can be suppressed.
  • the power conversion device 100 can suppress the leakage current, which is a kind of noise, by changing the switching pattern of the switching elements 21 to 24 of the converter 2, and is composed of the common mode choke coil 20, the Y capacitor 30, and the like.
  • the effect of the noise filter to be applied can be promoted.
  • the control circuit 9 is between the PL terminal between the P terminal which is the DC terminal of the positive electrode of the converter 2 and the L terminal of one of the AC power supplies 1, or the G terminal which is the DC terminal of the negative electrode of the converter 2.
  • the switching elements 21 to 24 are controlled so as to suppress the potential fluctuation caused by the switching operation between the GN terminal and the other N terminal of the AC power supply 1. Further, the control circuit 9 can change the potential fixing method between the PL terminals or the GN terminals by changing the switching pattern of the switching elements 21 to 24.
  • the control circuit 9 is one arm in the first arm in which the switching elements 21 and 22 are connected in series and the second arm in which the switching elements 23 and 24 are connected in series among the switching elements 21 to 24 of the converter 2. High-speed switching is performed to short-circuit the power supply and supply power at the first speed based on the frequency specified in the above.
  • the control circuit 9 performs low-speed switching in which the other arm synchronizes with the power frequency of the AC power supply 1 and switches at a second speed lower than the first speed.
  • the first speed may be a variable speed instead of a constant speed.
  • one of the high-side switching elements 21 and 23 or the low-side switching elements 22 and 24 among the switching elements 21 to 24 of the converter 2 is within one cycle of the power supply frequency of the AC power supply 1.
  • high-speed switching and low-speed switching may be switched once.
  • the control circuit 9 switches the switching element according to the polarity of the AC voltage Vac of the AC power supply 1 in low-speed switching.
  • the control circuit 9 switches the first switching element of the two switching elements performing high-speed switching as the main high-speed switching, and turns off the second switching element. Let me.
  • the control circuit 9 switches the first switching element of the two switching elements performing high-speed switching as the main of high-speed switching, and the second switching element is the first. Switching is performed in inverting synchronization with respect to the switching element.
  • FIG. 19 is a diagram showing an example of a hardware configuration that realizes the control circuit 9 included in the power conversion device 100 according to the first embodiment.
  • the control circuit 9 is realized by the processor 201 and the memory 202.
  • the processor 201 is a CPU (Central Processing Unit, central processing unit, processing unit, arithmetic unit, microprocessor, microprocessor, processor, DSP (Digital Signal Processor)), or system LSI (Large Scale Integration).
  • the memory 202 is a RAM (Random Access Memory), a ROM (Read Only Memory), a flash memory, an EPROM (Erasable Programmable Read Only Memory), an EEPROM (registered trademark) (Electrically Memory), or an EEPROM (registered trademark).
  • a semiconductor memory can be exemplified. Further, the memory 202 is not limited to these, and may be a magnetic disk, an optical disk, a compact disk, a mini disk, or a DVD (Digital Versaille Disc).
  • the control circuit 9 may be composed of an electric circuit element such as an analog circuit or a digital circuit.
  • the control circuit 9 is located between the PL terminals of the P terminal of the converter 2 and the L terminal of the AC power supply 1, or the G terminal of the converter 2. It was decided to control the switching elements 21 to 24 so as to suppress the potential fluctuation caused by the switching operation between the N terminal and the GN terminal of the AC power supply 1. As a result, the power conversion device 100 can achieve both noise suppression and control stability while reducing leakage current that causes noise. Further, the power conversion device 100 can further reduce the leakage current that causes noise by connecting the common mode choke coil 20 and the Y capacitor 30 which are noise filters.
  • Embodiment 2 In the second embodiment, a case where the power conversion device 100 includes a configuration for further reducing the leakage current will be described.
  • FIG. 20 is a diagram showing a configuration example of the power conversion device 100 according to the second embodiment.
  • the power conversion device 100 shown in FIG. 20 includes an AC power supply 1, a converter 2, a first reactor 31, a second reactor 32, a smoothing capacitor 4, a first diode 401, and a second diode 402. , An AC voltage detector 5, an AC current detector 6, a DC voltage detector 7, a control circuit 9, and a load 10.
  • the L terminal of the AC power supply 1 and one end of the first reactor 31 are connected, and the other end of the first reactor 31 and one AC terminal of the converter 2 are connected. Further, the N terminal of the AC power supply 1 and one end of the second reactor 32 are connected, and the other end of the second reactor 32 and the other AC terminal of the converter 2 are connected.
  • the cathode of the first diode 401 is connected to one end of the first reactor 31, and the cathode of the second diode 402 is connected to one end of the second reactor 32.
  • the anodes of the first diode 401 and the second diode 402 are both connected to the G terminal of the negative electrode, which is the DC terminal of the converter 2.
  • AC voltage detectors 5 are connected in parallel to both ends of the AC power supply 1.
  • An AC current detector 6 is connected in series between the AC power supply 1 and the cathode connection ends of the first diode 401 and the second diode 402.
  • one of the first reactor 31 or the second reactor 32 may be the reactor 3 of the first embodiment.
  • a smoothing capacitor 4, a load 10, and a DC voltage detector 7 are connected in parallel between the PG terminals of the DC terminals.
  • the control circuit 9 acquires the values detected by the AC voltage detector 5, the AC current detector 6, and the DC voltage detector 7, that is, the detection result.
  • the control circuit 9 generates gate signals Vgs for controlling the switching elements 21 to 24 of the converter 2 based on the detection results of the AC voltage detector 5, the AC current detector 6, and the DC voltage detector 7. Output.
  • the power converter 100 controls the switching elements 21 to 24 of the converter 2 based on the detection results of the AC voltage detector 5, the AC current detector 6, and the DC voltage detector 7 for the AC power input to the converter 2. By doing so, the power factor is improved and the bus voltage is controlled.
  • the power conversion device 100 of the second embodiment is a noise filter common mode choke coil 20 and a Y capacitor, similar to the power conversion device 100 of the first embodiment shown in FIG. At least one of thirty may be provided.
  • the power conversion device 100 to which the first diode 401 and the second diode 402 shown in FIG. 20 are connected is switched so that the power supply short-circuit path returns at the low side as in the switching pattern shown in FIGS. 13 and 14. Operate the element.
  • the power conversion device 100 can maximize the effect of connecting the first diode 401 and the second diode 402 by circulating the power supply short-circuit path on the low side.
  • the switching element for low-speed switching is switched by the polarity of the AC voltage Vac in the first embodiment, but the first diode 401 and the second diode 402 shown in FIG. 20 are connected.
  • the switching may be performed by the polarity of the alternating current Iac.
  • FIG. 21 is a diagram showing an example of a current path when the control circuit 9 of the power conversion device 100 according to the second embodiment is recirculated by the low-side switching elements 22 and 24 in the power supply short-circuit mode.
  • the power conversion device 100 can pass a current through the first diode 401 and the second diode 402 in the current short circuit mode and the load power supply mode by returning the current through the switching elements 22 and 24 on the low side of the converter 2. ..
  • the power conversion device 100 can fix the potential of the drain source voltage Vds of the switching elements 22 and 24 on the low side of the converter 2 to zero by flowing a current through the first diode 401 and the second diode 402. ..
  • the power conversion device 100 can reduce the leakage current because the potential of the drain source voltage Vds of the switching elements 22 and 24 on the low side of the converter 2 does not fluctuate.
  • FIG. 22 is a diagram showing an example of a current path when the control circuit 9 of the power conversion device 100 is recirculated by the high-side switching elements 21 and 23 in the power supply short-circuit mode as a comparative example.
  • the power conversion device 100 When the power conversion device 100 is recirculated by the switching elements 21 and 23 on the high side of the converter 2, the current cannot flow through the first diode 401 and the second diode 402 in the power short circuit mode. As a result, the power conversion device 100 cannot suppress fluctuations in the drain / source voltage Vds of the low-side switching elements 22 and 24 in the power short-circuit mode, and cannot obtain the maximum effect of reducing the leakage current.
  • FIG. 23 shows the case where the power conversion device 100 according to the second embodiment to which the first diode 401 and the second diode 402 shown in FIG. 20 are connected is recirculated by the low-side switching elements 22 and 24 in the power supply short-circuit mode. It is a figure which shows the waveform which measured the leakage current of.
  • FIG. 23 shows the waveforms of the alternating current Iac, the leakage current, and the drain / source voltages Vds22 and Vds44 of the low-side switching elements 22 and 24 in order from the top.
  • each waveform shown in FIG. 23 is a case where the switching element performing low-speed switching is synchronized with the polarity of the alternating current Iac. From the leakage current waveform shown in FIG. 23, it can be confirmed that the leakage current does not increase even during the period when the AC current Iac is a minute current.
  • one of the high-side switching elements 21 and 23 or the low-side switching elements 22 and 24 of the switching elements 21 to 24 of the converter 2 is an AC power supply 1.
  • High-speed switching and low-speed switching are switched once within one cycle of the power supply frequency of.
  • the control circuit 9 may switch the switching element according to the polarity of the AC voltage Vac of the AC power supply 1, or may switch the switching element according to the polarity of the AC current Iac of the AC power supply 1. good.
  • the control circuit 9 switches the first switching element of the two switching elements performing high-speed switching as the main high-speed switching, and turns off the second switching element.
  • the control circuit 9 switches the first switching element of the two switching elements performing high-speed switching as the main of high-speed switching, and the second switching element is the first. Switching is performed in inverting synchronization with respect to the switching element.
  • the power conversion device 100 further includes a first reactor 31, a second reactor 32, a first diode 401, and a second diode 402. , Leakage current that causes noise can be reduced.
  • Embodiment 3 In the third embodiment, an application example of the power conversion device 100 described in the first embodiment and the second embodiment will be described.
  • FIG. 24 is a diagram showing a configuration example of the motor drive device 101 according to the third embodiment including the power conversion devices 100 of the first and second embodiments.
  • the motor drive device 101 includes the power conversion device 100 described in the first and second embodiments, and the inverter 102 which is a load 10.
  • FIG. 24 shows a state in which the AC power supply 1 and the motor 103 are connected to the motor drive device 101.
  • the inverter 102 is connected to the DC terminal of the converter 2 included in the power conversion device 100.
  • the motor 103 is connected to the output terminal of the inverter 102.
  • the inverter 102 drives the motor 103 by converting the DC power output from the power conversion device 100 into AC power and applying it to the motor 103.
  • the motor drive device 101 shown in FIG. 24 can be applied to products such as blowers, compressors, and air conditioners.
  • FIG. 25 is a diagram showing a configuration example of the air conditioner 120 according to the third embodiment including the motor drive device 101 shown in FIG. 24.
  • the air conditioner 120 includes a motor drive device 101, a compressor 104, and a refrigeration cycle unit 106.
  • FIG. 25 shows a state in which the AC power supply 1 is connected to the air conditioner 120.
  • the compressor 104 includes a motor 103 driven by AC power output from the inverter 102, and a compression element 105.
  • a motor 103 is connected to the output terminal of the motor drive device 101.
  • the motor 103 is connected to the compression element 105.
  • the refrigeration cycle unit 106 includes a four-way valve 107, an indoor heat exchanger 108, an outdoor heat exchanger 109, and an expansion valve 110.
  • the flow path of the refrigerant circulating inside the air conditioner 120 passes from the compression element 105 via the four-way valve 107, the indoor heat exchanger 108, the expansion valve 110, and the outdoor heat exchanger 109, and again via the four-way valve 107. , It is configured to return to the compression element 105.
  • the motor drive device 101 receives an AC voltage Vac from the AC power supply 1 and rotates the motor 103.
  • the compression element 105 executes the compression operation of the refrigerant by rotating the motor 103, and circulates the refrigerant inside the refrigeration cycle unit 106.
  • FIG. 26 is a diagram showing a part of a leakage current propagation path mainly in the outdoor unit 140 in the air conditioner 120 according to the third embodiment.
  • the indoor unit 130 and the outdoor unit 140 are connected via a pipe 115.
  • the substrate GND116 of the motor drive device 101 mounted on the outdoor unit 140 is connected from the Y capacitor 30 to the housing 141 of the outdoor unit 140 via the jumper wire 113.
  • the leakage current propagates from the heat sink 111 of the substrate of the motor drive device 101, the outdoor unit fan 112, the compressor 104, etc., via the stray capacitance 114, and through the housing 141 of the outdoor unit 140. Although only a part of the stray capacitance 114 is shown in FIG.
  • the common mode choke coil 20, the reactor 3, and the like also have a stray capacitance 114 that is capacitively coupled to the housing 141 of the outdoor unit 140. do.
  • the heat sink 111 on the substrate of the motor drive device 101 is not grounded in the example of FIG. 26, it may be grounded.
  • FIG. 27 is a diagram showing measurement results of leakage current according to the compressor rotation speed of the compressor 104 mounted on the air conditioner 120 or the like according to the third embodiment.
  • the compressor rotation speed is actually the rotation speed of the motor 103 included in the compressor 104.
  • the leakage current becomes maximum in the region where the compressor rotation speed is low and the region where the compressor rotation speed is medium rotation.
  • the low rotation region is, for example, a region of 5 to 10 rps.
  • the region of medium rotation is, for example, a region of 40 to 70 rps. Therefore, the power conversion device 100 can obtain more effect of suppressing the leakage current by applying the leakage current suppression technique in the region of low rotation to medium rotation.
  • the control circuit 9 controls the switching of the switching elements 21 to 24 in the region of the compressor 104 from 5 rps to 70 rps as described above.
  • the power conversion device 100 can be applied to various products.
  • the configuration shown in the above embodiments is an example, and can be combined with another known technique, can be combined with each other, and does not deviate from the gist. It is also possible to omit or change a part of the configuration.

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