WO2021193456A1 - Circuit d'attaque pour une charge inductive et système de frein électromagnétique - Google Patents

Circuit d'attaque pour une charge inductive et système de frein électromagnétique Download PDF

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Publication number
WO2021193456A1
WO2021193456A1 PCT/JP2021/011460 JP2021011460W WO2021193456A1 WO 2021193456 A1 WO2021193456 A1 WO 2021193456A1 JP 2021011460 W JP2021011460 W JP 2021011460W WO 2021193456 A1 WO2021193456 A1 WO 2021193456A1
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Prior art keywords
output terminal
transistor
power supply
supply line
electrode power
Prior art date
Application number
PCT/JP2021/011460
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English (en)
Japanese (ja)
Inventor
鈴木　正志
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住友重機械工業株式会社
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Priority claimed from JP2020055465A external-priority patent/JP7445486B2/ja
Priority claimed from JP2020055464A external-priority patent/JP7445485B2/ja
Application filed by 住友重機械工業株式会社 filed Critical 住友重機械工業株式会社
Publication of WO2021193456A1 publication Critical patent/WO2021193456A1/fr

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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01F—MAGNETS; INDUCTANCES; TRANSFORMERS; SELECTION OF MATERIALS FOR THEIR MAGNETIC PROPERTIES
    • H01F7/00—Magnets
    • H01F7/06—Electromagnets; Actuators including electromagnets
    • H01F7/08—Electromagnets; Actuators including electromagnets with armatures
    • H01F7/18—Circuit arrangements for obtaining desired operating characteristics, e.g. for slow operation, for sequential energisation of windings, for high-speed energisation of windings
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P3/00—Arrangements for stopping or slowing electric motors, generators, or dynamo-electric converters
    • H02P3/02—Details of stopping control
    • H02P3/04—Means for stopping or slowing by a separate brake, e.g. friction brake or eddy-current brake
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/04—Modifications for accelerating switching
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/51—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used
    • H03K17/56—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices
    • H03K17/60—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being bipolar transistors
    • H03K17/615—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being bipolar transistors in a Darlington configuration
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/51—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used
    • H03K17/56—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices
    • H03K17/60—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being bipolar transistors
    • H03K17/64—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being bipolar transistors having inductive loads
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/51—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used
    • H03K17/56—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices
    • H03K17/687—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being field-effect transistors

Definitions

  • the present disclosure relates to an inductive load drive circuit.
  • Electromagnetic brakes are widely used as a means to stop the rotation of the motor.
  • the electromagnetic brake is one of the mechanical brakes.
  • the non-excitation actuated electromagnetic brake when the exciting coil is not energized, the armature is pressed against the brake hub by the spring coil, and the brake is activated (holding state). When a voltage is applied to the exciting coil, the electromagnet attracts the armature and the brake is released. Due to these characteristics, non-excitation actuated electromagnetic brakes are often used in applications where safety should be prioritized in the event of an emergency or power failure.
  • FIG. 1 is a block diagram of a control system including a motor.
  • the rectifier 10 rectifies the AC voltage.
  • the inverter 20 converts the DC voltage VDC generated by the rectifier 10 into an AC voltage and drives the motor 2.
  • the electromagnetic brake 4 and the brake drive circuit 40 form an electromagnetic brake system.
  • the brake drive circuit 40 switches between opening and braking by switching between excitation (energized) and non-excited (non-energized) of the exciting coil of the electromagnetic brake 4.
  • FIG. 2A and 2B are circuit diagrams showing a configuration example of the brake drive circuit 40.
  • the brake drive circuit 40 of FIG. 2A is a full bridge circuit including transistors Tr1 to Tr4.
  • the pair of transistors Tr1 and Tr2 is turned on, and a voltage of the first polarity is applied to the exciting coil of the electromagnetic brake 4. In this state, the holding current I 0 is flowing through the exciting coil.
  • the brake drive circuit 40 turns on the pair of transistors Tr3 and Tr4, applies a voltage having the opposite polarity to the released state to the exciting coil, and extinguishes the electromagnetic brake.
  • the brake drive circuit 40 of FIG. 2B includes a diagonal bridge circuit including transistors Tr1 and Tr2 and diodes D1 and D2.
  • the pair of transistors Tr1 and Tr2 is turned on, and a voltage of the first polarity is applied to the exciting coil of the electromagnetic brake 4. In this state, the holding current I 0 is flowing through the exciting coil.
  • the transistors Tr1 and Tr2 are turned off.
  • the current flowing through the exciting coil is regenerated via the diodes D1 and D2, and the electromagnetic brake is extinguished.
  • the brake drive circuit of FIG. 2A has a large number of transistors and needs to be provided with a gate drive circuit for each transistor, so that the circuit scale is large.
  • the arc extinguishing time ⁇ required for the holding current I 0 to drop to 0 is given by the equation (1) and is limited by the DC voltage VPN.
  • ⁇ L / V PN ⁇ I 0 ... (1)
  • One aspect of the present disclosure is made in such a situation, and one of its exemplary purposes is to provide a drive circuit capable of reducing the current of an inductive load in a short time.
  • Another aspect of the present disclosure is made in such a situation, and one of its exemplary purposes is to provide a drive circuit capable of reducing power consumption while shortening the brake release time.
  • the drive circuit of one aspect of the present disclosure includes a first output terminal and a second output terminal to which an inductive load is connected, a first transistor provided between the first output terminal and the positive electrode power supply line, and a first output terminal.
  • a first diode provided between the and negative electrode power supply lines, a second transistor provided between the second output terminal and the negative electrode power supply line, a Darlington circuit provided between the second output terminal and the positive electrode power supply line, and Darlington. It includes a Zener diode provided between the control terminal of the circuit and the second output terminal.
  • a voltage higher than the voltage of the positive electrode power supply line can be generated at the second output terminal, a boosted voltage can be applied to the inductive load, and the current of the inductive load can be reduced in a short time. Can be made to.
  • This drive circuit includes a first output terminal and a second output terminal to which an inductive load is connected, a first transistor provided between the first output terminal and the positive electrode power supply line, and a first output terminal and a negative electrode power supply line.
  • the Darlington circuit provided between them, the Zener diode provided between the control terminal and the first output terminal of the Darlington circuit, the second transistor provided between the second output terminal and the negative electrode power supply line, and the second output terminal.
  • a second diode provided between the positive electrode power supply lines is provided.
  • a voltage lower than the voltage of the negative electrode power supply line can be generated at the first output terminal, a boosted voltage can be applied to the inductive load, and the current of the inductive load can be reduced in a short time. be able to.
  • the Darlington circuit also includes a third transistor whose base is connected to the anode of the Zener diode, a fourth transistor whose base is connected to the emitter of the third transistor, and a resistor whose base is connected to the collector of the third transistor. good.
  • the inductive load may be a coil of a non-excited electromagnetic brake. This enables high-speed braking.
  • the brake drive circuit of a certain aspect of the present disclosure includes a full bridge circuit connected to an exciting coil of an electromagnetic brake, a current detection circuit for detecting a coil current flowing through the exciting coil, and a full bridge circuit in response to an excitation command. It includes a controller that starts driving the transistor pair of the diagonal arm and lowers the duty cycle of the transistor pair when it detects a fluctuation in the coil current due to the start of movement of the armature.
  • the power supply voltage of the full bridge circuit be VPN , the duty cycle of the transistor pair before the detection of the fluctuation of the coil current be d1, and the duty cycle of the transistor pair after the detection of the fluctuation of the coil current be d2.
  • the drive voltage VL applied to the exciting coil is equal to d1 ⁇ V PN
  • the drive voltage VL after the start of armature movement is d2 ⁇ V PN , which is V PN and d1, d2.
  • Drive conditions can be defined with three parameters. Therefore, by designing the VPN and the duty cycle d1 to be large and reducing the duty cycle d2 while shortening the time required to release the brake, the current after the brake is released can be reduced and the power consumption can be reduced.
  • the full bridge circuit consists of a first output terminal and a second output terminal to which an exciting coil is connected, a first transistor provided between the first output terminal and the positive electrode power supply line, and between the first output terminal and the negative electrode power supply line.
  • a voltage higher than the voltage of the positive electrode power supply line can be generated at the second output terminal, and by applying the boosted voltage to the exciting coil, until the electromagnetic brake braking becomes effective. You can save time.
  • the full bridge circuit consists of a first output terminal and a second output terminal to which an exciting coil is connected, a first transistor provided between the first output terminal and the positive electrode power supply line, and between the first output terminal and the negative electrode power supply line.
  • the Darlington circuit provided in the above, the Zener diode provided between the control terminal and the first output terminal of the Darlington circuit, the second transistor provided between the second output terminal and the negative electrode power supply line, the second output terminal and the positive electrode. It may include a diode provided between power lines.
  • a voltage lower than the voltage of the negative electrode power supply line can be generated at the first output terminal, and by applying the boosted voltage to the exciting coil, until the electromagnetic brake braking becomes effective. You can save time.
  • the Darlington circuit also includes a third transistor whose base is connected to the anode of the Zener diode, a fourth transistor whose base is connected to the emitter of the third transistor, and a resistor whose base is connected to the collector of the third transistor. good.
  • the current of the inductive load can be reduced in a short time.
  • FIG. 2 (a) and 2 (b) are circuit diagrams showing a configuration example of a brake drive circuit. It is a circuit diagram of the drive circuit which concerns on Embodiment 1.
  • FIG. It is an operation waveform diagram of the drive circuit of FIG. It is a circuit diagram of the drive circuit which concerns on Embodiment 2.
  • It is an operation waveform diagram of the drive circuit of FIG. It is a block diagram of the control system including a motor.
  • 9 (a) is an operation waveform diagram of the brake drive circuit of FIG. 8, and FIG. 9 (b) is an operation waveform diagram of the brake drive circuit according to the comparative technique.
  • FIG. 3 is a circuit diagram of the drive circuit 100A according to the first embodiment.
  • the drive circuit 100A drives the coil L1 which is an inductive load.
  • the type of inductive load is not limited, but may be, for example, an exciting coil of an electromagnetic brake.
  • the drive circuit 100A includes a first output terminal OUT1, a second output terminal OUT2, a first transistor Tr1, a second transistor Tr2, a first diode D1, and a Darlington circuit 112.
  • the first output terminal OUT1 is connected to one end of the coil L1, and the second output terminal OUT2 is connected to the other end of the coil L1.
  • the first transistor Tr1 is provided between the first output terminal OUT1 and the positive electrode power supply line 102.
  • the first diode D1 is provided between the first output terminal OUT1 and the negative electrode power supply line 104.
  • the second transistor Tr2 is provided between the second output terminal OUT2 and the negative electrode power supply line 104.
  • the first transistor Tr1 and the second transistor Tr2 are IGBTs (Insulated Gate Bipolar Transistors).
  • the Darlington circuit 112 is provided between the second output terminal OUT2 and the positive electrode power supply line 102.
  • the Zener diode ZD1 is provided between the gate (that is, the base) of the Darlington circuit 112 and the second output terminal OUT2.
  • the Darlington circuit 112 includes a third transistor Tr3 and a fourth transistor Tr4, which are NPN type bipolar transistors, and a resistor R1.
  • the base of the third transistor Tr3 is connected to the anode of the Zener diode ZD1.
  • the emitter of the fourth transistor Tr4 is connected to the positive electrode power supply line 102, its collector is connected to the second output terminal OUT2, and the base is connected to the emitter of the third transistor Tr3.
  • the resistor R1 is provided between the collector of the third transistor Tr3 and the second output terminal OUT2.
  • the above is the configuration of the drive circuit 100A. Subsequently, the operation of the electromagnetic brake system including the drive circuit 100A and the electromagnetic brake will be described assuming that the coil L1 is the exciting coil of the non-excitation type electromagnetic brake.
  • FIG. 4 is an operation waveform diagram of the drive circuit 100A of FIG. The before time t 0, a release period of the brake, the first transistor Tr1 and the second transistor Tr2 is turned on, the first output terminal OUT1, the voltage V PN of the cathode power line 102 is generated, the second output The voltage (0V) of the negative electrode power supply line 104 is generated at the terminal OUT2. Then, the coil L1, to the right in the circuit diagram of FIG. 3, the coil current I L of the current amount I 0 flowing.
  • the braking command is generated, the first transistor Tr1 of the driving circuit 100A, the second transistor Tr2 is turned off. Then, the coil current I L, first diode D1, a coil L1, starts to flow through the path of the Darlington circuit 112.
  • First voltage output terminal OUT1 becomes 0V at this time, the voltage of the second output terminal OUT2 becomes V PN + Vz + 2 ⁇ Vbe .
  • Vz is the Zener voltage of the Zener diode ZD1
  • Vbe is the base-emitter voltage of the third transistor Tr3 and the fourth transistor Tr4.
  • Coil current I L at time t 0 after is represented by the formula (2), it decreases with time.
  • the arc extinguishing time ⁇ until the coil current IL becomes 0 is expressed by Eq. (3).
  • ⁇ L ⁇ I 0 / ( VPN + Vz)... (3)
  • FIG. 4 shows the operation when the diagonal bridge circuit of FIG. 2 (b) is used by the alternate long and short dash line.
  • the arc extinguishing time ⁇ 'at this time is given by the equation (1), and the arc extinguishing time ⁇ 'is ( VPN + VPN) / VPN times the arc extinguishing time ⁇ in the first embodiment.
  • the extinguishing time can be shortened to V PN / (V PN + Vz ).
  • the time when braking starts is defined by the arc extinguishing time ⁇ . Therefore, by shortening the arc extinguishing time ⁇ , high-speed braking becomes possible.
  • the drive circuit 100A does not require a gate drive circuit for driving the transistors Tr3 and Tr4, it has an advantage that it can be configured more simply than the full bridge circuit of FIG. 2A.
  • FIG. 5 is a circuit diagram of the drive circuit 100B according to the second embodiment.
  • the position of the Darlington circuit 112 is changed between the first output terminal OUT1 and the negative electrode power supply line 104.
  • FIG. 6 is an operation waveform diagram of the drive circuit 100B of FIG.
  • the first transistor Tr1 and the second transistor Tr2 Prior to time t 0, a release period of the brake, the first transistor Tr1 and the second transistor Tr2 is turned on, the first output terminal OUT1, the voltage V PN of the cathode power line 102 is generated, the second output The voltage (0V) of the negative electrode power supply line 104 is generated at the terminal OUT2.
  • the coil L1 to the right in the circuit diagram of FIG. 5, the coil current I L of the current amount I 0 flowing.
  • the braking command is generated, the first transistor Tr1 of the drive circuit 100B, the second transistor Tr2 is turned off. Then, the coil current I L, Darlington circuit 112, a coil L1, starts to flow through the path of the second diode D2. Voltage of the first output terminal OUT1 at this time - (Vz + 2 ⁇ Vbe) and the voltage at the second output terminal OUT2 becomes V PN. At this time, VL ⁇ VPN + Vz is applied between both ends of the coil L1.
  • the time t 0 after the coil current I L is represented by formula (2), it decreases with time.
  • the arc extinguishing time ⁇ until the coil current IL becomes 0 is expressed by Eq. (3).
  • the arc extinguishing time ⁇ can also be shortened by the second embodiment.
  • a power transistor such as a bipolar transistor, a MOSFET (Metal Oxide Semiconductor Field Effect Transistor), or a GaN-HEMT (High Electron Mobility Transistor) can be used instead of the IGBT.
  • MOSFET Metal Oxide Semiconductor Field Effect Transistor
  • GaN-HEMT High Electron Mobility Transistor
  • the configuration of the Darlington circuit 112 is not limited to the illustrated circuit. In the embodiment, a two-stage Darlington circuit is shown, but it may be configured with three or more stages. Further, the transistors Tr3 and Tr4 may be composed of FETs. In this case, in the configuration of FIG. 3, a current path including a resistor may be added between the gate which is the control terminal of the Darlington circuit 112 and the positive electrode power supply line 102. Alternatively, in the configuration of FIG. 5, a current path including a resistor or the like may be added between the gate which is the control terminal of the Darlington circuit 112 and the first output terminal OUT1 of the negative electrode power supply line 104.
  • a resistor or a diode may be added in series with the Zener diode ZD1 between the second output terminal OUT2 and the control terminal of the Darlington circuit 112.
  • a resistor or a diode may be added in series with the Zener diode ZD1 between the negative electrode power supply line 104 and the control terminal of the Darlington circuit 112.
  • the coil L1 is an exciting coil of a non-excited electromagnetic brake, but the present invention can also be applied to an excited type.
  • the brake release time can be shortened by shortening the arc extinguishing time.
  • the drive target of the drive circuit 100 is not limited to the excitation target of the electromagnetic brake, and can be used for driving an electromagnetic clutch, and is also widely applicable to drive a load in which a current needs to flow in only one direction. ..
  • the drive target of the drive circuit 100 may be a brushed DC motor that rotates in only one direction. In this case, the DC motor can be rotated while the transistors Tr1 and Tr2 are on, and when they are turned off, the DC motor can be stopped.
  • FIG. 7 is a block diagram of a control system including a motor.
  • the rectifier 10 rectifies the AC voltage.
  • the inverter 20 converts the DC voltage VDC generated by the rectifier 10 into an AC voltage and drives the motor 2.
  • the brake drive circuit 100 switches between opening and braking by switching between excitation (energized) and non-excited (non-energized) of the exciting coil of the electromagnetic brake 4.
  • FIG. 8 is a circuit diagram of the electromagnetic brake system 6 including the brake drive circuit 100 according to the third embodiment.
  • the brake drive circuit 100 includes a positive electrode power supply line 102, a negative electrode power supply line 104, a full bridge circuit 110, a current detection circuit 120, a controller 130, and a gate driver circuit 140.
  • a power supply voltage VPN is supplied between the positive electrode power supply line 102 and the negative electrode power supply line 104.
  • the negative electrode power supply line 104 is used as a reference, and its potential is set to 0V.
  • the full bridge circuit 110 is connected to the exciting coil L1 of the electromagnetic brake 4.
  • the full bridge circuit 110 includes four arms A1 to A4.
  • the upper arm A1 and the lower arm A3 form a leg on the first output terminal OUT1 side
  • the upper arm A4 and the lower arm A2 form a leg on the second output terminal OUT2 side.
  • each arm A1 to A4 includes a power transistor and a fly wheel diode (reflux diode).
  • Current detecting circuit 120 detects a coil current I L flowing through the exciting coil L1, and generates a current detection signal S2.
  • the controller 130 generates a control signal S3 instructing on / off of the power transistors of the arms A1 to A4 based on the excitation command S1 instructing the state of the electromagnetic brake 4 and the current detection signal S2.
  • the gate driver circuit 140 drives the power transistors of the arms A1 to A4 based on the control signal S3.
  • the controller 130 starts driving the transistor pair of the diagonal arms A1 and A2 of the full bridge circuit 110 in response to the excitation command S1 instructing the brake release. Then, the controller 130 monitors the current detection signal S2, upon detecting a variation of the coil current I L caused by the start of movement of the armature, reducing the duty cycle of the transistor pair of the arms A1, A2 of the diagonal.
  • Method of detecting the variation of the coil current I L in the controller 130 is not particularly limited.
  • the controller 130 may include an analog comparator and compare the current detection signal S2 with the threshold.
  • a current detection signal may be input to the high-pass filter to extract spike-like changes.
  • the controller 130 may convert the current detection signal S2 into a digital value and perform equivalent processing by digital signal processing. Or by waveform matching, it may detect the variation of the coil current I L.
  • FIG. 9A is an operation waveform diagram of the brake drive circuit 100 of FIG.
  • FIG. 9B shows an operation waveform diagram of the brake drive circuit according to the comparative technique.
  • the excitation command S1 is negate (low)
  • the coil current IL is zero
  • the electromagnetic brake 4 is in the braking state.
  • the controller 130 starts to drive the transistor pair of the arms A1, A2 of the diagonal.
  • the duty cycle d1 immediately after the start of driving is 100% and is fixedly turned on.
  • a drive voltage VL substantially equal to the power supply voltage VPN is applied between both ends of the exciting coil L1.
  • the coil current I L is increased, it weakens the force of the electromagnetic brake 4.
  • FIG. 9 (b) The advantage of the brake drive circuit 100 becomes clear by comparison with the comparative technique.
  • the comparative technique when the excitation command S1 is asserted, the transistor pairs of the diagonal arms A1 and A2 are fixedly turned on.
  • the power supply voltage V PN 'in comparison techniques need to be designed to be lower than the power supply voltage V PN embodiment be. Then, immediately after the excitation command S1 is asserted, the speed at which the coil current IL increases becomes slow, and the time t 2 until the brake is released becomes long. On the other hand, in the embodiment, the brake release time can be shortened as compared with the comparative technique.
  • the power supply voltage V PN in comparison techniques may be the same voltage level as the power supply voltage V PN embodiment.
  • the drive voltage VL is equal to the power supply voltage VPN after the brake is released, the coil current (holding current) after the brake is released becomes large.
  • the holding current can be reduced and the power consumption can be reduced as compared with the comparative technique.
  • the trade-off relationship between the brake release time and the holding current can be eliminated, and a short opening time and a small holding current can be achieved at the same time.
  • FIG. 10 is a circuit diagram of the brake drive circuit 100A according to the modified example 3.1.
  • the full bridge circuit 110A is a diagonal full bridge circuit, and the diagonal arms A3 and A4 are composed of diodes. Others are the same as in FIG. Also in this modification, the same effect as that of the embodiment can be obtained.
  • FIG. 11 is a circuit diagram of the full bridge circuit 110B according to the modified example 3.2.
  • the full bridge circuit 110B includes a first transistor Tr1, a second transistor Tr2, a first diode D1, a Darlington circuit 112, and a Zener diode ZD1.
  • the first transistor Tr1 and the second transistor Tr2 are a transistor pair of the diagonal arms A1 and A2 described above.
  • the first diode D1 corresponds to the arm A3, and the Darlington circuit 112 and the Zener diode ZD1 correspond to the arm A4.
  • the first transistor Tr1 is provided between the first output terminal OUT1 and the positive electrode power supply line 102.
  • the first diode D1 is provided between the first output terminal OUT1 and the negative electrode power supply line 104.
  • the second transistor Tr2 is provided between the second output terminal OUT2 and the negative electrode power supply line 104.
  • the first transistor Tr1 and the second transistor Tr2 are IGBTs (Insulated Gate Bipolar Transistors).
  • the Darlington circuit 112 is provided between the second output terminal OUT2 and the positive electrode power supply line 102.
  • the Zener diode ZD1 is provided between the gate (that is, the base) of the Darlington circuit 112 and the second output terminal OUT2.
  • the Darlington circuit 112 includes a third transistor Tr3 and a fourth transistor Tr4, which are NPN type bipolar transistors, and a resistor R1.
  • the base of the third transistor Tr3 is connected to the anode of the Zener diode ZD1.
  • the emitter of the fourth transistor Tr4 is connected to the positive electrode power supply line 102, its collector is connected to the second output terminal OUT2, and the base is connected to the emitter of the third transistor Tr3.
  • the resistor R1 is provided between the collector of the third transistor Tr3 and the second output terminal OUT2.
  • FIG. 12 is an operation waveform diagram of the full bridge circuit 110B of FIG. Before the time t 0 , the brake is released, the first transistor Tr1 and the second transistor Tr2 are switched in the duty cycle d, and the exciting coil L1 has a current amount to the right in the circuit diagram of FIG. coil current I L of I 0 is flowing. Although the voltages of the first output terminal OUT1 and the second output terminal OUT2 are actually switched before the time t 0, they are shown in a simplified manner in FIG.
  • Coil current I L at time t 0 after is represented by the formula (1), it decreases with time.
  • the arc extinguishing time ⁇ until the coil current IL becomes 0 is expressed by Eq. (2).
  • ⁇ L ⁇ I 0 / ( VPN + Vz)... (2)
  • FIG. 12 shows the operation when the diagonal bridge circuit 110A of FIG. 10 is used by a alternate long and short dash line.
  • the arc extinguishing time ⁇ 'at this time is given by the equation (3), and the arc extinguishing time ⁇ 'is ( VPN + Vz) / VPN times the arc extinguishing time ⁇ in the modified example 3.2.
  • the extinguishing time can be shortened to V PN / (V PN + Vz ).
  • ⁇ ' L / V PN ⁇ I 0 ... (3)
  • the time when braking starts is defined by the arc extinguishing time ⁇ . Therefore, by shortening the arc extinguishing time ⁇ , high-speed braking becomes possible.
  • the drive circuit 100B does not require a gate drive circuit for driving the transistors Tr3 and Tr4, it has an advantage that it can be configured more simply than the full bridge circuit of FIG.
  • FIG. 13 is a circuit diagram of the full bridge circuit 110C according to the modified example 3.3.
  • the full bridge circuit 110C includes a first transistor Tr1, a second transistor Tr2, a diode D2, a Darlington circuit 112, and a Zener diode ZD1.
  • the first transistor Tr1 and the second transistor Tr2 are a transistor pair of the diagonal arms A1 and A2 described above. Further, the Darlington circuit 112 and the Zener diode ZD1 correspond to the arm A3, and the diode D2 corresponds to the arm A4.
  • the difference between the modified example 3.3 and the modified example 3.2 is the position of the Darlington circuit 112, and specifically, it is changed between the first output terminal OUT1 and the negative electrode power supply line 104.
  • FIG. 14 is an operation waveform diagram of the full bridge circuit 110C of FIG. Before the time t 0 , the brake is released, the first transistor Tr1 and the second transistor Tr2 are switched in the duty cycle d, and the exciting coil L1 has a current amount to the right in the circuit diagram of FIG. coil current I L of I 0 is flowing. Although the voltages of the first output terminal OUT1 and the second output terminal OUT2 are actually switched before the time t 0, they are shown in a simplified manner in FIG.
  • excitation command S1 is negated, the braking command is generated, the first transistor Tr1 of the drive circuit 100B, the second transistor Tr2 is turned off. Then, the coil current I L, Darlington circuit 112, a coil L1, begins to flow in the path of the diode D2. Voltage of the first output terminal OUT1 at this time - (Vz + 2 ⁇ Vbe) and the voltage at the second output terminal OUT2 becomes V PN. At this time, VL ⁇ VPN + Vz is applied between both ends of the coil L1.
  • the time t 0 after the coil current I L is represented by formula (1), decreases with time.
  • the arc extinguishing time ⁇ until the coil current IL becomes 0 is expressed by Eq. (2).
  • the arc extinguishing time ⁇ can be shortened as in the modified example 3.2.
  • a power transistor such as a bipolar transistor, a MOSFET (Metal Oxide Semiconductor Field Effect Transistor), or a GaN-HEMT (High Electron Mobility Transistor) can be used instead of the IGBT.
  • a bipolar transistor a MOSFET (Metal Oxide Semiconductor Field Effect Transistor), or a GaN-HEMT (High Electron Mobility Transistor)
  • MOSFET Metal Oxide Semiconductor Field Effect Transistor
  • GaN-HEMT High Electron Mobility Transistor
  • the configuration of the Darlington circuit 112 is not limited to the illustrated circuit. Although the Darlington circuit having two stages is shown in FIGS. 11 and 13, it may be configured with three or more stages. Further, the transistors Tr3 and Tr4 may be composed of FETs. In this case, in the configuration of FIG. 11, a current path including a resistor may be added between the gate which is the control terminal of the Darlington circuit 112 and the positive electrode power supply line 102. Alternatively, in the configuration of FIG. 13, a current path including a resistor or the like may be added between the gate which is the control terminal of the Darlington circuit 112 and the first output terminal OUT1 of the negative electrode power supply line 104.
  • a resistor or a diode may be added in series with the Zener diode ZD1 between the second output terminal OUT2 and the control terminal of the Darlington circuit 112.
  • a resistor or a diode may be added in series with the Zener diode ZD1 between the negative electrode power supply line 104 and the control terminal of the Darlington circuit 112.
  • the present invention relates to an inductive load drive circuit.

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  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Braking Arrangements (AREA)
  • Electronic Switches (AREA)

Abstract

Selon l'invention, un premier transistor (Tr1) et un second transistor (Tr2) sont positionnés en diagonale dans un circuit en pont complet. Une première diode (D1) est disposée entre une première borne de sortie (OUT1) et une ligne d'alimentation électrique d'électrode négative (104). Un circuit Darlington (112) est disposé entre une seconde borne de sortie (OUT2) et une ligne d'alimentation électrique d'électrode positive (102). Une diode Zener (ZD1) est disposée entre la borne de commande du circuit Darlington (112) et la seconde borne de sortie (OUT2).
PCT/JP2021/011460 2020-03-26 2021-03-19 Circuit d'attaque pour une charge inductive et système de frein électromagnétique WO2021193456A1 (fr)

Applications Claiming Priority (4)

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JP2020-055465 2020-03-26
JP2020055465A JP7445486B2 (ja) 2020-03-26 2020-03-26 ブレーキ駆動回路および電磁ブレーキシステム
JP2020-055464 2020-03-26
JP2020055464A JP7445485B2 (ja) 2020-03-26 2020-03-26 誘導性負荷の駆動回路および電磁ブレーキシステム

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Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3525883A (en) * 1967-07-28 1970-08-25 Dover Corp Bridge amplifier circuit
JPS61220523A (ja) * 1985-03-27 1986-09-30 Honda Motor Co Ltd スイツチング回路
JPS6461940A (en) * 1987-09-02 1989-03-08 Fuji Electric Co Ltd Semiconductor element
JP2006002807A (ja) * 2004-06-15 2006-01-05 Ogura Clutch Co Ltd ア−マチュア吸引検知方法および装置
JP2018126017A (ja) * 2017-02-03 2018-08-09 住友重機械工業株式会社 ブレーキ駆動回路

Family Cites Families (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
MY160103A (en) * 2008-10-03 2017-02-28 Access Business Group Int Llc Power system
JP6401222B2 (ja) * 2016-10-31 2018-10-10 油研工業株式会社 誘導負荷駆動回路

Patent Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3525883A (en) * 1967-07-28 1970-08-25 Dover Corp Bridge amplifier circuit
JPS61220523A (ja) * 1985-03-27 1986-09-30 Honda Motor Co Ltd スイツチング回路
JPS6461940A (en) * 1987-09-02 1989-03-08 Fuji Electric Co Ltd Semiconductor element
JP2006002807A (ja) * 2004-06-15 2006-01-05 Ogura Clutch Co Ltd ア−マチュア吸引検知方法および装置
JP2018126017A (ja) * 2017-02-03 2018-08-09 住友重機械工業株式会社 ブレーキ駆動回路

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