WO2020125235A1 - 一种升压功率变换电路、方法、逆变器、装置及系统 - Google Patents

一种升压功率变换电路、方法、逆变器、装置及系统 Download PDF

Info

Publication number
WO2020125235A1
WO2020125235A1 PCT/CN2019/115075 CN2019115075W WO2020125235A1 WO 2020125235 A1 WO2020125235 A1 WO 2020125235A1 CN 2019115075 W CN2019115075 W CN 2019115075W WO 2020125235 A1 WO2020125235 A1 WO 2020125235A1
Authority
WO
WIPO (PCT)
Prior art keywords
diode
voltage
power conversion
conversion circuit
boost power
Prior art date
Application number
PCT/CN2019/115075
Other languages
English (en)
French (fr)
Inventor
师涛
朱吉新
Original Assignee
华为技术有限公司
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by 华为技术有限公司 filed Critical 华为技术有限公司
Priority to EP19898626.7A priority Critical patent/EP3739740A4/en
Publication of WO2020125235A1 publication Critical patent/WO2020125235A1/zh
Priority to US16/938,119 priority patent/US11418114B2/en
Priority to US17/872,525 priority patent/US20220368227A1/en

Links

Images

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/483—Converters with outputs that each can have more than two voltages levels
    • H02M7/4837—Flying capacitor converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02S—GENERATION OF ELECTRIC POWER BY CONVERSION OF INFRARED RADIATION, VISIBLE LIGHT OR ULTRAVIOLET LIGHT, e.g. USING PHOTOVOLTAIC [PV] MODULES
    • H02S40/00—Components or accessories in combination with PV modules, not provided for in groups H02S10/00 - H02S30/00
    • H02S40/30—Electrical components
    • H02S40/32—Electrical components comprising DC/AC inverter means associated with the PV module itself, e.g. AC modules
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0095—Hybrid converter topologies, e.g. NPC mixed with flying capacitor, thyristor converter mixed with MMC or charge pump mixed with buck
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/32—Means for protecting converters other than automatic disconnection
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/36—Means for starting or stopping converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/06—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider
    • H02M3/07—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider using capacitors charged and discharged alternately by semiconductor devices with control electrode, e.g. charge pumps
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02E—REDUCTION OF GREENHOUSE GAS [GHG] EMISSIONS, RELATED TO ENERGY GENERATION, TRANSMISSION OR DISTRIBUTION
    • Y02E10/00—Energy generation through renewable energy sources
    • Y02E10/50—Photovoltaic [PV] energy

Definitions

  • the invention relates to the technical field of power electronics, in particular to a boosting power conversion circuit, method, inverter, device and system.
  • the Boost circuit is a boosting power conversion circuit, which can boost the input voltage and output it to achieve power conversion.
  • the boost circuit includes a two-level boost circuit and a multi-level boost circuit.
  • the two-level boost circuit is generally used in occasions where the voltage level is lower, and the input level of the two-level boost circuit is two.
  • the multi-level Boost circuit is applied to the occasions of higher voltage levels, and the multi-level Boost circuit can realize power conversion with input levels greater than or equal to three levels.
  • the multi-level Boost circuit realizes multi-level by improving its topology, and then realizes high voltage and high power output.
  • the outstanding advantage of the multi-level Boost circuit is that it can reduce the voltage stress of the power device.
  • the voltage stress that the power device withstands is half that of the two-level Boost circuit, so that the power device with a smaller withstand voltage level can achieve higher Level voltage output.
  • the multi-level Boost circuit has a smaller input current ripple than the two-level Boost circuit, thereby reducing the size and design cost of the filter. Therefore, the multi-level Boost circuit has wide application prospects.
  • the application of the multi-level Boost circuit is introduced as an example in the field of photovoltaic power generation.
  • the output terminal of the photovoltaic module is connected to the input terminal of the multi-level Boost circuit, and the output terminals of the multi-channel multi-level Boost circuit are connected in parallel to realize the control of the connected photovoltaic module, so that The photovoltaic module outputs large power.
  • the output terminals of the multiple boost circuits are connected in parallel, there may be an input terminal of one boost circuit that is not connected to the photovoltaic component, that is, the voltage is lower than the start voltage of the boost power conversion circuit, and the input of the other boost circuit is now The terminal is connected to the input source, so the bus voltage is established at the output of all Boost circuits.
  • the Boost circuit For the power devices in the Boost circuit whose voltage is lower than the start voltage of the boost power conversion circuit will withstand the bus voltage, therefore, the Boost circuit The diode must be selected with a voltage stress that can withstand the bus voltage, which makes the selection of the diode difficult, and the higher the voltage stress, the higher the cost of the device.
  • the present invention provides a boost power conversion circuit, method, inverter, device and system, which can make the voltage at the input end of the boost power conversion circuit lower than the boost power conversion
  • the diode with a smaller voltage stress can be selected by reducing the voltage that the diode in the Boost circuit withstands.
  • an embodiment of the present application provides a boost power conversion circuit that adds a voltage control circuit on the basis of a three-level Boost circuit
  • the three-level Boost circuit includes: a first switching tube, a second switching tube, Inductor, flying capacitor, first diode, second diode and voltage control circuit; inductance, first diode and second diode are connected in series to form a first branch, the first branch and the boost
  • the input positive pole and the input negative pole of the power conversion circuit are connected in series to form a main loop.
  • the anodes of the first diode and the second diode are close to the input anode of the boost power conversion circuit.
  • the cathode is close to the input negative pole of the boost power conversion circuit; the inductor, the first switch tube and the second switch tube are connected in series to form a first closed loop, the first switch tube, the second switch tube, the first diode and the second diode
  • the tube forms a second closed loop; one end of the flying capacitor is connected to the common point of the first diode and the second diode, and the other end of the flying capacitor is connected to the common point of the first switching tube and the second switching tube; voltage
  • the control circuit is connected in series with a third closed loop.
  • the third closed loop is a loop composed of an inductor, a first switch tube, a flying capacitor, a second diode, and an input positive pole and an input negative pole; a voltage control circuit is used to make the second The voltage that the diode withstands is less than the bus voltage of the boost power conversion circuit; the bus voltage is the voltage difference between the positive bus voltage and the negative bus voltage; or, the first end of the voltage control circuit is connected to the first diode and The common end of the second diode, the second end of the voltage control circuit is connected to a reference point, the reference point is used to provide a clamping potential, the clamping potential is located between the negative bus potential and the positive bus potential; the voltage control circuit is used to boost When the voltage at the input end of the power conversion circuit is lower than the starting voltage of the boost power conversion circuit, the common point of the first diode and the second diode is voltage clamped.
  • the added voltage control circuit can clamp the voltage at the common point of the first diode and the second diode.
  • the voltage at the input terminal of the boost power conversion circuit is lower than its starting voltage
  • the first diode and the The voltage at the common point of the second diode is less than the bus voltage, which in turn can reduce the voltage stress at the common point of the first diode and the second diode, which facilitates the selection of the diode.
  • the cost of a diode is proportional to the voltage stress it bears. The greater the voltage stress it can withstand, the higher the cost.
  • a voltage control circuit can be connected in series in the third closed loop, the purpose is to form a voltage division with the second diode, thereby reducing the voltage stress it bears.
  • the voltage control circuit includes: a clamping diode, a controllable switch tube or a composite device; the composite device includes a clamping diode and a controllable switch tube connected in parallel.
  • the controller needs to control its switching state, that is, whether it is on or off.
  • the voltage control circuit further includes: a controller; the controller is used to control the controllable switch to open when the voltage at the input end of the boost power conversion circuit is lower than the start voltage of the boost power conversion circuit; the controller is also used to boost When the voltage at the input end of the power conversion circuit is higher than the starting voltage of the boost power conversion circuit, the controllable switch tube is controlled to close.
  • the clamping diode can be automatically operated, that is, forward-conducting and reverse-cutting, so the controller does not need to control its switching state.
  • the voltage division is forced to be achieved through a resistor.
  • the voltage control circuit may further include: a first resistor and a second resistor; the first resistor is connected in parallel at both ends of the clamping diode; and the second resistor is connected in parallel at both ends of the second diode.
  • the voltage control circuit when the voltage control circuit includes a composite device, the voltage control circuit further includes a first resistor and a second resistor; the first resistor is connected in parallel across the clamp diode; the second resistor is connected in parallel across the second diode .
  • the voltage control circuit when the voltage control circuit includes a controllable switch tube, in order to achieve better voltage division for the second diode, the voltage division is forcibly achieved by a resistor.
  • the voltage control circuit further includes: a controller, a first resistor and a second resistor; the controllable switch tube is connected in series between the first diode and the second diode; the first resistor is connected in parallel across the controllable switch tube; The second resistor is connected in parallel across the second diode.
  • the existing resources in Boost can be effectively used to provide the clamping potential of the reference point, for example, a bus capacitor is used to provide the clamping potential, that is, Boost further includes: a first bus capacitor And the second bus capacitor; the first switch tube, the second switch tube, the first diode and the second diode, the first bus capacitor and the second bus capacitor form a second closed loop; the reference point is the first bus capacitor And the common point of the second bus capacitance.
  • the capacitance values of the first bus capacitor and the second bus capacitor are equal, the voltage of the clamp potential at this time is 1/2 bus voltage.
  • Boost can be effectively used to provide the clamping potential of the reference point
  • a bus capacitor is used to provide the clamping potential
  • Boost can also include the following four buses Capacitance: first bus capacitor, second bus capacitor, third bus capacitor and fourth bus capacitor; first switch tube, second switch tube, first diode and second diode, first bus capacitor, first The second bus capacitor, the third bus capacitor and the fourth bus capacitor form a second closed loop; the reference point is any common point between the first bus capacitor, the second bus capacitor, the third bus capacitor and the fourth bus capacitor.
  • the corresponding clamping voltages are different, such as connecting the first bus capacitor and the second bus capacitor At the common point of the capacitor, the voltage of the clamping potential is 1/4 bus voltage.
  • the voltage control circuit may specifically include a third switch tube and a controller; the controller is used to control the switching state of the third switch tube, and when clamping is required, the third switch is controlled When the tube is closed and the clamp is not needed, the third switch tube is controlled to be opened, that is, the voltage control circuit is disabled.
  • the first end of the third switch is connected to the common end of the first diode and the second diode, and the second end of the third switch is connected to the reference point; the controller is used to boost the power conversion circuit When the voltage at the input of the booster power conversion circuit is lower than the start voltage of the boost power conversion circuit, the third switch is closed; the controller is also used to control when the voltage at the input terminal of the boost power conversion circuit is higher than the start voltage of the boost power conversion circuit The third switch is open.
  • the voltage control circuit may specifically include a diode; when clamping is required, the diode is turned on to function, and when clamping is not required, the diode is turned off to reverse function.
  • the voltage control circuit includes a third diode; the cathode of the third diode is connected to the common point of the first diode and the second diode, and the anode of the third diode is connected to the reference point.
  • the first branch may be close to one end of the input anode, specifically: the first end of the inductor is connected to the input anode, and the second end of the inductor is connected to the first diode and the second diode connected in series in sequence.
  • the first branch may be close to one end of the input negative electrode, specifically: the first end of the inductor is connected to the input negative electrode, and the second end of the inductor is connected to the first diode and the second diode connected in series in sequence.
  • an embodiment of the present application also provides a control method for a boost power conversion circuit, which is applied to the boost power conversion circuit described above.
  • the method includes: when it is determined that the voltage at the input end of the boost power conversion circuit is lower than the boost When the starting voltage of the voltage power conversion circuit is reached, the voltage control circuit makes the voltage tolerated by the second diode less than the bus voltage of the boost power conversion circuit; the bus voltage is the voltage difference between the positive bus voltage and the negative bus voltage.
  • the voltage at the input end of the boost power conversion circuit is lower than its own starting voltage, the voltage at the common point of the first diode and the second diode is less than the bus voltage, which can reduce the first diode and the second diode
  • the voltage stress on the common point of the diode facilitates the selection of the diode.
  • the cost of a diode is proportional to the voltage stress it bears. The greater the voltage stress it can withstand, the higher the cost.
  • an embodiment of the present application further provides an inverter, the inverter includes a two-stage circuit, one stage is the boost power conversion circuit described above, namely DC-DC, and the other stage is an inverter circuit, That is DC-AC.
  • the inverter is used in the field of photovoltaic power generation, that is, the input terminal of the boost power conversion circuit is connected to the photovoltaic component, and is used to boost the output voltage of the photovoltaic component and output it to the input terminal of the inverter circuit.
  • the inverter circuit will boost the power
  • the DC power inverter output from the conversion circuit provides AC power to the post-stage circuit.
  • the post-stage circuit may be an AC power grid or an AC load.
  • an embodiment of the present application further provides a photovoltaic power generation device, including a photovoltaic component and the boost power conversion circuit described above; the boost power conversion circuit corresponds to the photovoltaic component in one-to-one correspondence; the input end of the boost power conversion circuit is connected Photovoltaic module; boost power conversion circuit, which is used to boost the output voltage of the connected photovoltaic module and output it to the subsequent circuit.
  • the voltage at the input end of the boost power conversion circuit is lower than its own starting voltage, the voltage at the common point of the first diode and the second diode is less than the bus voltage, which can reduce the first diode and the second diode The voltage stress on the common point of the diode facilitates the selection of the diode.
  • an embodiment of the present application further provides a photovoltaic power generation system, including at least two sets of photovoltaic power generation devices described above; the output ends of the boost power conversion circuits in at least two sets of photovoltaic power generation devices are connected in parallel.
  • a photovoltaic power generation system including at least two sets of photovoltaic power generation devices described above; the output ends of the boost power conversion circuits in at least two sets of photovoltaic power generation devices are connected in parallel.
  • the present invention has at least the following advantages:
  • the boost power conversion circuit includes a voltage control circuit.
  • the boost power conversion circuit includes a first diode and a second diode connected in series, both of which are freewheeling diodes.
  • the first diode and the second diode will withstand the bus voltage in reverse, so it is necessary Perform voltage clamping on the common point of the first diode and the second diode.
  • the voltage control circuit added in the embodiment of the present application may perform voltage clamping for the common point of the first diode and the second diode.
  • the first The voltage that the common point of the diode and the second diode withstands is less than the bus voltage, which can further reduce the voltage stress that the common point of the first diode and the second diode withstand, and facilitate the selection of the diode.
  • Figure 1 is a topology diagram of a three-level Boost circuit
  • Figure 2 is the drive signal waveform when D ⁇ 0.5
  • Figure 3 is the path diagram of the switch mode a when D ⁇ 0.5;
  • Figure 4 is the path diagram of the switch mode b when D ⁇ 0.5;
  • Figure 5 is the path diagram of the switch mode c when D ⁇ 0.5;
  • Figure 6 is the path diagram of the switch mode d when D ⁇ 0.5;
  • Figure 7 is the drive signal waveform when D>0.5
  • Figure 8 is the path diagram of the switch mode a when D>0.5;
  • Figure 9 is a path diagram of the switching mode b when D>0.5;
  • Figure 10 is a path diagram of the switching mode c when D>0.5;
  • Figure 11 is a path diagram of the switching mode d when D>0.5;
  • FIG. 12 is a schematic diagram of the application of multiple Boost circuit output terminals connected in parallel in a photovoltaic power generation system
  • FIG. 13 is a schematic diagram of a boost power conversion circuit provided by an embodiment of the present application.
  • FIG. 14 is a schematic diagram of another boost power conversion circuit provided by an embodiment of the present application.
  • FIG. 15 is a schematic diagram of yet another boost power conversion circuit provided by an embodiment of the present application.
  • 16 is a schematic diagram of an inductor connected to an input negative pole in a boost power conversion circuit provided by an embodiment of the present application;
  • 17a is a schematic diagram of another boost power conversion circuit provided by an embodiment of the present application.
  • 17b is a schematic diagram of a boost power conversion circuit provided by an embodiment of the present application.
  • FIG. 18 is a schematic diagram of another boost power conversion circuit provided by an embodiment of the present application.
  • FIG. 19 is a schematic diagram of yet another boost power conversion circuit provided by an embodiment of the present application.
  • FIG. 20 is a schematic diagram of yet another boost power conversion circuit provided by an embodiment of the present application.
  • 21 is a flowchart of a control method of a boost power conversion circuit provided by an embodiment of the present application.
  • 22 is a schematic diagram of an inverter provided by an embodiment of this application.
  • FIG. 23 is a schematic diagram of a photovoltaic power generation system provided by an embodiment of the present application.
  • FIG. 1 is a topology diagram of a three-level Boost circuit.
  • the three-level Boost circuit includes a flying capacitor C fly , V in is the input voltage, and V bus is the bus voltage on the output side of the Boost circuit, that is, the output voltage.
  • V in is the input voltage
  • V bus is the bus voltage on the output side of the Boost circuit, that is, the output voltage.
  • T1 and T2 are switch tubes
  • D1 and D2 are the anti-parallel diodes of T1 and T2
  • D3 and D4 are freewheeling diodes
  • L is the inductance
  • C bus is the bus capacitance on the output side of the boost circuit.
  • the Boost circuit works in two working modes of duty ratio D ⁇ 0.5 and D>0.5, respectively.
  • the switch states are different in the two modes, and their working principles are introduced below.
  • T is the switching period, and the driving signals of T1 and T2 differ by a phase angle of 180 degrees.
  • the switch modes b and d when D ⁇ 0.5 the two switch modes are identical and appear twice in the same cycle.
  • T1 and T2 are in the off state.
  • the inductor current flows freely through D3 and D4, and D3 and D4 are turned on without reverse voltage stress.
  • the switching mode c when D ⁇ 0.5: T1 is turned off, T2 is turned on, D3 is turned on, and D4 is turned off, and its voltage stress is V bus -V Cfly 0.5V bus .
  • the output voltage can be controlled by controlling the duty cycle of T1 and T2.
  • switch modes a and c when D>0.5 the current flow paths of the two switch modes are exactly the same and appear in different stages of a cycle.
  • T1 and T2 are turned on, and D3 and D4 are turned off.
  • the voltage across the inductor L is V in and the inductor current rises linearly.
  • the voltage stress of D3 and D4 are both 0.5V bus .
  • D4 voltage stress is 0.5V bus .
  • the voltage stress of D3 and D4 are half of the output voltage under various working conditions in steady state, that is, 0.5V bus , and the voltage stress can be selected according to the voltage stress when selecting the diode device. This is the advantage of a three-level boost circuit with flying capacitors.
  • the output terminals of multiple multilevel Boost circuits are connected in parallel, and the voltage of one or more input terminals is lower than the starting voltage of the boost power conversion circuit, the output of the Boost circuit whose input terminal is connected to the input source The bus voltage will be established at the terminal. Since the output terminals of all Boost circuits are connected in parallel, the diode in the Boost circuit that causes the voltage at the input terminal to be lower than the starting voltage of the boost power conversion circuit will withstand the voltage stress of the bus voltage. The diode is damaged, otherwise the diode needs to select a device whose voltage stress is greater than or equal to the bus voltage.
  • the input voltage of the boost power conversion circuit is lower than its own starting voltage.
  • One case means that the input terminal is not connected to the input source.
  • the input terminal of the boost power conversion circuit is not connected.
  • Corresponding photovoltaic modules When the input end of the boost power conversion circuit is not connected to the input source, the voltage at the input end is lower than the starting voltage, that is, it cannot start working.
  • FIG. 12 is a schematic diagram of the output ends of multiple Boost circuits connected in parallel in the field of photovoltaic power generation.
  • the output terminals of the first Boost circuit 100 and the second Boost circuit 200 are connected in parallel, the input terminal of the first Boost circuit 100 is connected to the first photovoltaic module PV1, and the input terminal of the second Boost circuit 200 is connected to the second photovoltaic module PV2.
  • a power station includes N PVs, N is a positive integer, corresponding to N Boost circuits, the user may freely configure the connection of each PV, it is possible that one or more PVs are not connected to the corresponding Boost circuit. At this time, the diode in the Boost circuit not connected to the PV will withstand a higher bus voltage. You can continue to refer to Figure 1.
  • the output terminals of the multi-channel Boost circuit are connected in parallel, that is, the multi-channel common output bus.
  • the present application provides a boost power conversion circuit including a voltage control circuit.
  • the boost power conversion circuit includes a first diode and a second diode connected in series, both of which are freewheeling diodes.
  • the first diode and the second diode will withstand the bus voltage in reverse, so the common point of the first diode and the second diode needs to be Voltage clamping.
  • the voltage control circuit added in the embodiment of the present application may perform voltage clamping for the common point of the first diode and the second diode.
  • the voltage at the input end of the boost power conversion circuit is lower than its own starting voltage
  • the The voltage at the common point of the first diode and the second diode is less than the bus voltage, which in turn can reduce the voltage stress at the common point of the first diode and the second diode, and facilitate the selection of the diode.
  • FIG. 13 is a schematic diagram of a boost power conversion circuit provided by an embodiment of the present application.
  • the boost power conversion circuit includes: a first switching tube T1, a second switching tube T2, an inductor L, a flying capacitor Cfly, a first diode D1, a second diode D2, and a voltage control circuit 300.
  • the inductance L, the first diode D1 and the second diode D2 are serially connected in series to form a first branch, and the first branch is connected in series with the input positive pole and input negative pole of the boost power conversion circuit to form a main loop;
  • the inductor L, the first switch tube T1 and the second switch tube T2 are connected in series to form a first closed loop, the first switch tube T1, the second switch tube T2, the first diode D1 and the The second diode D2 forms a second closed loop; one end of the flying capacitor Cfly is connected to the common point of the first diode D1 and the second diode D2, and the other end of the flying capacitor Cfly It is connected to the common point of the first switch tube T1 and the second switch tube T2.
  • the voltage control circuit 300 has the following two implementation methods:
  • One is connected in series to the third closed loop, and the voltage control circuit is used to make the voltage to which the second diode withstands less than the bus voltage of the boost power conversion circuit;
  • the bus voltage refers to the bus positive voltage and the bus negative voltage. The voltage difference between Vbus+ and Vbus-.
  • the other is that the first end of the voltage control circuit 300 is connected to the common end of the first diode D1 and the second diode D2, and the second end of the voltage control circuit 300 is connected to a reference point, which is used to provide clamping Potential, the clamping potential is between the negative bus potential and the positive bus potential.
  • the voltage control circuit is used for voltage clamping the common point of the first diode and the second diode when the voltage at the input terminal of the boost power conversion circuit is lower than the starting voltage of the boost power conversion circuit.
  • clamping potential can be the same as the reference potential of the positive bus potential and the negative bus potential, for example, both of them refer to ground.
  • the third closed loop is a loop formed by the inductor L, the first switch tube T1, the flying capacitor Cfly, the second diode D2, and the input source, as shown in FIG. 13 by a dashed line.
  • the voltage control circuit 300 is used to clamp the common point of D1 and D2 to make the voltage at the common point of D1 and D2 Less than the bus voltage of the boost power conversion circuit.
  • the function of the voltage control circuit 300 is to clamp the common point of D1 and D2 when the voltage at the input terminal of the boost power conversion circuit is lower than the starting voltage of the boost power conversion circuit. If the common point of D1 and D2 is not voltage clamped, then the output of the boost power conversion circuit is connected in parallel with other boost power conversion circuits, and the input of the other boost power conversion circuit is connected to the input source, so it is established at the output Bus voltage, at this time the bus voltage will be applied to D2, so that D2 withstands the bus voltage.
  • the voltage control circuit 300 forcibly clamps the voltage at the common point of D1 and D2 to a voltage value lower than the bus voltage, so that D2 does not need to withstand a higher bus voltage, thereby reducing the voltage stress of D2, So as to facilitate the selection of D2.
  • the voltage control circuit 300 can be turned off to make it ineffective, that is, the voltage clamping of D2 is not performed, thereby not affecting the normal operation of the boost converter circuit.
  • the voltage control circuit 300 may include a voltage dividing device, which divides the bus voltage and clamps the divided voltage at both ends of D2.
  • the voltage control circuit 300 may also be connected at a reference point whose clamping potential is between the negative bus potential and the positive bus potential. It can be understood that the smaller the clamping voltage, the smaller the voltage stress that D2 bears, and the easier it is for the selection of D2.
  • the second end of the voltage control circuit 300 can be connected to a reference point.
  • the clamping potential of the reference point is between the negative bus potential and the positive bus potential. It is not specifically limited in the embodiments of the present application.
  • the voltage of the clamping potential may be half of the bus voltage or 1/4 of the bus voltage.
  • FIG. 14 is a schematic diagram of another boost power conversion circuit provided by an embodiment of the present application.
  • the voltage control circuit includes at least a controllable switch as an example for introduction.
  • the controllable switch may be a relay, a contactor, a semiconductor switch, or a reverse conduction switch.
  • the semiconductor switch includes a metal oxide semiconductor field effect tube or an insulated gate bipolar transistor, and the reverse conduction type switch tube includes a metal oxide semiconductor field effect transistor or a reverse conduction type insulated gate bipolar transistor.
  • a normally closed type can be used, that is, when there is no input source, it is in a closed state; when it is energized, it is in a closed state.
  • the controller needs to control its switching state.
  • the following uses the controllable switch as the third switch S and the controller to control its state as an example.
  • the voltage of the clamping potential is half of the bus voltage Vbus, that is, 1/2Vbus as an example for description.
  • the first positive bus capacitor Cbus+ and the second bus capacitor Cbus- are connected in series between the output positive pole and the output negative pole of the boost power conversion circuit, and the capacitance values of Cbus+ and Cbus- are equal, that is, Cbus+ and Cbus-
  • the midpoint voltage is half of the bus voltage Vbus. That is, in this embodiment, the first end of S is connected to the common point of D1 and D2, and the second end of S is connected to the common point of Cbus+ and Cbus-.
  • the boost power conversion circuit of this embodiment further includes: a controller (not shown in the figure);
  • the controller is configured to determine that when the voltage at the input end of the boost power conversion circuit is lower than the starting voltage of the boost power conversion circuit, control the controllable switch S to be closed to clamp the voltage control circuit At this time, the voltage of D2 is clamped at 1/2Vbus, so that D2 does not have to withstand the entire bus voltage Vbus.
  • V in 0
  • the bus has established a voltage.
  • the output sides of multiple boost power conversion circuits are connected in parallel and share the same bus.
  • the other Boost has been powered up, but the The circuit has no input voltage V in yet .
  • T1 is equivalent to being bidirectionally short-circuited by D3 and D1, so V in , L, T1, T2, D3 and Cfly can all be regarded as equipotentials.
  • D2 will withstand the entire bus voltage V bus . If D2 is selected according to the 0.5V bus , D2 will overvoltage breakdown. After increasing S.
  • the other boost When the other boost is powered on, it will charge the bus. At the same time, due to S conduction, the current forms a charging loop through S, Cfly, D3 and the input capacitor to ensure that the voltage of the positive terminal of Cfly is not lower than the voltage of the negative bus.
  • the controller is also used to determine that when the input end of the boost power conversion circuit is connected to the input source, the S is controlled to be disconnected to disconnect the voltage control circuit. That is, when S is off, the entire voltage control circuit does not function, and the entire boost power conversion circuit operates normally.
  • Fig. 14 is that the voltage clamping point connected to the second end of S is 1/2Vbus, in addition to 1/2Vbus, other voltage points can also be connected, such as 1/4Vbus, for details, please refer to Fig. 15, boost power conversion
  • the capacitor Cbus4 forms a second closed loop; the reference point is any common point between the first bus capacitor Cbus1, the second bus capacitor Cbus2, the third bus capacitor Cbus3 and the fourth bus capacitor Cbus4.
  • the reference point in Figure 15 takes the common point of Cbus3 and Cbus4 as an example.
  • the voltage provided by the reference point is 1/4Vbus.
  • it can also be other reference points, such as the common point of Cbus1 and Cbus2, and the corresponding clamping voltage is 3/4Vbus.
  • the reference point can also be the common point of Cbus2 and Cbus3, and the corresponding clamping voltage is 1/2Vbus.
  • the voltage corresponding to the reference point may also be other values, as long as it is lower than the bus voltage, which is not specifically limited in the embodiments of the present application.
  • FIG. 14 and FIG. 15 are described by taking the inductance L connected to an end near the input anode as an example, that is, the inductance L, the first diode D1 and the second diode D2 are connected in series to form a first branch , The first branch and the input end of the boost power conversion circuit are connected in series to form a main loop, specifically:
  • the first end of the inductor L is connected to the input positive electrode, and the second end of the inductor L is connected to a first diode D1 and a second diode D2 connected in series.
  • L can also be connected to the end near the input negative electrode.
  • FIG. 16 is a schematic diagram of L connected to the input negative end corresponding to FIG.
  • the inductance L, the first diode D1 and the second diode D2 are serially connected in series to form a first branch, and the first branch and the input end of the boost power conversion circuit are connected in series to form a main loop, specifically:
  • the first end of the inductor L is connected to the input negative electrode, and the second end of the inductor L is connected to a first diode D1 and a second diode D2 connected in series.
  • connection method of the inductor L may also be the above two, that is, the input positive electrode of the boost power conversion circuit or the input negative electrode of the boost power conversion circuit.
  • Fig. 14 to Fig. 16 take the example that the switch included in the voltage control circuit is a controllable switch tube, and the following uses a diode whose switch is not controllable as an example. Due to the unidirectional conduction characteristics of the diode, there is no need for the controller to control its switching state, and it can be automatically turned on or off when the voltage at both ends meets the conditions.
  • FIG. 17a this figure is a schematic diagram of yet another boost power conversion circuit provided by an embodiment of the present application.
  • the voltage control circuit in the boost power conversion circuit provided in this embodiment includes at least a third diode D5.
  • the anode of the third diode D5 is connected to a reference point, and the cathode of the third diode D5 is connected to a common point of the first diode D1 and the second diode D2.
  • V in 0
  • the output sides of multiple boost power conversion circuits are connected in parallel and share the same bus.
  • the other channels are powered up, but the path
  • the boost power conversion circuit has no input voltage V in yet . If D5 is not added, the flying capacitor voltage V Cfly and the input voltage V in are both 0, T1 is equivalent to a two-way short circuit by diodes D3 and D1, so V in , inductance L, switch modules T1, T2, D1 and flying The capacitances can all be regarded as equipotential. At this time, D2 will withstand the entire bus voltage V bus .
  • D2 If D2 is selected according to the 0.5V bus , D2 will overvoltage breakdown. After adding D5, when other roads are powered, the bus will be charged. At the same time, due to the conduction of D5, the current forms a charging loop through D5, flying capacitor, D3 and input capacitor to ensure that the positive voltage of flying capacitor is not lower than negative bus voltage.
  • the voltage control circuit may further include a resistor, for example, for FIG. 14, the resistor and the third switch S are connected in series, and for FIG. 17a, the third diode D5 may In series with the resistor.
  • the number of resistors is not specifically limited, and one resistor may be connected in series, or multiple resistors may be connected in series.
  • the second end of the voltage control circuit described in the above embodiment is connected to a reference point.
  • the following embodiment introduces that the voltage control circuit is connected in series in the loop to divide the bus voltage to achieve clamping of the voltage at the common point of D1 and D2 .
  • FIG. 17b this figure is a schematic diagram of a boost power conversion circuit provided by an embodiment of the present application.
  • a voltage control circuit can be connected in series at any one or more of the multiple positions of the loop.
  • a voltage control circuit can be connected at one position in the loop.
  • the position of the specific series connection is not specifically limited in the embodiment of the present application, and may be the positions shown in A1, A2, A3, A4, and A5 in FIG. 17b, for example.
  • the voltage control circuit connected in series in the loop includes one of a clamping diode, a controllable switch tube or a composite device, wherein the composite device includes a clamping diode and a controllable switch tube connected in parallel.
  • the voltage control circuit further includes a controllable switch tube connected in parallel across the clamp diode or includes a parallel clamp diode and a controllable switch tube;
  • the voltage control circuit further includes: a controller;
  • the controller is configured to control the controllable switch to open when the voltage at the input end of the step-up power conversion circuit is lower than the starting voltage of the step-up power conversion circuit; otherwise control the controllable switch to close .
  • the A1-A5 diode in Figure 17b is connected in parallel with the controllable switch tube.
  • many controllable switch tubes come with anti-parallel diodes. Therefore, such a controllable switch tube can be directly used as a voltage control circuit. It can be understood that the direction in which the diode passes the current is the direction of the current in the return.
  • the following is an example of connecting a voltage control circuit between D1 and D2.
  • FIG. 18 is a schematic diagram of another boost power conversion circuit provided by an embodiment of the present application.
  • the voltage control circuit in the boost power conversion circuit provided by this embodiment includes: a clamping diode D6, a first resistor R1 and a second resistor R2;
  • the anode of the clamping diode D6 is connected to the cathode of the first diode D1, and the cathode of the clamping diode D6 is connected to the anode of the second diode D2;
  • the first resistor R1 is connected in parallel across the clamping diode D6;
  • the second resistor R2 is connected in parallel across the second diode D2.
  • the bus voltage Vbus is applied to the series circuit composed of R1 and R2, and R1 and R2 divide the voltage, so the voltage D4 is subjected to Corresponding to the partial voltage of R2, the voltage on R2 is less than the bus voltage, so the voltage that D4 withstands can be reduced.
  • D6 is also a diode
  • the voltage on R1 is the voltage that D6 withstands. Therefore, in order to unify the selection of the diode, the resistance of R1 and R2 can be equal, that is, R1 and R2 divide the bus voltage equally. However, the resistances of R1 and R2 may not be equal.
  • the voltage control circuit when the voltage control circuit is A4 or A5, it can be applied not only to the case where the voltage at the input end of the boost power conversion circuit is lower than the starting voltage of the boost power conversion circuit, but also It is applicable to the case where the input end is connected to the input source in reverse, that is, the positive and negative poles of the input source are connected in reverse.
  • the implementation of A1-A3 is only applicable to the case where the input voltage is lower than the starting voltage of the boost power conversion circuit.
  • the embodiment corresponding to FIG. 18 includes a clamping diode D6. Since D6 is connected in series in the main loop, that is, when the input terminal of the boost power conversion circuit is connected to the input source, current will flow when D6 is turned on, and the diode current loss It is relatively large, so it wastes electrical energy and reduces efficiency, especially in the field of photovoltaic power generation and reduces the efficiency of photovoltaic power generation. In order to reduce the loss of D6, you can switch in parallel at both ends of D6. When the input of the boost power conversion circuit is connected to the input source, the switch that controls D6 in parallel is closed to short-circuit D6, so that the current does not flow through D6, so D6 can be avoided. The power loss caused by conduction will be described in detail below with reference to the drawings.
  • FIG. 19 is a schematic diagram of another boost power conversion circuit provided by an embodiment of the present application.
  • the voltage control circuit provided in this embodiment further includes: a controller (not shown in the figure); and a fifth switching tube S; the fifth switching tube S is connected in parallel across the clamping diode D6;
  • the controller is used to determine that the voltage at the input terminal of the boost power conversion circuit is lower than the starting voltage of the boost power conversion circuit, and control the fifth switch S to be turned off; and also used to determine the boost When the input end of the power conversion circuit is connected to the input source, control S is closed.
  • both include a fourth diode.
  • the following description does not include the fourth diode, and the voltage clamping of the second diode is achieved through a controllable switch and a voltage dividing resistor.
  • FIG. 20 is a schematic diagram of another boost power conversion circuit provided by an embodiment of the present application.
  • the voltage control circuit provided in this embodiment further includes: a controller (not shown in the figure); and a fifth switch S, a first resistor R1 and a second resistor R2;
  • the first resistor R1 is connected in parallel across the fourth diode D6;
  • the second resistor R2 is connected in parallel across the second diode D2;
  • the controller is used to determine that the voltage at the input end of the boost power conversion circuit is lower than the starting voltage of the boost power conversion circuit, and control S to be turned off; and also used to determine the voltage of the boost power conversion circuit. When the input is connected to the input source, control S is closed.
  • FIGS. 18-20 are all introduced by taking the inductance L connected to the positive input as an example. It can be understood that the embodiments corresponding to FIGS. 18-20 are also applicable to the inductance L connected to the negative input Case.
  • the selection of the controllable switch S in FIGS. 19 and 20 is not limited in the embodiments of the present application, and reference may be made to the selection principles of the controllable switches in the above other embodiments.
  • an embodiment of the present application further provides a control method of the boost power conversion circuit, which will be described in detail below with reference to the drawings.
  • FIG. 21 is a flowchart of a control method of a boost power conversion circuit provided by an embodiment of the present application.
  • control method of the boost power conversion circuit provided in this embodiment is applied to the boost power conversion circuit provided in any of the above embodiments, and the method includes:
  • S210 Determine whether the voltage at the input end of the boosting power conversion circuit is lower than the starting voltage of the boosting power conversion circuit; if yes, execute S220; otherwise, execute S230.
  • whether the input terminal is connected to the input source can be determined by measuring the voltage of the input terminal of the boost power conversion circuit.
  • the voltage of the input terminal is lower than the preset voltage value, it means that the voltage of the input terminal is lower than the boost power The starting voltage of the converter circuit.
  • the voltage control circuit is automatically triggered, it is not necessary to measure the voltage at the input terminal.
  • there is no input source it will automatically close for voltage clamping.
  • the state is closed.
  • the status is off.
  • the embodiment of the present application does not specifically limit how to determine whether the input terminal is connected to the input source.
  • the method provided in this embodiment is applicable to a boost power conversion circuit.
  • the boost power conversion circuit includes a first diode and a second diode connected in series, both of which are freewheeling diodes.
  • the first diode and the second diode will withstand the bus voltage in the reverse direction.
  • the common point of the diode and the second diode is voltage clamped.
  • the voltage control circuit added in the embodiment of the present application may perform voltage clamping for the common point of the first diode and the second diode.
  • the first two The voltage that the common point of the pole tube and the second diode withstands is less than the bus voltage, which can reduce the voltage stress that the common point of the first diode and the second diode withstand, which facilitates the selection of the diode.
  • the boost power conversion circuit can be applied to many occasions, such as the field of photovoltaic power generation.
  • the following uses the boost power conversion circuit as an example in the field of photovoltaic power generation.
  • An embodiment of the present application further provides an inverter.
  • FIG. 22 is a schematic diagram of the inverter provided by the embodiment of the present application.
  • the inverter includes two stages, one stage is the boost power conversion circuit 2000 introduced above, namely DC-DC, and the other stage is the inverter circuit 3000, namely DC-AC.
  • the inverter is used in the field of photovoltaic power generation, that is, the input end of the boost power conversion circuit 2000 is connected to the photovoltaic module PV, and is used to boost the output voltage of the photovoltaic module PV to the input end of the inverter circuit 3000, and the inverter circuit 3000 inverts the DC power output by the boost power conversion circuit 2000 into AC power to the subsequent circuit, and the latter circuit may be an AC power grid or an AC load.
  • the power station in the field of photovoltaic power generation generally includes multiple inverters, the DC-DC output terminals of the multiple inverters are connected in parallel, but for some reasons, the input terminal of a certain DC-DC may not be successfully connected to the photovoltaic. Module, the other parallel DC-DC is successfully connected to the photovoltaic module. Since the output terminals are connected in parallel, the bus voltage of the output terminal of the parallel DC-DC has been established, so that the input terminal is not successfully connected to the DC-DC of the photovoltaic module. Diodes will withstand the back pressure of the bus voltage, but using the DC-DC provided by the embodiments of the present application will advantageously protect the diodes withstand the back pressure, making it easier to select the type.
  • the boost power conversion circuit can be applied to many occasions, such as the field of uninterrupted input sources and the field of photovoltaic power generation.
  • the following uses the boost power conversion circuit as an example in the field of photovoltaic power generation.
  • photovoltaic power generation devices Examples of photovoltaic power generation devices:
  • the photovoltaic power generation device includes a photovoltaic component and the boost power conversion circuit described in any of the above embodiments; wherein, the boost power conversion circuit corresponds to the photovoltaic component in one-to-one correspondence; the input end of the boost power conversion circuit is connected to photovoltaic Module; boost power conversion circuit, used to boost the output voltage of the connected photovoltaic module and output it to the post-stage circuit.
  • the boosting power conversion circuit can be applied to many occasions, such as the field of uninterrupted input sources and the field of photovoltaic power generation.
  • the following uses the boost power conversion circuit as an example in the field of photovoltaic power generation.
  • Embodiments of the present application also provide a photovoltaic power generation system, which will be described in detail below with reference to the drawings.
  • the photovoltaic power generation system provided in this embodiment includes photovoltaic components and at least two sets of photovoltaic power generation devices;
  • the output ends of the boost power conversion circuits in all photovoltaic power generation devices are connected in parallel; the following takes two photovoltaic power generation devices as an example to introduce, correspondingly including two boost power conversion circuits, as shown in FIG. 23, the first boost power conversion
  • the outputs of the circuit 2200 and the second boost power conversion circuit 2300 are connected in parallel.
  • the output terminals of the first boost power conversion circuit 2200 and the second boost power conversion circuit 2300 are both connected to the input terminal of the inverter circuit 3000.
  • each boost power conversion circuit is connected to a corresponding photovoltaic component
  • the step-up power conversion circuit is used to step up the output voltage of the connected photovoltaic module and output it to the post-stage circuit.
  • the input terminal of the first boost power conversion circuit 2200 is connected to the first photovoltaic module PV1
  • the input terminal of the second boost power conversion circuit 2300 is connected to the second photovoltaic module PV2
  • the first boost power conversion circuit 2200 is used to The output voltage of is boosted
  • the second boosted power conversion circuit 2300 is used to boost PV2.
  • some photovoltaic modules may be disconnected from the corresponding boost power conversion circuit, that is, the voltage at the input end of the boost power conversion circuit is lower than the starting voltage of the boost power conversion circuit.
  • the voltage at the input end of the boost power conversion circuit is lower than the starting voltage of the boost power conversion circuit.
  • the output terminals of all boost power conversion circuits can be connected in parallel together, and the inverter can convert the DC power into AC power and feed it back to the AC power grid or AC load.
  • the output terminals of all boost power conversion circuits can also be connected to a DC power grid or a DC load after being connected together in parallel.
  • At least one (item) refers to one or more, and “multiple” refers to two or more.
  • “And/or” is used to describe the association relationship of related objects, indicating that there can be three kinds of relationships, for example, “A and/or B” can mean: there are only A, only B, and A and B at the same time , Where A and B can be singular or plural.
  • the character “/” generally indicates that the related object is a "or” relationship.
  • At least one of the following” or a similar expression refers to any combination of these items, including any combination of a single item or a plurality of items.
  • At least one (a) of a, b, or c can be expressed as: a, b, c, "a and b", “a and c", “b and c", or "a and b and c" ", where a, b, c can be a single or multiple.

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

本申请公开了一种升压功率变换电路、方法、逆变器、装置及系统，该变换电路在三电平Boost上增加电压控制电路，电压控制电路可以串联于第三闭合回路，第三闭合回路为电感、第一开关管、飞跨电容、第二二极管和输入端构成的回路；或，电压控制电路的第一端连接第一二极管和第二二极管的公共端，电压控制电路的第二端连接参考点，参考点提供箝位电位，箝位电位位于负母线电位和正母线电位之间；电压控制电路在升压功率变换电路的输入端的电压低于升压功率变换电路的启动电压时对第一二极管和第二二极管的公共点进行电压箝位，第二二极管承受的电压小于母线正电压。降低第二二极管承受的电压，进而可以选择电压应力较小的二极管。

Description

一种升压功率变换电路、方法、逆变器、装置及系统
本申请要求于2018年12月21日提交中国国家知识产权局、申请号为201811573498.5、发明名称为“一种升压功率变换电路、方法、逆变器、装置及系统”的中国专利申请的优先权，其全部内容通过引用结合在本申请中。
技术领域
本发明涉及电力电子技术领域，尤其涉及一种升压功率变换电路、方法、逆变器、装置及系统。
背景技术
Boost电路为一种升压功率变换电路，可以将输入电压升压后输出，从而实现功率变换。Boost电路包括两电平Boost电路和多电平Boost电路，两电平Boost电路一般应用于电压等级较低的场合，两电平Boost电路的输入电平为两个。多电平Boost电路应用于更高电压等级的场合，多电平Boost电路能够实现输入电平大于或等于三个电平的功率变换。
与两电平Boost电路相比，多电平Boost电路通过改进自身拓扑结构实现多电平，进而实现高电压大功率输出。相同的输入电压，多电平Boost电路突出优点是可以降低功率器件的电压应力，功率器件承受的电压应力是两电平Boost电路的一半，从而可以用较小耐压等级的功率器件实现较高等级的电压输出。同时，由于调制方式的不同，多电平Boost电路与两电平Boost电路相比输入电流纹波小，从而降低了滤波器的体积和设计成本。因此，多电平Boost电路具有广泛的应用前景。
下面以光伏发电领域为例介绍多电平Boost电路的应用。
为了提高光伏组件的发电效率，光伏组件的输出端连接多电平Boost电路的输入端，而多路多电平Boost电路的输出端并联在一起，可实现对连接的光伏组件进行控制，从而使光伏组件输出较大功率。
但是，多路Boost电路的输出端并联时，可能存在某一路Boost电路的输入端未连接光伏组件，即的电压低于所述升压功率变换电路的启动电压，此时其他路Boost电路的输入端连接输入源，因此在所有Boost电路的输出端建立母线电压，对于的电压低于所述升压功率变换电路的启动电压的Boost电路中的功率器件将承受母线电压，因此，需要Boost电路中的二极管必须选用电压应力能够承受母线电压的类型，致使二极管的选型困难，而且电压应力越高，器件成本越高。
发明内容
为了解决现有技术中存在的以上技术问题，本发明提供一种升压功率变换电路、方法、逆变器、装置及系统，能够在升压功率变换电路的输入端的电压低于升压功率变换电路的启动电压时，降低Boost电路中二极管承受的电压，可以选择电压应力较小的二极管。
第一方面，本申请实施例提供一种升压功率变换电路，在三电平Boost电路的基础上增加了电压控制电路，其中三电平Boost电路包括：第一开关管、第二开关管、电感、飞跨电容、第一二极管、第二二极管和电压控制电路；电感、第一二极管和第二二极 管依次串联形成第一支路，第一支路与升压功率变换电路的输入正极和输入负极串联形成主回路，第一二极管和第二二极管的阳极均靠近升压功率变换电路的输入正极，第一二极管和第二二极管的阴极均靠近升压功率变换电路的输入负极；电感、第一开关管和第二开关管串联形成第一闭合回路，第一开关管、第二开关管、第一二极管和第二二极管形成第二闭合回路；飞跨电容的一端连接第一二极管和第二二极管的公共点，飞跨电容的另一端连接在第一开关管和第二开关管的公共点；电压控制电路串联于第三闭合回路，第三闭合回路为电感、第一开关管、飞跨电容、第二二极管和输入正极和输入负极构成的回路；电压控制电路用于使所述第二二极管承受的电压小于所述升压功率变换电路的母线电压；所述母线电压为正母线电压与负母线电压的电压差；或，电压控制电路的第一端连接第一二极管和第二二极管的公共端，电压控制电路的第二端连接参考点，参考点用于提供箝位电位，箝位电位位于负母线电位和正母线电位之间；电压控制电路用于在升压功率变换电路的输入端的电压低于升压功率变换电路的启动电压时对第一二极管和第二二极管的公共点进行电压箝位。
增加的电压控制电路可以为第一二极管和第二二极管的公共点进行电压箝位，在升压功率变换电路的输入端的电压低于自身启动电压时，使第一二极管和第二二极管的公共点承受的电压小于母线电压，进而可以降低第一二极管和第二二极管的公共点承受的电压应力，方便二极管的选型。二极管的成本与承受电压应力成正比，能够承受的电压应力越大，则成本越高。
优选地，可以在第三闭合回路串联电压控制电路，目的是为了与第二二极管形成分压，从而降低其承受的电压应力。其中电压控制电路包括：箝位二极管、可控开关管或复合器件中的一种；复合器件包括并联在一起的箝位二极管与可控开关管。
优选地，由于当电压控制电路包括可控开关管或包括复合器件时，存在可控开关管，而可控开关管不能自动动作，需要控制器控制其开关状态，即开通还是关断。电压控制电路还包括：控制器；控制器用于在升压功率变换电路的输入端的电压低于升压功率变换电路的启动电压时，控制可控开关管断开；控制器还用于在升压功率变换电路的输入端的电压高于升压功率变换电路的启动电压时控制可控开关管闭合。
优选地，由于当电压控制电路包括箝位二极管时，箝位二极管可以自动动作，即正向导通，反向截止的特性，因此不需要控制器控制其开关状态。为了更好地实现给第二二极管分压，通过电阻来强制实现分压。此时，电压控制电路还可以包括：第一电阻和第二电阻；第一电阻并联在箝位二极管的两端；第二电阻并联在第二二极管的两端。
优选地，当电压控制电路包括复合器件时，电压控制电路还包括第一电阻和第二电阻；第一电阻并联在箝位二极管的两端；第二电阻并联在第二二极管的两端。
优选地，当电压控制电路包括可控开关管时，为了更好地实现给第二二极管分压，通过电阻来强制实现分压。电压控制电路还包括：控制器、第一电阻和第二电阻；可控开关管串联在第一二极管和第二二极管之间；第一电阻并联在可控开关管的两端；第二电阻并联在第二二极管的两端。
优选地，为了降低成本，节省电路的体积，可以有效利用目前Boost中的已有资源来提供参考点的箝位电位，例如利用母线电容来提供箝位电位，即Boost还包括：第一母线电容和第二母线电容；第一开关管、第二开关管、第一二极管和第二二极管、第一母线电容和第二母线电容形成第二闭合回路；参考点为第一母线电容和第二母线电容的公共点。当第一母线电容和第二母线电容的容值相等时，此时箝位电位的电压为1/2母线电压。
优选地，为了降低成本，节省电路的体积，可以有效利用目前Boost中的已有资源来提供参考点的箝位电位，例如利用母线电容来提供箝位电位，即Boost还可以包括以下四个母线电容：第一母线电容、第二母线电容、第三母线电容和第四母线电容；第一开关管、第二开关管、第一二极管和第二二极管、第一母线电容、第二母线电容、第三母线电容和第四母线电容形成第二闭合回路；参考点为第一母线电容、第二母线电容、第三母线电容和第四母线电容之间的任意一个公共点。当第一母线电容、第二母线电容、第三母线电容和第四母线电容的容值均相等时，参考点位置不同，则对应的箝位电压不同，例如连接第一母线电容和第二母线电容的公共点时，箝位电位的电压为1/4母线电压。
优选地，当电压控制电路的一端连接参考点时，电压控制电路具体可以包括第三开关管和控制器；控制器用来控制第三开关管的开关状态，当需要箝位时，控制第三开关管闭合，不需要箝位时，控制第三开关管断开，即电压控制电路失去作用。具体地，第三开关管的第一端连接第一二极管和第二二极管的公共端，第三开关管的第二端连接参考点；控制器，用于在升压功率变换电路的输入端的电压低于升压功率变换电路的启动电压时，控制第三开关管闭合；控制器还用于在升压功率变换电路的输入端的电压高于升压功率变换电路的启动电压时控制第三开关管断开。
优选地，当电压控制电路的一端连接参考点时，电压控制电路具体可以包括一个二极管；当需要箝位时，二极管导通起作用，不需要箝位时，二极管反向截止不起作用。具体地，电压控制电路包括第三二极管；第三二极管的阴极连接第一二极管和第二二极管的公共点，第三二极管的阳极连接参考点。
优选地，第一支路可以靠近输入正极一端，具体为：电感的第一端连接输入正极，电感的第二端连接依次串联的第一二极管和第二二极管。
优选地，第一支路可以靠近输入负极一端，具体为：电感的第一端连接输入负极，电感的第二端连接依次串联的第一二极管和第二二极管。
第二方面，本申请实施例还提供一种升压功率变换电路的控制方法，应用于以上介绍的升压功率变换电路，该方法包括：当确定升压功率变换电路的输入端的电压低于升压功率变换电路的启动电压时，电压控制电路使第二二极管承受的电压小于升压功率变换电路的母线电压；所述母线电压为正母线电压与负母线电压的电压差。在升压功率变换电路的输入端的电压低于自身启动电压时，使第一二极管和第二二极管的公共点承受的电压小于母线电压，进而可以降低第一二极管和第二二极管的公共点承受的电压应力，方便二极管的选型。二极管的成本与承受电压应力成正比，能够承受的 电压应力越大，则成本越高。
第三方面，本申请实施例还提供一种逆变器，该逆变器包括两级电路，一级为以上介绍的升压功率变换电路，即DC-DC，另一级为逆变电路，即DC-AC。该逆变器应用于光伏发电领域，即升压功率变换电路的输入端连接光伏组件，用于将光伏组件的输出电压升压后输出给逆变电路的输入端，逆变电路将升压功率变换电路输出的直流电逆变为交流电提供给后级电路，后级电路可以为交流电网，也可以为交流负载。
第三方面，本申请实施例还提供一种光伏发电装置，包括光伏组件和以上介绍的升压功率变换电路；升压功率变换电路和光伏组件一一对应；升压功率变换电路的输入端连接光伏组件；升压功率变换电路，用于将连接的光伏组件的输出电压升压后输出给后级电路。在升压功率变换电路的输入端的电压低于自身启动电压时，使第一二极管和第二二极管的公共点承受的电压小于母线电压，进而可以降低第一二极管和第二二极管的公共点承受的电压应力，方便二极管的选型。
第四方面，本申请实施例还提供一种光伏发电系统，包括至少两套以上介绍的光伏发电装置；至少两套光伏发电装置中的升压功率变换电路的输出端并联在一起。当其中一套光伏发电装置中的升压功率变换电路的输入端的电压低于其自身启动电压时，其自身的二极管将承受与其并联的其他升压功率变换电路的母线电压的反压，因此可以利用电压控制电路为二极管进行电压箝位，使二极管承受比母线电压低的电压应力，有利于二极管的选型。
与现有技术相比，本发明至少具有以下优点：
该升压功率变换电路包括电压控制电路，升压功率变换电路包括串联的第一二极管和第二二极管，两者均为续流二极管。当升压功率变换电路的输入端的电压低于升压功率变换电路的启动电压，但是其输出端存在母线电压时，第一二极管和第二二极管将反向承受母线电压，因此需要对第一二极管和第二二极管的公共点进行电压箝位。本申请实施例增加的电压控制电路可以为第一二极管和第二二极管的公共点进行电压箝位，在升压功率变换电路的输入端的电压低于自身启动电压时，使第一二极管和第二二极管的公共点承受的电压小于母线电压，进而可以降低第一二极管和第二二极管的公共点承受的电压应力，方便二极管的选型。
附图说明
为了更清楚地说明本申请实施例或现有技术中的技术方案，下面将对实施例或现有技术描述中所需要使用的附图作简单地介绍，显而易见地，下面描述中的附图仅仅是本申请中记载的一些实施例，对于本领域普通技术人员来讲，在不付出创造性劳动的前提下，还可以根据这些附图获得其它的附图。
图1为三电平Boost电路的拓扑结构图；
图2为D<0.5时驱动信号波形图；
图3为D<0.5时开关模态a的路径图；
图4为D<0.5时开关模态b的路径图；
图5为D<0.5时开关模态c的路径图；
图6为D<0.5时开关模态d的路径图；
图7为D>0.5时驱动信号波形图；
图8为D>0.5时开关模态a的路径图；
图9为D>0.5时开关模态b的路径图；
图10为D>0.5时开关模态c的路径图；
图11为D>0.5时开关模态d的路径图；
图12为多个Boost电路的输出端并联在光伏发电系统应用的示意图；
图13为本申请实施例提供的一种升压功率变换电路示意图；
图14为本申请实施例提供的另一种升压功率变换电路的示意图；
图15为本申请实施例提供的再一种升压功率变换电路的示意图；
图16为本申请实施例提供的升压功率变换电路中电感连接输入负极的示意图；
图17a为本申请实施例提供的又一种升压功率变换电路的示意图；
图17b为本申请实施例提供的一种升压功率变换电路的示意图；
图18为本申请实施例提供的另一种升压功率变换电路的示意图；
图19为本申请实施例提供的再一种升压功率变换电路的示意图；
图20为本申请实施例提供的又一种升压功率变换电路的示意图；
图21为本申请实施例提供的升压功率变换电路的控制方法流程图；
图22为本申请实施例提供的逆变器的示意图；
图23为本申请实施例提供的光伏发电系统示意图。
具体实施方式
为了使本领域技术人员更好地理解本申请实施例提供的技术方案，下面以多电平Boost电路为三电平Boost电路为例介绍其工作原理。
参见图1，该图为三电平Boost电路的拓扑结构图。
该三电平Boost电路包括飞跨电容C fly，V in为输入电压，V bus为Boost电路输出侧的母线电压，即输出电压。T1和T2均为开关管，D1、D2分别是T1和T2反并联的二极管，D3和D4为续流二极管，L为电感，C bus为Boost电路输出侧的母线电容。
根据输入电压Vin和输出电压C bus的关系，该Boost电路分别工作于占空比D<0.5和D>0.5两种工作模式。当V in>0.5Vbus时占空比D<0.5，当V in<0.5V bus时占空比D>0.5。两种模式下开关状态有所差异，下面分别介绍其工作原理。
(1)D<0.5
当V in>0.5V bus时占空比D<0.5，D<0.5时驱动信号波形如图2所示，各开关模态下的电流流通路径如图3-图6所示，其中实线表示电流通路。
其中，T为开关周期，T1、T2驱动信号相差180度相角。
参见图3，D<0.5时开关模态a：T1开通，T2关断。D4导通，D3截止。由于飞跨电容电压控制为V Cfly＝0.5V bus，电感L两端承受电压V in-0.5V bus>0，电感电流线性上升。此时D3电压应力为0.5V bus，D4管导通，无反电压应力。
参见图4和图6，D<0.5时开关模态b和d：两个开关模态完全相同，在同一个周期内 出现两次。T1、T2均处于关断状态。电感电流通过D3、D4续流，D3、D4导通，不存在反电压应力。
参见图5，D<0.5时开关模态c：T1关断，T2开通，D3导通，D4截止，其电压应力为V bus-V Cfly＝0.5V bus。根据电感两端电压伏秒守恒原理，即一个工作周期内，电感两端电压与时间的乘积为0，可得：
(V in-V bus+V Cfly)·DT+(V in-V bus)·(1-2D)T+(V in-V Cfly)·DT＝0
化简可得
Figure PCTCN2019115075-appb-000001
通过控制T1、T2的占空比即可控制输出电压。
(2)D>0.5
当V in<0.5V bus时占空比D>0.5，D>0.5时驱动信号波形如图7所示，D>0.5时各开关模态下的电流流通路径如图8-图11所示，其中实线表示电流通路。
参见图8和图10，D>0.5时开关模态a、c：两种开关模态电流流通路径完全相同，出现在一个周期的不同阶段。T1、T2开通，D3、D4截止。电感L两端电压为V in，电感电流线性上升。D3和D4的电压应力均为0.5V bus。
参见图9，D>0.5时开关模态b：T1开通，T2关断，D4导通，D3截止。D3电压应力为0.5V bus。
参见图11，D>0.5时开关模态d：T2开通，T1关断，D3导通，D4截止。D4电压应力为0.5V bus。
同样根据电感两端电压伏秒守恒原理，可得
Figure PCTCN2019115075-appb-000002
从上面的分析可以看出，稳态情况下各种工作状态时，D3、D4的电压应力均为输出电压的一半，即0.5V bus，二极管器件选型时均可按该电压应力进行选取，这是三电平带有飞跨电容Boost电路的优点。
但是，当多个多电平Boost电路的输出端并联在一起，其中一路或多路的输入端的电压低于所述升压功率变换电路的启动电压时，输入端连接输入源的Boost电路的输出端将建立母线电压，由于所有Boost电路的输出端并联在一起，此时造成输入端的电压低于所述升压功率变换电路的启动电压的Boost电路中的二极管承受母线电压大小的电压应力，将造成二极管损坏，否则二极管需要选型电压应力大于或等于母线电压的器件。
需要说明的是，升压功率变换电路的输入端的电压低于其自身的启动电压一种情况是指其输入端没有连接输入源，例如在光伏发电领域，升压功率变换电路的输入端没有连接对应的光伏组件。当升压功率变换电路的输入端没有连接输入源时，其输入端的电压低于启动电压，即无法启动工作。
作为一种示例，参见图12，该图为光伏发电领域，多个Boost电路的输出端并联在一起的示意图。
第一Boost电路100和第二Boost电路200的输出端并联在一起，第一Boost电路 100的输入端连接第一光伏组件PV1，第二Boost电路200的输入端连接第二光伏组件PV2。在实际运用中，一个电站包括N路PV，N为正整数，对应N个Boost电路，用户可能自由配置各路PV的连接，有可能一路或多路PV不与对应的Boost电路连接。此时不连接PV的Boost电路中的二极管将承受较高的母线电压。可以继续参见图1，当存在多路Boost电路的输出端并联时，即多路共输出母线，若其他路已上电，但该路Boost电路还未上电，此时已有母线电压，由于该路飞跨电容电压和输入电压均为0，D3阴极到D2正极之间近似可以看成等电位，此时D4承受整个母线电压Vbus，如果D4按照0.5Vbus应力来选型，此时D4会过压被击穿。
因此，本申请为了解决以上存在的技术问题，提供一种升压功率变换电路，包括电压控制电路。升压功率变换电路包括串联的第一二极管和第二二极管，两者均为续流二极管。当升压功率变换电路的输出端存在母线电压时，第一二极管和第二二极管将反向承受母线电压，因此需要对第一二极管和第二二极管的公共点进行电压箝位。本申请实施例增加的电压控制电路可以为第一二极管和第二二极管的公共点进行电压箝位，在升压功率变换电路的输入端的电压低于其自身的启动电压时，使第一二极管和第二二极管的公共点承受的电压小于母线电压，进而可以降低第一二极管和第二二极管的公共点承受的电压应力，方便二极管的选型。
电路实施例一：
参见图13，该图为本申请实施例提供的一种升压功率变换电路示意图。
本实施例提供的升压功率变换电路，包括：第一开关管T1、第二开关管T2、电感L、飞跨电容Cfly、第一二极管D1、第二二极管D2和电压控制电路300。
所述电感L、第一二极管D1和第二二极管D2依次串联形成第一支路，所述第一支路与升压功率变换电路的输入正极和输入负极串联形成主回路；所述电感L、所述第一开关管T1和第二开关管T2串联形成第一闭合回路，所述第一开关管T1、所述第二开关管T2、所述第一二极管D1和所述第二二极管D2形成第二闭合回路；所述飞跨电容Cfly的一端连接所述第一二极管D1和第二二极管D2的公共点，所述飞跨电容Cfly的另一端连接在所述第一开关管T1和第二开关管T2的公共点。
所述电压控制电路300有以下两种实现方式：
一种是串联于第三闭合回路，电压控制电路用于使所述第二二极管承受的电压小于所述升压功率变换电路的母线电压；母线电压是指母线正电压和母线负电压之间的电压差，即Vbus+与Vbus-之间的电压差。
另一种是电压控制电路300的第一端连接第一二极管D1和第二二极管D2的公共端，电压控制电路300的第二端连接参考点，参考点的用于提供箝位电位，所述箝位电位位于负母线电位和正母线电位之间。电压控制电路用于在升压功率变换电路的输入端的电压低于升压功率变换电路的启动电压时对第一二极管和第二二极管的公共点进行电压箝位。
需要说明的是，箝位电位与正母线电位和负母线电位的参考电位可以相同，例如 均以地为参考电位。
其中第三闭合回路为所述电感L、第一开关管T1、飞跨电容Cfly、第二二极管D2和输入源构成的回路，如图13所示的虚线形成的凹形回路。
当升压功率变换电路的输入端的电压低于升压功率变换电路的启动电压时，电压控制电路300用于对D1和D2的公共点进行电压箝位，以使D1和D2的公共点的电压小于所述升压功率变换电路的母线电压。
电压控制电路300的作用是当升压功率变换电路的输入端的电压低于所述升压功率变换电路的启动电压时，对D1和D2的公共点进行电压箝位。如果不对D1和D2的公共点进行电压箝位，则由于升压功率变换电路的输出端并联其他升压功率变换电路，其他升压功率变换电路的输入端连接输入源，因此，在输出端建立母线电压，此时母线电压将施加在D2上，使D2承受母线电压。而本实施例中电压控制电路300强制将D1和D2的公共点的电压箝位在比母线电压小的一个电压值，这样D2便不需要承受较高的母线电压，从而降低D2的电压应力，从而便于D2的选型。
另外，当升压变换电路的输入端连接输入源时，可以断开电压控制电路300，使其不起作用，即不对D2进行电压箝位，进而不影响升压变换电路的正常工作。
具体实现时，电压控制电路300可以包括分压器件，将母线电压分压后将分压电压箝位在D2的两端。电压控制电路300也可以连接在一个参考点，该参考点的箝位电位位于负母线电位和正母线电位之间。可以理解的是，箝位电压越小，D2承受的电压应力越小，对于D2的选型越容易。
下面分别结合附图介绍电压控制电路300的具体实现方式，首先介绍电压控制电路300的第二端可以连接在一个参考点，该参考点的箝位电位位于负母线电位和正母线电位之间，具体值本申请实施例中不做具体限定。例如，箝位电位的电压可以为母线电压的一半或所述母线电压的1/4。
电路实施例二：
参见图14，该图为本申请实施例提供的另一种升压功率变换电路的示意图。
本实施例以电压控制电路至少包括可控开关为例进行介绍，可控开关可以为继电器、接触器、半导体开关或逆导型开关管。半导体开关包括金属氧化物半导体场效应管或绝缘栅双极型晶体管，逆导型开关管包括金属氧化物半导体场效应管或逆导型绝缘栅双极型晶体管。对于可控开关为继电器或接触器时，可以采用常闭型，即没有输入源时，为闭合状态；当通电时为断开状态。
对于半导体开关和逆导型开关管，需要控制器控制其开关状态，下面以可控开关为第三开关管S，需要控制器控制其状态为例进行介绍。
本实施例中以箝位电位的电压为所述母线电压Vbus的一半，即1/2Vbus为例进行介绍。一般情况下，升压功率变换电路的输出正极和输出负极之间连接有串联的第一母线电容Cbus+和第二母线电容Cbus-，而且Cbus+和Cbus-的容值相等，即Cbus+和Cbus-的中点电压为母线电压Vbus的一半。即本实施例中S的第一端连接D1和D2的 公共点，S的第二端连接Cbus+和Cbus-的公共点。
由于可控开关管不可以自动进行开关动作，因此本实施例的升压功率变换电路，还包括：控制器(图中未示出)；
所述控制器，用于确定所述升压功率变换电路的输入端的电压低于升压功率变换电路的启动电压时，控制所述可控开关管S闭合以使所述电压控制电路进行箝位，即此时将D2的电压箝位在1/2Vbus，这样D2不必承受整个母线电压Vbus。
下面介绍添加S后的工作原理：
升压功率变换电路的输入端还未上电(V in＝0)但母线已建立电压，例如多路升压功率变换电路的输出侧并联，共用同一母线，其他路Boost已上电，但该路还没有输入电压V in。若不加S，由于此时V Cfly和V in均为0，T1相当于被D3和D1双向短路，故V in、L、T1、T2、D3和Cfly均近似可以看成等电位。此时D2将会承受整个母线电压V bus，若D2按照0.5V bus来选型，D2将会过压击穿。增加S后。当其他路Boost上电时，会给母线充电，与此同时由于S导通，电流通过S、Cfly、D3以及输入电容形成充电回路，保证Cfly正端电压不低于负母线电压。
所述控制器，还用于确定所述升压功率变换电路的输入端连接输入源时，控制所述S断开以使电压控制电路断开。即当S断开时，整个电压控制电路不起作用，整个升压功率变换电路正常运行。
图14是以S的第二端连接的电压箝位点为1/2Vbus，除了连接1/2Vbus以外，还可以连接其他电压点，例如连接1/4Vbus，具体可以参见图15，升压功率变换电路的输出正极和输出负极之间连接有串联的四个母线电容，分别为：第一母线电容Cbus1、第二母线电容Cbus2、第三母线电容Cbus3和第四母线电容Cbus4；所述第一开关管T1、所述第二开关管T2、所述第一二极管D1和所述第二二极管D2、第一母线电容Cbus1、第二母线电容Cbus2、第三母线电容Cbus3和第四母线电容Cbus4形成第二闭合回路；所述参考点为第一母线电容Cbus1、第二母线电容Cbus2、第三母线电容Cbus3和第四母线电容Cbus4之间的任意一个公共点。图15中参考点以Cbus3和Cbus4的公共点为例，当四个母线电容的容值相等时，则参考点提供的电压为1/4Vbus。另外除了图15所示的参考点以外，还可以为其他参考点，例如Cbus1和Cbus2的公共点，对应的箝位电压为3/4Vbus。当然参考点也可以为Cbus2和Cbus3的公共点，对应的箝位电压为1/2Vbus。
图14和图15均是示意说明参考点的位置，参考点对应的电压也可以为其他数值，只要比母线电压小即可，本申请实施例中不做具体限定。
另外，图14和图15均是以电感L连接在靠近输入正极一端为例进行的介绍，即所述电感L、第一二极管D1和第二二极管D2依次串联形成第一支路，所述第一支路与升压功率变换电路的输入端串联形成主回路，具体为：
所述电感L的第一端连接所述输入正极，所述电感L的第二端连接依次串联的第一二极管D1和第二二极管D2。
可以理解的是，L也可以连接在靠近输入负极的一端，具体可以参见图16，该图 为与图14对应的L连接在输入负极一端的示意图。
所述电感L、第一二极管D1和第二二极管D2依次串联形成第一支路，所述第一支路与升压功率变换电路的输入端串联形成主回路，具体为：
所述电感L的第一端连接所述输入负极，所述电感L的第二端连接依次串联的第一二极管D1和第二二极管D2。
以下实施例中电感L的连接方式也可以为以上两种，即连接升压功率变换电路的输入正极或连接升压功率变换电路的输入负极。
图14-图16以电压控制电路包括的开关为可控开关管为例进行了介绍，下面以开关为不可控的二极管为例进行介绍。由于二极管的单向导通特性，因此，不需要控制器控制其开关状态，其两端电压满足条件时实现自动导通或关断。
电路实施例三：
参见图17a，该图为本申请实施例提供的又一种升压功率变换电路的示意图。
本实施例提供的升压功率变换电路中的电压控制电路至少包括第三二极管D5。
所述第三二极管D5的阳极连接参考点，所述第三二极管D5的阴极连接所述第一二极管D1和第二二极管D2的公共点。
下面介绍添加S后的工作原理：
升压功率变换电路的输入端还未上电(V in＝0)但母线已建立电压，例如多路升压功率变换电路的输出侧并联，共用同一母线，其他路已上电，但该路升压功率变换电路还没有输入电压V in。若不加D5，此时飞跨电容电压V Cfly和输入电压V in均为0，T1相当于被二极管D3和D1双向短路，故V in、电感L、开关模块T1、T2、D1和飞跨电容均近似可以看成等电位。此时D2将会承受整个母线电压V bus，若D2按照0.5V bus来选型，D2将会过压击穿。增加D5后，当其他路上电时，会给母线充电，与此同时由于D5导通，电流通过D5、飞跨电容、D3以及输入电容形成充电回路，保证飞跨电容正端电压不低于负母线电压。
需要说明的是图14-图17a对应的实施例，其中所述电压控制电路还可以包括电阻，例如对于图14，电阻和第三开关管S串联，对于图17a，第三二极管D5可以和电阻串联。本申请实施例中不具体限定电阻的个数，可以串联一个电阻，也可以串联多个电阻。
以上实施例介绍的电压控制电路的第二端连接参考点，下面的实施例介绍电压控制电路串联于回路中，用于对母线电压进行分压，实现对D1和D2公共点的电压进行箝位。
电路实施例四：
参见图17b，该图为本申请实施例提供的一种升压功率变换电路的示意图。
本实施例中示意了在回路的多个位置中的任意一个或多个可以串联电压控制电路，为了简单节省器件和成本，可以在回路中的一个位置串联电压控制电路。具体串联的 位置本申请实施例中不做具体限定，例如可以为图17b中的A1、A2、A3、A4和A5所示的位置。
需要说明的是，串联于回路中的电压控制电路包括：箝位二极管、可控开关管或复合器件中的一种，其中复合器件包括并联在一起的箝位二极管与可控开关管。
当所述电压控制电路还包括并联在所述箝位二极管两端的可控开关管或包括并联的箝位二极管与可控开关管时；
所述电压控制电路还包括：控制器；
所述控制器，用于当所述升压功率变换电路的输入端的电压低于升压功率变换电路的启动电压时，控制所述可控开关管断开；反之控制所述可控开关管闭合。
图17b中的A1-A5位二极管与可控开关管并联的形式，实际应用中，很多可控开关管自带反并联的二极管，因此可以直接利用这样的可控开关管来作为电压控制电路。可以理解的是，其中二极管通过电流的方向是回来中电流的方向。
下面以在D1和D2之间连接电压控制电路为例进行介绍。
参见图18，该图为本申请实施例提供的又一种升压功率变换电路的示意图。
本实施例提供的升压功率变换电路中电压控制电路包括：箝位二极管D6、第一电阻R1和第二电阻R2；
所述箝位二极管D6的阳极连接所述第一二极管D1的阴极，所述箝位二极管D6的阴极连接所述第二二极管D2的阳极；
所述第一电阻R1并联在所述箝位二极管D6的两端；
所述第二电阻R2并联在所述第二二极管D2的两端。
下面介绍本实施例的工作原理：
当升压功率变换电路的输入端的电压低于所述升压功率变换电路的启动电压时，母线电压Vbus施加在R1和R2组成的串联回路上，R1和R2进行分压，因此D4承受的电压对应R2的分压，R2上的电压小于母线电压，因此可以降低D4承受的电压，当然R2越小，R1越大，D4承受的电压越小。但是由于D6也是二极管，R1上的电压为D6承受的电压，因此为了二极管的选型统一，可以使R1和R2的阻值相等，即R1和R2均分母线电压。但是，R1和R2的阻值也可以不相等。
需要说明的是，本实施例提供的方案中，当电压控制电路为A4或A5时，不但可以适用于升压功率变换电路的输入端的电压低于升压功率变换电路的启动电压的情况，还适用于输入端反接输入源的情况，即输入源的正负极接反的情况。而A1-A3的实现方式仅适用于输入端的电压低于升压功率变换电路的启动电压的情况。
电路实施例五：
图18对应的实施例中包括箝位二极管D6，由于D6串联在主回路中，即当升压功率变换电路的输入端连接输入源时，D6导通时会流过电流，而二极管的电流损耗比较大，因此浪费电能，减低效率，尤其是光伏发电领域，降低光伏发电效率。为了降低D6的损耗，可以再D6两端并联开关，当升压功率变换电路的输入端连接输入源时， 控制D6并联的开关闭合，将D6短路，进而电流不流过D6，因此可以避免D6导通带来的电能损耗，下面结合附图进行详细介绍。
参见图19，该图为本申请实施例提供的又一种升压功率变换电路的示意图。
本实施例提供的电压控制电路，还包括：控制器(图中未示出)；以及第五开关管S；第五开关管S并联在所述箝位二极管D6的两端；
所述控制器，用于确定所述升压功率变换电路的输入端的电压低于所述升压功率变换电路的启动电压时，控制第五开关管S断开；还用于确定所述升压功率变换电路的输入端连接输入源时，控制S闭合。
本实施例中，当升压功率变换电路的输入端连接输入源时，控制S断开，从而D6和D2串联，R1和R2对母线电压进行分压，其中D6承受R1分的电压，D2承受R2分的电压，因此可以降低D2承受的电压应力，避免D2独自承受母线电压。当升压功率变换电路的输入端连接输入源时，不必对D2进行电压箝位，因此，可以控制S闭合，进而将D6短路，因此，电流不通过D6，可以避免D6通过对电流造成电能损耗。
电路实施例六：
图18和图19对应的实施例中，均包括第四二极管，下面介绍不包括第四二极管，通过可控开关和分压电阻实现对第二二极管的电压箝位。
参见图20，该图为本申请实施例提供的另一种升压功率变换电路的示意图。
本实施例提供的电压控制电路还包括：控制器(图中未示出)；以及第五开关管S、第一电阻R1和第二电阻R2；
S串联在所述第一二极管D1和第二二极管D2之间；
所述第一电阻R1并联在所述第四二极管D6的两端；
所述第二电阻R2并联在所述第二二极管D2的两端；
所述控制器，用于确定所述升压功率变换电路的输入端的电压低于所述升压功率变换电路的启动电压时，控制S断开；还用于确定所述升压功率变换电路的输入端连接输入源时，控制S闭合。
当升压功率变换电路的输入端的电压低于所述升压功率变换电路的启动电压时，需要将第D2的电压应力，因此，此时需要R1和R2分压，控制S断开，从而实现R1和R2分压。D2承受的电压应力为R2分的电压，R2分的电压比母线电压低，从而可以避免D2承受母线电压大小的电压应力。当升压功率变换电路的输入端连接输入源时，此时为了降低电路损耗，可以控制S闭合，从而S将R1短路，避免R1引起的电能损耗。
需要说明的是，图18-图20对应的实施例均是以电感L连接输入正极为例进行的介绍，可以理解的是，图18-图20对应的实施例同样适用于电感L连接输入负极的情况。另外，图19和图20中的可控开关S的选型本申请实施例中不做限定，可以参考以上其他实施例中的可控开关的选型原则。
方法实施例：
基于以上实施例提供的一种升压功率变换电路，本申请实施例还提供一种升压功率变换电路的控制方法，下面结合附图对其进行详细介绍。
参见图21，该图为本申请实施例提供的升压功率变换电路的控制方法流程图。
本实施例提供的升压功率变换电路的控制方法，应用于以上任意一个实施例提供的升压功率变换电路，该方法包括：
S210：判断升压功率变换电路的输入端的电压是否低于升压功率变换电路的启动电压；如果是，则执行S220；反之执行S230。
一种可能的实现方式，可以通过测量升压功率变换电路的输入端的电压来判断输入端是否连接输入源，当输入端电压低于预设电压值，说明输入端的电压低于所述升压功率变换电路的启动电压。当然如果电压控制电路为自动触发的，可以不必测量输入端的电压，当没有输入源时自动闭合进行电压箝位，例如对于常闭型的继电器或接触器，当没有输入源时，状态为闭合。有输入源时，状态为断开。本申请实施例中不具体限定如何判断输入端是否连接输入源。
S220：当确定所述升压功率变换电路的输入端的电压低于升压功率变换电路的启动电压时，所述电压控制电路使所述第二二极管承受的电压小于所述升压功率变换电路的母线电压。
S230：当确定所述升压功率变换电路的输入端的电压大于或等于启动电压时，所述电压控制电路停止箝位。
本实施例提供的方法适用于升压功率变换电路，升压功率变换电路包括串联的第一二极管和第二二极管，两者均为续流二极管。当升压功率变换电路的输入端的电压低于其自身的启动电压，而输出端存在母线电压时，第一二极管和第二二极管将反向承受母线电压，因此需要对第一二极管和第二二极管的公共点进行电压箝位。本申请实施例增加的电压控制电路可以为第一二极管和第二二极管的公共点进行电压箝位，在升压功率变换电路的输入端没有输入源接入时，使第一二极管和第二二极管的公共点承受的电压小于母线电压，进而可以降低第一二极管和第二二极管的公共点承受的电压应力，方便二极管的选型。
基于以上实施例提供的一种升压功率变换电路和方法，其中升压功率变换电路可以应用于很多场合，例如光伏发电领域等。下面以升压功率变换电路应用于光伏发电领域为例进行介绍。
本申请实施例还提供一种逆变器，参见图22，该图为本申请实施例提供的逆变器的示意图。
该逆变器包括两级电路，一级为以上介绍的升压功率变换电路2000，即DC-DC，另一级为逆变电路3000，即DC-AC。该逆变器应用于光伏发电领域，即升压功率变换电路2000的输入端连接光伏组件PV，用于将光伏组件PV的输出电压升压后输出给逆变电路3000的输入端，逆变电路3000将升压功率变换电路2000输出的直流电逆变为 交流电提供给后级电路，后级电路可以为交流电网，也可以为交流负载。
由于光伏发电领域的电站一般包括多路逆变器，这样多路逆变器中DC-DC的输出端并联在一起，但是由于某些原因，可能某一路DC-DC的输入端没有成功连接光伏组件，这样并联的其他路DC-DC成功连接光伏组件，由于输出端并联在一起，因此，并联的DC-DC的输出端的母线电压已经建立，致使输入端没有成功连接光伏组件的DC-DC中的二极管将承受母线电压的反压，但是利用本申请实施例提供的DC-DC将有利保护承受反压的二极管，使其选型较容易。
基于以上实施例提供的一种升压功率变换电路和方法，其中升压功率变换电路可以应用于很多场合，例如不间断输入源领域，光伏发电领域等。下面以升压功率变换电路应用于光伏发电领域为例进行介绍。
光伏发电装置实施例：
本实施例提供的光伏发电装置，包括光伏组件和以上任意一个实施例介绍的升压功率变换电路；其中，升压功率变换电路和光伏组件一一对应；升压功率变换电路的输入端连接光伏组件；升压功率变换电路，用于将连接的光伏组件的输出电压升压后输出给后级电路。
光伏发电系统实施例：
基于以上实施例提供的一种升压功率变换电路、方法和光伏发电装置，其中升压功率变换电路可以应用于很多场合，例如不间断输入源领域，光伏发电领域等。下面以升压功率变换电路应用于光伏发电领域为例进行介绍。
本申请实施例还提供一种光伏发电系统，下面结合附图对其进行详细介绍。
具体可以继续参见图23，本实施例提供的光伏发电系统，包括光伏组件和至少两套以上的光伏发电装置；
所有光伏发电装置中的升压功率变换电路的输出端并联在一起；下面以两个光伏发电装置为例进行介绍，对应包括两个升压功率变换电路，如图23，第一升压功率变换电路2200和第二升压功率变换电路2300的输出端并联在一起。而且第一升压功率变换电路2200和第二升压功率变换电路2300的输出端均连接逆变电路3000的输入端。
每个所述升压功率变换电路的输入端连接对应的光伏组件；
所述升压功率变换电路，用于将连接的光伏组件的输出电压升压后输出给后级电路。其中，第一升压功率变换电路2200的输入端连接第一光伏组件PV1，第二升压功率变换电路2300的输入端连接第二光伏组件PV2，第一升压功率变换电路2200用于对PV1的输出电压进行升压，第二升压功率变换电路2300用于对PV2进行升压。
但是实际应用中，可能有的光伏组件断开与对应的升压功率变换电路的连接，即升压功率变换电路的输入端的电压低于所述升压功率变换电路的启动电压。此时为了降低升压功率变换电路中第二二极管的电压应力，需要对其进行电压箝位，从而降低其承受的电压应力，便于器件选型。
可以理解的是，所有升压功率变换电路的输出端并联在一起后可以连接逆变器，由逆变器将直流电逆变为交流电后反馈给交流电网，或者交流负载。另外，所有升压功率变换电路的输出端并联在一起后也可以连接直流电网，或者连接直流负载。
应当理解，在本申请中，“至少一个(项)”是指一个或者多个，“多个”是指两个或两个以上。“和/或”，用于描述关联对象的关联关系，表示可以存在三种关系，例如，“A和/或B”可以表示：只存在A，只存在B以及同时存在A和B三种情况，其中A，B可以是单数或者复数。字符“/”一般表示前后关联对象是一种“或”的关系。“以下至少一项(个)”或其类似表达，是指这些项中的任意组合，包括单项(个)或复数项(个)的任意组合。例如，a，b或c中的至少一项(个)，可以表示：a，b，c，“a和b”，“a和c”，“b和c”，或“a和b和c”，其中a，b，c可以是单个，也可以是多个。
以上所述，仅是本发明的较佳实施例而已，并非对本发明作任何形式上的限制。虽然本发明已以较佳实施例揭露如上，然而并非用以限定本发明。任何熟悉本领域的技术人员，在不脱离本发明技术方案范围情况下，都可利用上述揭示的方法和技术内容对本发明技术方案做出许多可能的变动和修饰，或修改为等同变化的等效实施例。因此，凡是未脱离本发明技术方案的内容，依据本发明的技术实质对以上实施例所做的任何简单修改、等同变化及修饰，均仍属于本发明技术方案保护的范围内。

Claims (16)

  1. 一种升压功率变换电路，其特征在于，包括：第一开关管、第二开关管、电感、飞跨电容、第一二极管、第二二极管和电压控制电路；
    所述电感、所述第一二极管和所述第二二极管依次串联形成第一支路，所述第一支路与所述升压功率变换电路的输入正极和输入负极串联形成主回路，所述第一二极管和所述第二二极管的阳极均靠近所述升压功率变换电路的输入正极，所述第一二极管和所述第二二极管的阴极均靠近所述升压功率变换电路的输入负极；所述电感、所述第一开关管和所述第二开关管串联形成第一闭合回路，所述第一开关管、所述第二开关管、所述第一二极管和所述第二二极管形成第二闭合回路；所述飞跨电容的一端连接所述第一二极管和所述第二二极管的公共点，所述飞跨电容的另一端连接在所述第一开关管和所述第二开关管的公共点；
    所述电压控制电路串联于第三闭合回路，所述第三闭合回路为所述电感、所述第一开关管、所述飞跨电容、所述第二二极管、所述输入正极和输入负极构成的回路，所述电压控制电路用于使所述第二二极管承受的电压小于所述升压功率变换电路的母线电压,所述母线电压为正母线电压与负母线电压的电压差；或，所述电压控制电路的第一端连接所述第一二极管和所述第二二极管的公共端，所述电压控制电路的第二端连接参考点，所述参考点用于提供箝位电位，所述箝位电位位于负母线电位和正母线电位之间；所述电压控制电路用于在所述升压功率变换电路的输入端的电压低于所述升压功率变换电路的启动电压时对所述第一二极管和所述第二二极管的公共点进行电压箝位。
  2. 根据权利要求1所述的功率变换电路，其特征在于，当所述电压控制电路串联于所述第三闭合回路时，所述电压控制电路包括：箝位二极管、可控开关管或复合器件中的一种；
    所述复合器件包括并联在一起的箝位二极管与可控开关管。
  3. 根据权利要求2所述的升压功率变换电路，其特征在于，当所述电压控制电路包括所述可控开关管或包括所述复合器件时，所述电压控制电路还包括：控制器；
    所述控制器，用于在所述升压功率变换电路的输入端的电压低于所述升压功率变换电路的启动电压时，控制所述可控开关管断开；所述控制器还用于在所述升压功率变换电路的输入端的电压高于所述升压功率变换电路的启动电压时控制所述可控开关管闭合。
  4. 根据权利要求2所述的升压功率变换电路，其特征在于，当所述电压控制电路包括所述箝位二极管时，所述电压控制电路还包括：第一电阻和第二电阻；
    所述第一电阻并联在所述箝位二极管的两端；
    所述第二电阻并联在所述第二二极管的两端。
  5. 根据权利要求2或权利要求3所述的升压功率变换电路，其特征在于，当所述电压控制电路包括复合器件时，所述电压控制电路还包括第一电阻和第二电阻；
    所述第一电阻并联在所述箝位二极管的两端；
    所述第二电阻并联在所述第二二极管的两端。
  6. 根据权利要求2或权利要求3所述的升压功率变换电路，其特征在于，当所述电压 控制电路包括可控开关管时，所述电压控制电路还包括：控制器、第一电阻和第二电阻；
    所述可控开关管串联在所述第一二极管和第二二极管之间；
    所述第一电阻并联在所述可控开关管的两端；
    所述第二电阻并联在所述第二二极管的两端。
  7. 根据权利要求1所述的升压功率变换电路，其特征在于，还包括：第一母线电容和第二母线电容；
    所述第一开关管、所述第二开关管、所述第一二极管和所述第二二极管、所述第一母线电容和所述第二母线电容形成第二闭合回路；所述参考点为所述第一母线电容和第二母线电容的公共点。
  8. 根据权利要求1所述的升压功率变换电路，其特征在于，还包括：第一母线电容、第二母线电容、第三母线电容和第四母线电容；
    所述第一开关管、所述第二开关管、所述第一二极管和所述第二二极管、所述第一母线电容、所述第二母线电容、第三母线电容和第四母线电容形成第二闭合回路；所述参考点为所述第一母线电容、所述第二母线电容、第三母线电容和第四母线电容之间的任意一个公共点。
  9. 根据权利要求7或8所述的升压功率变换电路，其特征在于，所述电压控制电路包括第三开关管和控制器；所述第三开关管的第一端连接所述第一二极管和所述第二二极管的公共端，所述第三开关管的第二端连接所述参考点；
    所述控制器，用于在所述升压功率变换电路的输入端的电压低于所述升压功率变换电路的启动电压时，控制所述第三开关管闭合；所述控制器还用于在所述升压功率变换电路的输入端的电压高于所述升压功率变换电路的启动电压时控制所述第三开关管断开。
  10. 根据权利要求7或8所述的升压功率变换电路，其特征在于，所述电压控制电路包括第三二极管；所述第三二极管的阴极连接所述第一二极管和第二二极管的公共点，所述第三二极管的阳极连接所述参考点。
  11. 根据权利要求1-10任一项所述的升压功率变换电路，其特征在于，所述电感、第一二极管和第二二极管串联形成第一支路，所述第一支路与升压功率变换电路的输入端串联形成主回路，具体为：
    所述电感的第一端连接所述输入正极，所述电感的第二端连接依次串联的所述第一二极管和所述第二二极管。
  12. 根据权利要求1-10任一项所述的升压功率变换电路，其特征在于，所述电感、所述第一二极管和所述第二二极管串联形成第一支路，所述第一支路与升压功率变换电路的输入端串联形成主回路，具体为：
    所述电感的第一端连接所述输入负极，所述电感的第二端连接依次串联的所述第一二极管和所述第二二极管。
  13. 一种升压功率变换电路的控制方法，其特征在于，应用于权利要求1-12任一项所述的升压功率变换电路，该方法包括：
    当确定所述升压功率变换电路的输入端的电压低于所述升压功率变换电路的启动电压 时，所述电压控制电路使所述第二二极管承受的电压小于所述升压功率变换电路的母线电压；所述母线电压为正母线电压与负母线电压的电压差。
  14. 一种逆变器，其特征在于，包括逆变电路和权利要求1-12任一项所述的升压功率变换电路；
    所述升压功率变换电路，用于将接收到的电压升压后输出给所述逆变电路的输入端；
    所述逆变电路，用于将所述升压功率变换电路输出的直流电逆变为交流电。
  15. 一种光伏发电装置，其特征在于，包括光伏组件和权利要求1-12任一项所述的升压功率变换电路；所述升压功率变换电路和所述光伏组件一一对应；
    所述升压功率变换电路的输入端连接所述光伏组件；
    所述升压功率变换电路，用于将连接的所述光伏组件的输出电压升压后输出给后级电路。
  16. 一种光伏发电系统，其特征在于，包括至少两套如权利要求15所述的光伏发电装置；
    所述至少两套光伏发电装置中的所述升压功率变换电路的输出端并联在一起。
PCT/CN2019/115075 2018-12-21 2019-11-01 一种升压功率变换电路、方法、逆变器、装置及系统 WO2020125235A1 (zh)

Priority Applications (3)

Application Number Priority Date Filing Date Title
EP19898626.7A EP3739740A4 (en) 2018-12-21 2019-11-01 STEP UP CONVERTER CIRCUIT, PROCESS, INVERTER, DEVICE AND SYSTEM
US16/938,119 US11418114B2 (en) 2018-12-21 2020-07-24 Boost power conversion circuit, method, inverter, apparatus, and system
US17/872,525 US20220368227A1 (en) 2018-12-21 2022-07-25 Boost power conversion circuit, method, inverter, apparatus, and system

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
CN201811573498.5A CN109756115B (zh) 2018-12-21 2018-12-21 一种升压功率变换电路、方法、逆变器、装置及系统
CN201811573498.5 2018-12-21

Related Child Applications (1)

Application Number Title Priority Date Filing Date
US16/938,119 Continuation US11418114B2 (en) 2018-12-21 2020-07-24 Boost power conversion circuit, method, inverter, apparatus, and system

Publications (1)

Publication Number Publication Date
WO2020125235A1 true WO2020125235A1 (zh) 2020-06-25

Family

ID=66402872

Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/CN2019/115075 WO2020125235A1 (zh) 2018-12-21 2019-11-01 一种升压功率变换电路、方法、逆变器、装置及系统

Country Status (4)

Country Link
US (2) US11418114B2 (zh)
EP (1) EP3739740A4 (zh)
CN (1) CN109756115B (zh)
WO (1) WO2020125235A1 (zh)

Families Citing this family (16)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN109039061B (zh) * 2018-08-29 2020-03-24 阳光电源股份有限公司 一种多电平boost装置
CN109756115B (zh) * 2018-12-21 2021-12-03 华为数字技术（苏州）有限公司 一种升压功率变换电路、方法、逆变器、装置及系统
CN110165888B (zh) 2019-06-11 2024-05-14 阳光电源股份有限公司 三电平Boost电路、多路输出并联系统
CN110429815B (zh) * 2019-07-19 2021-04-20 华为技术有限公司 升压电路以及升压电路的控制方法
US11362589B2 (en) * 2019-08-28 2022-06-14 Delta Electronics, Inc. Flying capacitor converter
CN112491270B (zh) * 2019-09-12 2023-04-11 厦门科华数能科技有限公司 一种升压电路及其装置和系统
CN112701913A (zh) * 2019-10-22 2021-04-23 阳光电源股份有限公司 升压功率变换电路及其控制方法与应用装置
CN110896278B (zh) * 2019-12-06 2021-02-12 阳光电源股份有限公司 电容钳位型直流变换电路及其控制方法
CN110943618A (zh) * 2019-12-13 2020-03-31 科华恒盛股份有限公司 一种多电平升压电路及其装置和系统
CN110994975B (zh) * 2019-12-18 2020-11-10 阳光电源股份有限公司 一种电容钳位式直流变换电路
AU2019478501B2 (en) 2019-12-20 2023-10-12 Huawei Digital Power Technologies Co., Ltd. Dc-dc converter
CN111262429B (zh) * 2020-03-17 2021-06-11 阳光电源股份有限公司 直流变换电路及光伏逆变装置
CN111371323B (zh) * 2020-04-03 2024-06-18 锦浪科技股份有限公司 一种boost升压功率变换电路及其控制方法
CN113972836B (zh) * 2020-07-22 2024-01-30 华为数字能源技术有限公司 一种三电平升压变换器及控制方法
CN113098253B (zh) * 2021-04-28 2022-10-18 厦门科华数能科技有限公司 一种功率变换电路
CN113258773A (zh) * 2021-05-18 2021-08-13 阳光电源股份有限公司 一种电力变换系统和电力变换装置及其控制方法

Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20120182775A1 (en) * 2008-04-25 2012-07-19 Delta Electronics, Inc. Three-phase buck-boost power factor correction circuit and controlling method thereof
CN107070215A (zh) * 2017-04-12 2017-08-18 特变电工西安电气科技有限公司 一种三电平boost共地系统及其控制方法
CN108258899A (zh) * 2017-12-29 2018-07-06 华为技术有限公司 一种升压功率变换电路
CN108847769A (zh) * 2018-06-22 2018-11-20 阳光电源股份有限公司 一种三电平boost装置及其控制方法
CN109756115A (zh) * 2018-12-21 2019-05-14 华为数字技术（苏州）有限公司 一种升压功率变换电路、方法、逆变器、装置及系统

Family Cites Families (20)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US6043501A (en) * 1995-04-19 2000-03-28 Gec Alsthom Acec Transport S.A. Continuous input cell for data acquisition circuits
CN101888734B (zh) * 2009-05-13 2014-07-16 通用电气公司 带升/降压功率因数校正dc-dc转换器的电子镇流器
US8604757B2 (en) * 2010-02-01 2013-12-10 Mitsubishi Electric Corporation DC/DC power conversion apparatus
CN202231930U (zh) * 2011-10-21 2012-05-23 北京市电力公司 白炽灯灯座
CN108988836B (zh) * 2013-12-16 2023-02-28 台达电子企业管理（上海）有限公司 控制方法及功率电路的封装结构
DE102014109048B4 (de) * 2014-06-27 2022-02-10 Sma Solar Technology Ag Schaltungsanordnung mit einer Mehrfachniveau-Halbbrückenanordnung
US9966875B2 (en) * 2015-01-29 2018-05-08 Hongliang Wang Five-level topology units and inverter thereof
WO2017028776A1 (zh) * 2015-08-14 2017-02-23 汪洪亮 高电压增益的五电平逆变器拓扑电路
CN106559004B (zh) * 2015-09-29 2019-04-12 华为技术有限公司 多电平逆变器
WO2017076366A1 (zh) * 2015-11-06 2017-05-11 汪洪亮 五电平逆变器拓扑电路及三相五电平逆变器拓扑电路
EP3439158B1 (en) * 2016-03-28 2022-06-22 Mitsubishi Electric Corporation Power conversion device
CN107677877A (zh) * 2016-08-01 2018-02-09 庄祥荣 中高压带电指示电路
CN106230253B (zh) 2016-09-09 2019-05-07 华为技术有限公司 升压功率变换电路和控制方法
JP6462969B2 (ja) * 2016-10-11 2019-01-30 東芝三菱電機産業システム株式会社 電力変換装置及びその運転方法
US9979291B2 (en) * 2016-10-26 2018-05-22 Futurewei Technologies, Inc. Inverter apparatus
CN206370772U (zh) * 2017-01-24 2017-08-01 杭州中恒派威电源有限公司 一种反激输出高压二极管替代电路
US10554128B2 (en) * 2018-01-05 2020-02-04 Futurewei Technologies, Inc. Multi-level boost converter
CN108923632B (zh) * 2018-08-29 2020-03-24 阳光电源股份有限公司 一种多电平boost装置
CN109039061B (zh) * 2018-08-29 2020-03-24 阳光电源股份有限公司 一种多电平boost装置
CN108988635B (zh) * 2018-09-13 2019-09-20 阳光电源股份有限公司 一种多电平Boost变换器、逆变系统及控制方法

Patent Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20120182775A1 (en) * 2008-04-25 2012-07-19 Delta Electronics, Inc. Three-phase buck-boost power factor correction circuit and controlling method thereof
CN107070215A (zh) * 2017-04-12 2017-08-18 特变电工西安电气科技有限公司 一种三电平boost共地系统及其控制方法
CN108258899A (zh) * 2017-12-29 2018-07-06 华为技术有限公司 一种升压功率变换电路
CN108847769A (zh) * 2018-06-22 2018-11-20 阳光电源股份有限公司 一种三电平boost装置及其控制方法
CN109756115A (zh) * 2018-12-21 2019-05-14 华为数字技术（苏州）有限公司 一种升压功率变换电路、方法、逆变器、装置及系统

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
See also references of EP3739740A4

Also Published As

Publication number Publication date
US11418114B2 (en) 2022-08-16
EP3739740A1 (en) 2020-11-18
CN109756115B (zh) 2021-12-03
CN109756115A (zh) 2019-05-14
US20220368227A1 (en) 2022-11-17
US20200358356A1 (en) 2020-11-12
EP3739740A4 (en) 2021-04-14

Similar Documents

Publication Publication Date Title
WO2020125235A1 (zh) 一种升压功率变换电路、方法、逆变器、装置及系统
US11264894B2 (en) Converter and current control system thereof
WO2016119736A1 (zh) 五电平拓扑单元及五电平逆变器
CN104638949A (zh) 无电阻器预充电
CN110572069B (zh) 一种双向dc-ac变换器
WO2024037058A1 (zh) 飞跨电容三电平dcdc变换器、光伏系统及控制方法
WO2018127054A1 (zh) 具有多输入的混联变换器和使用其的充换电设施
CN111277131A (zh) 一种升压功率变换电路及其控制方法
CN216216527U (zh) 直流变换电路、直流变换器、逆变器和光伏发电系统
CN109167525B (zh) 一种新型非隔离五电平逆变器
CN105262355B (zh) 一种多端口逆变器
CN109217704B (zh) 一种抑制系统漏电流非隔离型五电平逆变器
CN110572026A (zh) 一种钳位型三电平升压功率变换电路
CN113364334B (zh) 一种双并联Buck-Boost逆变器及其控制方法
US10630195B2 (en) Converter and power conversion device using same
CN215528878U (zh) 一种开关电源装置
CN211908650U (zh) 一种升压功率变换电路
CN215120607U (zh) 一种直流充电桩功率拓扑及直流充电桩
US11217993B2 (en) Conversion system with high voltage side and low voltage side
CN210724554U (zh) 一种嵌位型升压功率变换电路结构
CN110729913B (zh) 一种单级式高增益五开关Boost型逆变器
CN110729896B (zh) 基于mmc的双向直流变换器及其控制系统
TWI658687B (zh) 直流至交流轉能器及其控制方法
CN111525792A (zh) 一种混合开关电感高输出电压增益z源逆变器
CN112054700B (zh) 一种变换电路

Legal Events

Date Code Title Description
121 Ep: the epo has been informed by wipo that ep was designated in this application

Ref document number: 19898626

Country of ref document: EP

Kind code of ref document: A1

ENP Entry into the national phase

Ref document number: 2019898626

Country of ref document: EP

Effective date: 20200814

NENP Non-entry into the national phase

Ref country code: DE